DE1616312B2 - Single sideband transmission device according to the third method - Google Patents

Description

There are several ways to transmit single sideband signals:

a) the filter method,

b) the phase method,

c) the so-called third method.
35

The third method was published for the first time

by Donald K. Weaver under the title "A third method of generation and detection of single-sideband signals "in Proc. Inst. Radio Engs., 1956,

Vol. 44, No. 12, pp. 1703 to 1705.

Further publications are:

IFH Aspinwall, "The third method" in Wireless World, 1959, No. 1, pp. 39 to 43,
H. Meiηke and FW Gundlach, "The third method" in the pocket book of high frequency technology, 1962, pp. 1311 and 1499,
P. AIfke, "A new single sideband modulator" in radio technology, 1958, issue 6, pp. 169 and 170,

"Zeitschriftendienst" in radio technology, 1959, issue 13, pp. 477 and 478,
Günter Peltz, "SSB according to the third method" in the DL-QTC, 1963, issue 2, pp. 50 to 54.

The block diagram of an SSB receiver constructed according to this method is shown in Fig. 1. From this it can be seen that the received signal is split into two branches 1 and 2, each with an RF modulator and an LF modulator included. Both modulators are made up of a common oscillator each fed, but with a 90 ° phase difference. The RF modulators are used to keep the phase constant operated with a fixed oscillator frequency which is equal to the intermediate frequency of the is located in front of the RF modulators superhet part. The AF balance modulators must be precisely

be adjusted so that the audio frequency of the LF 'oscillator is not audible. The transmitter contains the same steps, but in reverse order (see block diagram Fig. 2).

The mode of operation of the Third Method in sending and receiving is best based on the following, for an IF of 450 kHz applicable examples can be seen. · .- · .-

Example of the mode of operation when sending (all frequency specifications in kHz)

1. Speech frequency spectrum to be transmitted (1.5 kHz is the AF center frequency)

2. Division into two branches with NF spectrum as in 1

3. Mix in balance modulators with

a NF of

gives the mixed products

and

4. Only go through the low-pass filter with 1.2 kHz cutoff frequency

5. Now mix in HF balance modulators _t with an HF of

* results

and superimposed with it

6. Now both branches are put together. As a result of the different phase position the HF and the LF oscillator

■ Vibrations in each branch cancel out either the increasing frequencies, and the decreasing frequencies are retained, or after reversing one of the phases by 180 ° the falling frequencies cancel each other out and the rising frequencies are retained. Either a "lower sideband" or an "upper sideband" appears. These frequencies can then be mixed up and be broadcast.

7. Due to deficiencies in the phase position or in the composition, at most one of the overlapping spectra cannot be completely extinguished, by no means but this can generate a frequency that is outside the single sideband transmission range 448.8 ... 451.2 kHz.

0 3 15 27

0.3 ... 1.5 ... 2.7

1.5

1.8 ... 3.0 ... 4.2
1.2 ... 0 ... 1.2

1.2 ... 0 ... 1.2

450

451.2 ... 450 ... 448.8
448.8 ... 450 ... 451.2

0.3 ... 1.5 .. ■ ·: 2.7 ■>.

1.5

4.2 ■ >> 1.2

1.2 ... 0 ... 1.2

450

451.2 ... 450 ... 448.8 448.8 ... 450 ... 451.2

451.2 ... 450 ... 448.8

or
448.8 ... 450 ... 451.2

The most important property of the third method compared to the other two methods is there in the fact that the "other sideband" can indeed arise on the sending and receiving sides, but that it is in reality can never be transmitted or received alongside the transmitted sideband, but only in the transmitted sideband, thus superimposed with it, which turns out to be an increase in the subordinate low-frequency Interference level affects.

The SSB transmission method according to the third method was also used in practice. A Commercial radio transmitting and receiving device built according to this system is in the already mentioned Publication "Wireless World" 1959, No. 1, pp. 41 to 43, described. .: ■■ "■■ ;;

Despite the advantages mentioned, this transmission method has not yet been able to establish itself because On the receiving side, the interference immunity in the present switching mode is too low and the setting of the Phase relationships is too complicated and because on the transmitter side the oscillator oscillation leads to a radiation the HF medium frequency would lead, must be suppressed very strongly.

Example of the mode of operation during reception (all frequency information in kHz)

1. Speech frequency spectrum to be transmitted (1.5 kHz is the AF center frequency)

2. So receiver IF spectrum z. B.

(450 kHz is HF center frequency) ........

3. Division into two branches with HF spectrum as in 2

4. Oscillator frequency in the middle of the transmission range '.'.'....'. '..'. '.' .. ". I

gives the mixed products after the HF modulators. '

5. These are available again after the low-pass filters with a 1.2 kHz cutoff frequency

6. a) Now mix in balance modulators with a low frequency oscillation (reading frequency) from

b) This results in mixed products as

understandable (readable) language

and superimposed as inverse, incomprehensible language _t

7. Now both branches are put together. As a result of the different phase position the high frequency and low frequency oscillator vibrations in each branch cancel each other out when composing either the inverse frequencies, and the understandable ones are retained, or after reversing the polarity of one of the phases by 180 °, the intelligible frequencies cancel each other out, and the inverse are retained. You can change the "reading direction" of the HF spectrum by using a polarity switch Turn No. 2 so that the speech frequency spectrum is not only legible when it is concurrent with the HF spectrum increases ("upper sideband"), but also when increasing speech frequencies correspond to decreasing high frequencies ("Lower sideband").

8. All out of range

448.8 ... 451.2 kHz occurring frequencies (carrier or other sideband or Jammers) only generate frequencies above 1.2 kHz under No. 4, which are filtered out will.

0.3 ... 1.5 ... 2.7
448.8 ... 450.0 ... 451.2

. ":." ._ .: "iI:.
448.8 ... 450 ... 451.2

450
1,2 ..; 0 ... 1.2

1.2 ..: 0 ... 1.2

0.3. 2.7.

1.5

1.5.
1.5.

.2.7

II

448.8 ... 450 ... 451.2

450
1.2 ... 0 ... 1.2

.0.3

0.3 ... 1.5 ... 2.7

or
2.7: .. 1.5 ... 0.3

0.3.

2.7.

1.5

.1.5 ... 2.7
.1.5 ... 0.3

... The subject of the application is now based on the task of the previous transfer procedures according to the third method with regard to interference immunity and phase adjustment and one on the transmitter side to render radiated HF center carriers harmless or to use them advantageously and frequency conversions, as it was usual in superhets up to now to be avoided. .

This task is solved in the following way: The gain distribution on HF and LF stages is reversed contrary to the prior art, i. i.e., the main reinforcement is moved to the NF part, while the RF input and intermediate frequency part only. amplified so much that the noise the modulator stage, which converts from HF to LF, no longer appears significantly. the Gain in the LF part is supplemented by inserting DC voltage amplifiers between filters and LF modulators, so that the signals at least about the noise and the residual sound of the LF balance modulators be raised (A b b. 3 a). The further amplification takes place in the NF part after the NF modulators. The DC voltage amplifiers can, according to the previous switching method of the mo-

15 16

dulators in the third 'method, in push-pull oscillators and the lines to the RF modulators, execution or with single-ended input and its shielding, neutralization by means of compensation outputs work when the HF and NF modulation HF to the pre-stages, common zero point for the oscillator zero lines, weak grid output

The measures mentioned have the effect that strong 5 control, etc.

Jammers, in addition to the signals to be received, with the present arrangement is also reception

before the final sieving, not significantly amplitude-keyed telegraphy is possible. This amplified so that it does the modulator function by lowering the upper limit frequency cannot affect the low-pass filter on the highest NF to be transmitted by amplitudes that are too high nen. The interference immunity is therefore compared to the herio of the telegraphic impulses. The oscillator is on the conventional switching method significantly improved. Reception frequency set, but not synchronized AIs Another advantage is to be assessed that this is rated. In the filters arise in polarity and arrangement especially good for the so-called integrated ph'tude changing telegraphic pulses (depending on the pha circuit technology is suitable because there is only a small position between the receiving frequency and the oscillator frequency), Part of the overall build leads to high frequency. 15 which, according to the third method, have an NF part

It should be noted, however, that any interspersion graphic signal result with a pitch that is the same the oscillator oscillation is on the inputs of the HF generator frequency. For example, the Modulators to a tuning process differentiated from the oscillator frequency depending on the phase position If the DC voltage at the modulator output frequency decreases, it changes accordingly Gangen leads, but also the pitch of the NF-side signals through corresponding zero 20. It will Point shifting of the DC voltage amplifiers thus achieves the same effect as when spinning can be compensated. In order to do this, the coordination of a conventional telegraphy zero point shift is required do not become too high too recipient. Consider the advantages mentioned above or in order to avoid them entirely, but also lent immunity to interference remain with telegraphy erhalum an HF-side volume control without verbs; in addition, there is now the possibility of Change such disruptive DC voltages by using relatively simple low-pass filters to be able to, is z. B. to achieve a shielding of the Os- neatly narrow bandwidths. So can zillators, so according to the invention low-scatter Ausman z. B. in poor reception conditions guidance required. Skip bandwidths of ± 20 Hz or less,

The .the HF converter (mixer) supplying Os- 3 ° so that the telegraphy connections, also because of the zillator can be made variable or as reduced noise, very reliable. Fixed or crystal oscillator, in the latter case the transmission speed decreases, Lower frequency oscillator for the HF modulator but an otherwise disturbed connection can at least are coordinated and the phases are thus maintained in synchronism. Displacement links. 35 With such narrow-band connections, the

Now that a greater RF gain is not exactly adhering to the transmit and receive frequencies more is needed, one can be important to the superhet principle. Even just by the influence do without at all and straight-ahead reception of the ionosphere frequency fluctuations occur, skip over (Fig. 3b). The HF oscillator then has to cope with this problem, the straight-ahead switching very much auf'der HF center frequency of the transmitted transmitter 4 ° opposite, because to control the transmitter from the spectrum and must be synchronized with the receiver, or vice versa (known transceiver 90 ° phase shifter be matched. Straight-ahead principle), no frequency conversions are required, Reception is according to the current state of the single-channel operation of two or more stations with Technology as completely unsuitable for SSB receivers - mutual tracking of the operating frequency is seen, here, however, according to the invention, the opposite 45 is particularly easy to carry out here, and the The case, because in addition to the previously mentioned transmitter can be switched to straight-ahead with telegraphy ten favorable properties still be built up an improvement. There is a corresponding one for telephony the noise ratio (no more mixer) and straight-ahead operation of the transmitter only possible if there is one further improvement of the interference immunity is balanced particularly well by sen HF modulator Elimination of all image frequency and interference problems (elimination of this disadvantage: see further sub-problems come in addition. The RF pre-amplification can claim). It should be noted that the company is still further .lowered, .. the branch signal and LF distortions for the "DC voltage amplifiers and Strengthening can be increased even more. Since the full for the oscillator must be stable, constant and final selectivity already achieved. The described arrangements are improved

as long as the signals are still in the order of magnitude of 55 due to the fact that the sending and receiving side instead of habit a few microvolts, external oscillators with subsequent phase shifts result quite well favorable interference immunity values (far-offs now HF ring oscillators (= with resonant circuits) lesson + near selection + cross modulation + in-. or HF ring generators (= with other frequency interference). end elements, e.g. B. RC elements) and equal-

^{According to the} invention, however, especially 6o-wise low-frequency ring oscillators or low-frequency ring generators for straight-ahead reception, it must be prevented that the can be used. Such known oscillator on the circuit parts in front of the HF-Modu- ring oscillators and ring generators consist of lators too heavily scattered, because this would make an HF-side one or more amplifier or switching stages and volume control very difficult. These are other elements that do not necessarily take place spatially by means known per se: especially ⁶ 5 must be arranged in a ring, but good or even double shielding of the oscillator from one another from a wave or from pulses, itself or a closed oscillator box with only one Repeatedly, with the desired frequency connection to the chassis, push-pull circuit of the OS can be run through. Such a ring generator can

17 18

be active, that is, in itself an excitation in relation to both branches may only be 45 ° or provide sufficient feedback, or it can passively 135 or 225 or 315 °, i.e. odd multiples of so that each step is 45 ° from a central control so that it is triggered or switched with respect to the receiving unit. In every frequency 90 ° result. It must then be appropriate The element of such a ring generator has the phase shifter elements or in the case of ring oscillators running wave or the rotating impulse an on- connection connections for 45 ° or 135 or 225 or their phase position, e.g. B. compared to a fixed 315 °, that is, odd multiples of 45 ° phase under-receiving frequency. The phase shift must be different. Due to this arrangement, however, each link will not be of the same size. When one reaches that the radiation of the oscillator on the once through all the links, the result is that the receiving frequency is much lower, the oseine Total phase shift of 360 ° or multiple oscillator and modulator stages are no longer required times it. The frequency of the generated vibrations are so strongly shielded, and the HF-side sound depends on the operating voltage and the data strength control is less critical; also can of the components. Here such ring oscillators are now the oscillator because of the lower oscillation frequency gates and ring generators are used, in which the 15 run more stable, there are no drive plate phase shift between the individual stages voltages due to strong received signals, and the or divisions in the event of a frequency change by tuning supply of the transmitter in straight-ahead operation mung stay the same, z. B. by simultaneous and the receiver oscillator is reaction-free, equal change in the phase-shifting one. It should be noted that the self-doubling Elements or in particular the operating voltages. 2 ° modulator in the receiver not through a Ver-In addition these ring generators have to be replaced at points, because these are exactly the same be accessible, the 90 ° phase difference would have to be shielded strongly like an equal, so that the HF or LF modulators are a frequently oscillating oscillator, each branch can be connected. As in the transmitter, such a self-doubling Ring generators and ring oscillators in which the modulator is used (see Fig. 5). Circuit are used, shows A b b. 4. Accordingly, the transition to oscillator frequency = V2 they are connected in a single-ended circuit; how'e ?. is shown, for example, on the HF ring oscillator, if only telephony and a superheterodyne or in push-pull circuit with two voltages each circuit according to claim 1 is used, opposite phase position and a phase difference. The above arrangements are improved differed from branch to branch by 90 °, as is the case with one in front of each HF modulator game of the LF ring generator shows. Buffer stage or instead of the common HF pre

It also appears expedient to have a separate HF preamplifier stage from the club amplifier stage in the following for the HF-side (A b b. 6). This is beneficial in cases where Vibration or impulse generators only ever from 35 mixing oscillators that interfere with the HF modulator inputs, have products on the LF-side of generators. These are thereby at the entrance speak. When using such ring generators, the other branch is prevented from entering. The Pufferren and ring oscillators do not require additional or RF pre-stages must therefore be in a corresponding phase shifter and their synchronous design be carried out, z. B. with Pentmung. The curve shape of the emitted oscillation 4 ° boring equipped (low capacity anode / grid) or can be sinusoidal or rectangular. The period shielded. These levels must be the same, it may each square pulse is V2 period of the Os- so no phase difference occurs, oscillator frequency. Square-wave generators in particular are in the process of being improved. The described arrangements are being improved known way particularly easy for the abbot continue to dadujeh that one instead of an oscilmation by changing an operating voltage to +5 lator phase shift of 90 or 45 ° to build the HF. To achieve a phase shift of 90 ° to modulators with an oscillator oscillation of reach, each subsequent pulse must then feed 0 ° phase shift and the required begin in the middle of the previous pulse. Phase shift of 90 ° by inserting

The described circuits, corresponding phase shift elements in the receiving

by making the oscillator transmit and / or receive 5 ° paths in front of the RF modulators. This applies so-

side with half the frequency (V2 the receiving frequency for oscillators with the same as well as with half

frequency or IF) and the HF modulator receive frequency. This phase shift

gates in a self-doubling construction, d. H. can e.g. B. can be achieved by the in

in such a circuit that the double Fre- A b b. 6 RF preamplifier stages against

frequency (eg if the straight receiving recom- detuned 5 ⁵ side +45 and -45 °, and the detuning

frequency) does not appear to the outside;

the circuitry of the modulator itself is compensated for or the like.

It is also possible to work in one of the HF branches, although the modulator or after the HF amplifiers mixes one capacitive at essentially the same level as if a normal ^6o- loaded tube were inserted (Fig . 7), the so switched modulator with the oscillator frequency is the same that the total capacitance of the anode (switching capa reception frequency. When mixing, e.g. zität + fixed capacitance or variable capacitor), in an oscillator frequency of 3.5 MHz an impedance designated with an illustration 3, reception frequency of 7.01 MHz, so must the GR for the reception frequency of such size sentlichen a branch signal frequency of 10 kHz corresponds ⁶ S has, that a gain is by one. Thus, while the frequency of 7.0 MHz is only very weak outside the phase shift with the greatest approximation of 90 ° modulator, the internal resistance of the tube must and must. The phase shift of the oscillator oscillation ohmic or choke resistance in the anode

19 20

Voltage supply must be much larger than the ristics to be inserted because it eliminates the impedance of the capacitance. Otherwise harmonic can be generated again,
instead of capacitive also an inductive load. The described arrangements are selected, in the form of a coil, which is placed directly in the anode line by a self-doubling HF modulator, with one of the capacitive f A b b. 8. The charging capacitor 7, the impedance equivalent to a load for HF. The advantage of having a very small resistance is that on a charging part of this arrangement, the phase shift of an oscillator half-wave is maintained at a change in voltage that is approximately 0.71 of the peak value of the tuning. The diode does not open significantly changed, it only changes during the period in which the oscillator amplitude, in a straight line with the frequency, io half-wave exceeds this blocking voltage, so that is only slightly in the case of narrow tuning ranges. Va half wave = ¹ U period of the oscillator frequency. To compensate for this, the amplification of this diode is made permeable for a whole half-wave of the stage or the capacitance load or the inductive reception oscillation, so that the arrangement load is variable and thus mixes in the same way as a normal mixer arrangement at the same time an average, the signal amplitudes in both 15 voltage with an oscillator frequency equal to the Emp branches so that they are matched at the catch frequency. The reverse voltage (= charging voltage) composition cancels the inverse language completely. of 0.71 of the peak value is achieved without external voltage gain control in the DC voltage source, since the ratio of amplifiers would require considerably more effort to change the resistor of the diode to the discharge resistor 8. If you tune through larger areas * or about 1:16 to 1:20 (depending on the diode's will, you can degenerate the capacitance or inductance, also results in a slightly higher reverse voltage in neither switching nor in synchronism with the some cases better effect). When higher detuning change. charging resistors are required, are added to the

The described arrangements are improved.

gen in that when using an ordinary 25 speaking size. The received oscillation lies

borrowed oscillator and doubling modulators in series with the oscillator oscillation, they can also

the oscillator voltages are fed into a common oscillator at the base of the charging capacitor

lato'rausgang be taken from the very low. The place of the received oscillation can be with

is ohmic, namely the internal resistance of the oscillator oscillation should be swapped

The oscillator can be much smaller than the inner 30 den, and it does not matter at which point the

resistance of the connected modulator. This connects the circuit to ground, provided that this is the case

it is avoided that the mixed products of the one are taken care of, that the HF is not short-circuited.

Branch into the other branch. This can e.g. B. by an HF choke in the LF output

Low-resistance oscillator outputs can occur through passage. The NF, with more precise frequency and

known circuits can be achieved, e.g. B. also a DC voltage through 35 phase correspondence,

Cathode followers or their cascade connections. can be removed from the charging capacitor.

It should be noted that the purely ohmic resistance is also the above-mentioned ratio of 1:16

The value of the common oscillator output small is calculated as follows: The one in the charging capacitor 7

compared to the ohmic internal resistance of the incoming current I ₀ is generated by the over the

should be closed HF modulator, because otherwise 4 ° reverse voltage lying voltage peak 0.29 U ₀ . (U ₀

a coupling of the branch signals occurs. Except- is the idle oscillator peak amplitude.) The arith-

The metic mean value of the dome is 0.6 · 0.29 · U _n , see above

contained therein, because otherwise mixed products, which are that during a period T in the charging

fall on these resonance points, are raised. _{capacitor 7} ^ ß ^ amount of electricity I ₀ ■ L er

The arrangements 45 & a 4 described are improved

furthermore by the fact that when using Forgives to

doping modulators in all stages before the 0.6 x 0.29 UT

RF modulators advertising counter couplings inserted ~ '->

the, z. B. non-bridged cathode resistors, the & d ⁴

do not reduce the gain too much. As a result, 50 where R _{0 is} the effective forward resistance of the diode

it is achieved that there is also a very strong incident, not plus internal resistance of the oscillator. The during

intended for reception, but pre-amplified for a period T out of the charging capacitor 7-

Transmitters hitting the RF modulators is not an own flowing amount of electricity

Form harmonics and with the HF modulators \ j _c 0.71 U

can deliver. This purpose is served by 55 Ι _Ε · Τ = ~~ r ~ 'T - ~ · T,

also the HF resonant circuits themselves. When using ■ .. -He ^ e
Diode modulators only result in combination, where I _{E is} the discharge current, U _{c is} the charging voltage, from negative feedback with the resonant circuit and R _{E is} the discharge resistor 8. Adequate freedom from harmonics through equal selection. For setting both expressions we get R _E = 16 · R ₀ . higher demands should even be band filters instead of 60. Since the period is no longer available, we recommend the simpler resonance circuits. The mentioned circuit independent of the frequency.
Otherwise there is no negative feedback in HF amplifiers. It is now useful to switch two such customary, but here it contributes to an essential order in push-pull. Your discharge resistors 7 increase the immunity to interference. The reduction of the are either both according to ground as in Fig. 8, amplification (HF) is meaningless, because they are usually too high, or they are too high without a ground connection across the why with the usual levels. Placed between charging capacitors, as pos. 9 in Fig. 9, resonant circuit or band filter and HF modulator should 10 and 11, whereby the same limited compensation of the then no further stage with non-linear character charges is achieved because the charging blocks 10 and

21 22

11 yes charged with different polarities the difference between peak value and blocking voltage. In this case the series connection of the diodes merges. This results in a very good one processing of the discharge resistors to a single double interference immunity.

pelter size (pos. 9). In order to make the circuit more highly resistive, comparative and modulation voltages can now be used, as already mentioned, diode series resistors in the middle of the bridge or discharge resistors. In the case of the push-pull circuit it is a status 9 (see Fig. 9), be it by tapping a great advantage, a common for both diodes or a potentiometer or, if you use the series resistor, with the same size, DC voltage component is not required, can be done by everyone because it works alternately for the diodes (Fig. 11). . Charging capacitor 10 and 11 such a large capacitor. This reduces the noise of the diodes, ports 12 and 13 are connected to the common output, the diode characteristics and the charging voltages are so that all the desired frequencies are passed through and the harmonics are matched, ie that the impedance of this oscillator oscillation is reduced even more.
Capacitors 12, 13 (both calculated in parallel, because the effect of these diode modulators and the

they act in the same direction) in comparison to the circuitry built up from them is essentially understood the connected further circuit improves small by using diodes with as much as possible should be. Also with this circuit and all wide ideal, i.e. straight, characteristic and low Either the oscillator oscillation or the forward resistance can ren, thereby reducing the noise and Reception oscillation or both in the base points the harmonic formation.

of the charging block (see Fig. 11). ao It is now possible that in such a Then, however, before or after the coupling-out diode push-pull modulator circuit through Unlungskondensatoren 12, 13 RF chokes or a similar structure or other influences are elek resistance that the RF from connected Irish asymmetries result. Their harmful we-filter keeps away (see Fig. 11). If chokes in front of the kungen can be eliminated by lying across capacitors, they can both together 25 over the charging capacitors 10, 11 a large Kapaau | a core can be wound. The two concavity 14 switches, the asymmetrical fluctuating capacitors 12 and 13 should be as equal as possible, which compensates for the charging voltages. This is especially important in the case of strong inequalities, otherwise the oscillator fluctuations could be important in circuits with discharge resistors. Both methods based on mass, because asymmetries are more pronounced. You can then even use the low-pass filters at the same time: for telegraphy from the middle, place the discharge resistors 8, which then serve as the central point of the bridge resistor 9, the direct current filter terminating resistor (parallel value; similar impulses and for telephony via the capacitance see Fig . 13). Very large transverse capacitances 14 result in factors 12 and 13 (see Fig. 12). In this case, the stabilization of the oscillator oscillation output blocks can also be significantly smaller because they do not transfer the amplitude of the oscillator, because the change thereof does not transfer the transfer of low telegraph frequencies and requires the capacitance 14 during the recommendations. With the third method in which the previous output signals are not influenced,
As a guide, however, the deep frequencies are also improved. Those described above are improved

sequences used. Arrangements by the fact that instead of a common

; The mode of operation of the push-pull circuit in the series resistor to each of the diodes is its own. Vorsen Single-ended / push-pull doubling modulators is resistance 15, 16 (see Fig. 14) and -that the following: these series resistors to oppositely equal

<One half-wave of the oscillator oscillation charges oscillator _{voltages, in particular to a counter r} the capacitor 10, the other half-wave is applied to the contact oscillator output 17, between the capacitor 11. The discharge current of both capacitors 45 whose center tap and the base point of the charging gates flows together via the bridge resistor 9, capacitors 10, II the received oscillation one to which a stable zero point is fed in in the middle. The connection point with ground can be. Between the opening time of one diode and here too at any point in the circuit the opening time of the other can be set in opposite directions. The advantageous effect of this diode is an equally long time in which both circuit changes are based on the following processes: Diodes are blocked. From an incoming recipient. _,. ,. ,. , ","..,; ■■. ■

base oscillation are therefore z. B. the positive ^a ) ψ ¹ f ^{hr st} ™ \ incident jammers: half-waves can pass, the negative ones blocked. There-,. ^ Rch unequal diode characteristics one

caused by the charging capacitors 10, 11 detector effect occur so that the modula-

Receiving voltages of the same polarity, which are in full 55 I ¹ . ^{011 the} jammer becomes audible. The height at the bridge's zero point or between the above- this »detector disturbance« is independent "of the

Carrying capacitors 12, 13 appear. Since the ^Abs j ^{and m} F receive frequency, as long as the Stpr-

Diodes are connected in push-pull, the ^{transmitter is still in} the preamplification area;

Harmonic of the oscillator oscillation. These _. b) Strong jammers in addition to the reception frequency ■ However, the mix is not clear. But the Fre- 60 can result in undesirable mixed products, sequences, the same superimpositions as the reception including those with a frequency in the

capture frequencies can result are very far from, near the oscillator frequency, as well as with a

and-their effect is for the most part offset within the frequency of the difference between reception halves the mixer itself. Such a Mo frequency and strong jammer frequency. These

dulatorc mixes with twice the amount of mixed products that can be added at the tuned oscillator frequency, without the noticeable lator oscillating circuit or its decoupling module

arises. The entire range or at RF chokes with resonance points acts as the dynamic range

Peak value of the oscillator amplitude, i.e. not only cause phase-dependent voltage drop,

23 24

the one mixed with the oscillator frequency in the number of diodes the overall characteristic of the one

LF or DC voltage range, chip conduction direction better the overall characteristic

tion results and so again the modulation of the other forward direction can be adjusted

the jammer makes audible. The size of this can. At the same time, the now common

"Mixed interference" increases with the proximity of the interfering series resistance of the diodes, the noise voltage

transmitter to the reception frequency and can vary considerably depending on. In addition, the circuit is insensitive

Phase position in the interaction of the two against asymmetries of the coupling winding or

Branches numerous maxima and minima in the diode series resistors, because the result

Form the vicinity of the receiving frequency. caused voltage changes.

lo pens. Here, too, both reception branches can

Both disturbances can be caused by exactly the same from a single oscillator coupling winding 17

Diodes can be eliminated, but it is better to use them.

Written push-pull circuit according to Fig. 14, because the transmission facilities are being improved

This is the mixed disorder, which is much stronger than that according to the third method in that the described

Detector fault, diode modulators in the push-pull output winding 15 also in the transmitter.

17 of the oscillator circuit itself compensated. are set. To this end, the previous

An additional advantage of the circuit is that the NF-Mod.output the transmitter-NF (branch signal span

that harmonics of the oscillator oscillation are not supplied in voltages), while the oscillator input

the receiving circle because it remains unchanged at the zero (Fig. 17). At the base of the

points of the bridge circuit, which on the one hand consists of 20 charging blocks 10, 11 or at any other point in the

the winding 17, on the other hand, from the series connection line of the oscillator oscillation then arises

direction of the diodes, their series resistors 15, 16 and the double sideband of the folded branch signal NF,

the loading blocks 10, 11 is formed. A practical one but with the suppressed carrier (center frequency)

The exemplary embodiment has the following individual part values: in the amount of the doubled oscillator frequency. This

Pos. 15, 16 each 2kOhm; Pos. 10, 11 each 3.3 nF; Pos 9 25 modulator or mixer works like this here too,

39 kOhm + 39 kOhm + pot. 1 kOhm; Oscillator - as if twice the oscillator frequency is effective

voltage 2 X 10 V peak value. would be without this in the absence of NF modulation in

The second branch of the receiver will appear expediently: the diodes leave without AF

from the same oscillator coupling winding 17 only those exceeding 0.71 of the oscillator amplitude

feeds (if from branch to branch there is no phase-30 peaks of the oscillator oscillation through which

shifted oscillator voltages are desired), cancel each other out. Depending on the polarity of the

where the diodes, which are connected to a common end of the th AF instantaneous voltage, this DC-

Winding 17 go in opposite directions, so weight disturbed so that either one or the other

that during both half-waves of the oscillator oscillation, the other phase of the doubled oscillator oscillation

tion current flows, i.e. no direct current is generated. 35 predominates. Even with this arrangement, the

For small signal processing it is necessary that the qualities of the modulation and the carrier suppression Diode series resistors 15 and 16 low-noise type are improved by common repetition because their noise is at this switching status of the diodes. The NF can either be in the device does not cancel (as it is supplied in the middle of the discharge resistors 8 described above Single-ended / push-pull modulator was the case). 40 (Fig. 17) or as with the receiving circuits

In all of these circuits with diodes and capacitors and an HF filter chain (e.g. Loading capacity can also change the order of the. Fig. 18). According to the Third Method are Diodes and charging blocks are swapped. This is. now two such modulators are arranged in the transmitter, particularly favorable in the present case the opposite, namely to suppress the inverse clock / push-pull circuit, because you can use it to reach the frequencies that are the base points of the charging disconnects Diode series resistors 15, 16 as potentio blocks 10, 11 on a common decoupling coil meter and thus can easily adjust or a decoupling oscillating circuit connected, like it (see Fig. 15). Fig. 17 shows. There stand out according to the

The previously described arrangement, selected phase shifts, either the stone build-up, is improved in that each individual charging capacitor 50 lowers or the decreasing frequency spectra. is charged in push-pull (Fig. 16, counter- The common output, in Fig. 17 that is an example clock / double push-pull circuit). For this purpose, wise the resonant circuit should be for the oscillator to oscillate on each of the charging capacitors 10 and 11 supply low resistance, it is doping the already existing diodes 18 and 21 pelte oscillator frequency matched. The two another diode each with the same forward direction 55 double sideband outputs (the folded NF) can be 20 and 19. These additional diodes are crossed but also put together via separate steps wisely with the connection points of prejudice. In the same way as Fig. 17 can stood 15, 16 and existing diode 18, 21 of the an- also the circuits according to A b b. 9 with 16 set up Charging blocks 10, 11 connected. Therefore, the tet are, so that all of these types of modulators for Series resistors can now be used again for two diodes each 60 transmitter purposes, i.e. folded transmitters together, and its value is to be doubled. to get the correct discharge voltage of 0.7 the band from the EF connector.

The oscillator amplitude. These modulator circuits are improved at the same time.

it comes out when instead the value of the Ent through that instead of the diodes transistors are used

charging resistance 9 (= 8 + 8) should be reduced by half (22, 23 in Fig. 19), and accordingly

is rigt. the different forward direction of the diodes with

Such an arrangement reduces the different types of conduction (pnp and npn). Included

Detector and mixing fault, because because of the larger collectors are with the previous one

25 26

Diode resistor 15, the emitter with the respective charging capacitor 10 and 11, which are sensitive to magnetic interference, etc., and the base connections of the filter are located at a less sensitive point of the Verüber each a series resistor 24 and 25 with the oscil-strengthening path, although the HF modulator voltage connected to the on which the associated receive voltages were not increased,
common series resistor 15 is located. The transmission levels described for the base connections have values such that, when each of the low-pass filters is split into two cores by the base (LC filter) when the transistor is conducting, the transmission levels described above (Fig. 21) provide a sufficient current flows in order to make the line KoI to the two charging capacitors 10, 11 in each lektor / emitter very low resistance. Are connected in the non-branch. The inductors each conductive state of the transistor ^; is as a result of the io filter element are wound on a common ring or then present blocking the line base / emitter square-core, on opposite sides also the resistance of the line collector / emitter lowing, so that an from the outside on the core is very high. The same effect occurs as the magnetic interference field in diodes with the (iron core), only with the difference that the two sides of the iron core create a rectified resistance of these "transistor diodes" very much power flow. This induced in both wicks is lower than with normal diodes. This will ■ - payments equal ripple voltages that reaches in that the noise of the diodes respect almost comparable pick up on the filter output when the waning and that the passband much the windings entgenau sense of direction on both sides is the same, because inequality of Lower - runs in the opposite direction, as shown in Fig. 21. There is also a compensation of the larger common series resistance at the same time not included in the pre-magnetization, which fall due to the current flow. This further reduces the detector interference and from the charging blocks 10, 11 to the discharge resistors, the mixing interference. In addition, the 8 would arise. To short circuit the at the ends of the choke windings, the sensitivity to harmonic wave formation decreases constant "switching" (rapid transition from the filter terminating resistor 29, which is used for the high-resistance to the low-resistance state), each of which ensures a proper transmission curve. Insofar as the positive and negative cut-out a further reduction of the hum half-waves of the recorded transmitter oscillations 30 voltage as a result of the action of a magnetic field desirably have the same content, i.e. there is no direct current component, the input can be given by a further division. In this way, all circuits can load resistors 8 in the resistors 30, 31, 32, 33 according to claim 8 with 13 from diodes to transistor - a circuit according to A b b. 22, in which the ren are converted. to the right of the connections of the very large condenser. The described circuits are improved by the circuit part located in the sator 34 (including the fact that the known mixing potentiometer part) is brought to a uniform hum potential through this capacitor 34 with field effect transistors on the RF modulators (Fig. 20). This is in a simple manner which, in turn, is only possible with the aid of the potentiometer 30 if equal-frequency mixing can be adjusted to zero. The capacitor (oscillator frequency = receiving frequency) applies, 40 34 can, for. B. be an electrolytic capacitor, which in turn, if you have strong shields incorrectly polarized and so large that you want to avoid the hum, the voltage mentioned in claim 1 does not lead to a significant voltage drop on it superheat circuit. The field effect transistor generates. One of the iron cores of the LC filter (FET) is switched in such a way that the ripple voltage touching its gate electrode is generated in both cores and the receiving oscillation can be directed in opposite directions, but does not have to be of the same magnitude here, advantageously a common one IF preamplifier. If this ripple voltage ratio use the circuit for both branches, because the mixed wires cannot get into the gate circuit by changing the potentiometer 30, i.e. the resistance ratio of 33 to the left part of 30 cannot be transferred from one branch to the other. is made equal, the electrolytic capacitor 34 and thus the
corresponding to the desired operating point, the insensitivity is combined with a high preload. The oscillator interference arrives at the drain-electrode LC filters (multi-element) against hum electrode via a resistor 26 because the iron cores, in particular oscillation, which can be supplied in particular from a ring shell core, of each filter in the winding axis oscillator . From the mixture 55 are placed directly on top of one another (or only with a short distance between the received oscillation and the oscillator oscillation), but the low-frequency branch signal voltage is created alternately by 180 °, rotates and is not magnetically coupled to one another via an HF choke and a filter capacitance 27 (see Fig. 23). This ensures that the outer can be removed. If the direct-voltage magnetic fields, which the inductances uniformly voltage component are not required, the capacitor 28 is inserted in both windings, which generate the voltages to be passed, which have a low resistance in relation to the frequencies. Cancel filter output if you have the same inductive The advantage of this type of circuit is that it uses activities. The filter capacitances do not cause any mixed products from one branch to the other, because they can exceed their size, since the 65 on the ring oscillator are also designed for the upper limit frequency B. are separated by a step. In addition to telephony) as the upper limit frequency of the filter, the resistor 26 is amplified, so that the technically somewhat more difficult to achieve solution.

27 28

Solution would also be the use of what is known per se, namely through DC voltage amplifiers.

th toroidal core chokes (as filter elements between the ker or through a low frequency amplifier with extremely deep

Capacities), which are so evenly along the ring lower limit frequency or by an amplification

are wrapped so that hum interference is not grained by the third method,

retire. 5 _; . _r

The described arrangements are improved. The sometimes disruptive effect of self-reception for telephony and amplitude-keyed telegraphy due to the fact that the reception frequency is the same or doubled by the fact that instead of the DC voltage amplifier, the oscillator frequency pelts with straight-ahead reception as a branch signal amplifier between the filter and LF- .. is alleviated because this triggered modulators now LF amplifiers with low lower than lower DC voltage shift no longer throughrer limit frequency, ie high transmission time con- ■ .. · comes,:. .; ..:;.,:. _; \ _T ; ;;,.;, η.: · stante, to be inserted and with an upper limit- ν
frequency according to the third method, f) _au ch b _emi sending a reachable in the same manner from the bandwidth of the folded LF central gap itself by results between NF and transmission range. The lower limit 15 HF modulator elements with a corresponding frequency can be _{inserted, for example, 100 or 20 Hz or 1 or:} lower limit frequency, - ~ s 0.1 Hz or even less, depending on how .. ■■ .. -...., -....; ■ · '.— ■■; large one the resulting twice as large _{} the} transmitter can now also work with the telephone! ^ in the ^ gap m in the middle of the HF and LF transmission range, so do * roll without high mixing area. Such an Mxttellucke disturbs * ° ^ HF frequency band. That is why the Senbei cannot transmit telephony at all, because it can now be made very narrow, even if required, directly _{in the TranWiver operation.} The telephony, from the oscillator of the straight-ahead probability that em ^ naturally generated sound _{receivers are} controlled, with which this gap already falls, is approximately zero. in the case of telegraphy (to claim 1) mentioned at the frequency mentioned in the introduction with 25 advantages ■ - ·. · ■■
This narrow incision arises in the reception area
at exactly 1500 Hz of the voice frequency band.

'yellow with telegraphy affects a narrow medium. B. 0.05 Hz not disturbing. Theoretically, this means that for telegraphy a branch signal would be used with an exact match of 3 ° stronger with an actually much too high lower transmission and reception frequency, the signals in the - <■ cutoff frequency, which still disappears the middle gap, but in practice the edges of the telegraphic characters, i.e. the highest low-frequency signal frequencies that are transmitted to the transmitter oscillations with each use of the characters, have a different phase position, so that the filter did not produce the fundamental frequencies (see Fig. 24). Come into dig mark changing polarity for 35 its output is a magnetic or elektrodie time constant of the low-frequency signal amplifier branch _overall: (. For example, Pos 35) African relay which is high on the cient. The construction of such branch signal flank of the telegraphic sign at the beginning of which an amplifier speaks with an extremely low lower limit frequency and actuates mechanical contacts or is known from oscillograph technology. Charging of switching diodes or switching transistors or field effect of the CÄ transmission elements can be prevented in particular by strong negative feedback (Fig. 25), which switch on the branch signal amplifier when a certain signal voltage is exceeded, e.g. B. by Umeinsetzt. The advantages of the described measures circuit of the resistances of the coupling elements, as can apply: in Fig. 24, or even by switching on

45 DC voltage gain. This switchover

a) expensive DC voltage amplifiers are omitted, ^remains > as long as the symbol lasts, and only becomes

repealed when the sign is no longer valid

b) the low-pass filter can also set a lower limit - ^the relay drops out or switches off. These "signal frequency (bandpass) can thus effects instead controlled time constant" that charges iron core chokes have now phototransistors Reaktanzröhren or 5 "CAE coupling members or Nullpunktsabweichun- that un- to magnetic fields 8 ^en g ^erin S remain because they are sensitive in the pauses between drawing, balance again and again ...;

The high time constant or the DC voltage

c) A strong suppression of the amplification on the transmitter side can also have an oscillator or oscillation frequency for each branch separately (which can be switched as 55, in that the branch signals themselves actuate relays (one for each branch) of the carrier in the middle of the RF transmission range, because depending on expresses) is no longer necessary, because this phase position of the characters can often only allow a carrier to fall into the central gap in one branch, ■ impulse occurs. .; .. ·: .. ,, ^ ?. _f i .v vv V

The transmission facilities are being improved

d) With telephony, the middle gap with the carrier can 60 through various lower limit frequencies for teIegerrest for the transmission of information telephony and telegraphy. This is achieved through. Umnen, for tuning display, for automatic switching of one or more C7? coupling elements Follow-up to the automatic volume per branch (see Fig. 26) by turning on for telephony control, for diversity switching or for further leakage resistor 36 is switched on, the Telegraphic transmission. This information etc. 65 not only reduces the time constant and the means can either with the telephony in the same gap enlarged, but also the amplification ver-receiving path amplified and only then reduced separately, because the noise in telephony as a result or already in the filters separately and amplified the larger bandwidth increases. In the case of telegraphy

29 30

against an additional capacitance 37 is switched on, which a) In the cycle of the reading frequency is simultaneously 4T

The time constant remains high, as does the gain, and 44 decreases, while 43 and 48 remain the same.

but through the capacity the upper limit remains or is increased, or vice versa,

quenz and thus the noise is reduced

both for telephony through the capacities of the 5 b) In the cycle of the reading frequency is for the duration Anodes were determined by mass. the one half-wave 43 is reduced, while 47

Now this switchover can also be left unchanged or increased without switching, or

if one or more of the CA- reversed, and for the duration of the other half-

Coupling links according to Fig. 27 forms. Here is ^: wave 44 is reduced, while 48 is the same

the time constant of the transmission for slow parts remains or is increased, or vice versa,
grafie determined by 38 and 39, while for the

DC-like characters the resistor 40 In branch 2 the same is applied to the corresponding

remains ineffective. The resistors are made for telephony frequencies, but with 90 ° phases Capacities 41 and 42 as a voltage divider (different. Since all anodes are reduced in thickness in parallel) and determine the upper 15 tet, the effects of this Ver cutoff frequency add up in connection with the internal resistance changes, while the branch signal frequencies stood the pre-tube. For telegraphy the results are suppressed when the resistors are paired upper limit frequency from the iüC member 40, 42. Which are the same (balance mixture). The added and Resistor 40 also derives the grid currents, it is due to the composition of the inverse Frefür Telephony frequencies greater than the apparent resistance output voltage is available at the booth of 41 so that he does not share the voltage division available anode connection. if the significantly impaired. In the case of telephony, the tube systems cannot be exactly the same, they can be in Excessive gain in the vicinity of the central gap can be adjusted in a known manner. The change through an increased lower limit frequency of the filter borrowed or switchable resistors must be in a be rendered harmless. Dimensioning in such a known construction be made, play: Pos. 38 10OnF, Pos. 39 2MOhm, Pos. 40 that the control voltage (= reading frequency) in the 3Oo £ ohm, Pos. 41 2.2 nF, Pos. 42 1OnF, anode-switched line paths no significant interference resistance the 1st tube 80 kOhm, upper limit voltages generated, because these would otherwise be audible, frequency for telephony around 1500 Hz, for telegraphy e.g. as a 1500 Hz tone. Now, however, can also be a about 50 Hz. 30 branch signal amplifiers with single ended output used

The insensitivity of the scarf will be improved when the balance mixture is achieved against magnetic stray field disturbances. that in the circuit part of the RF modulators, 43 and 50 would say that not all anode par filters and the branch signal amplifier input stages are all connected, but only one anode each the zero lines are laid twice, namely 35 of one branch with an anode of the other on both sides of the branch leading in each case LF current and a cathode of one branch with a Head and laid close to this. Fig. 28 shows the cathode of the other branch (Fig. 30), and that as an example an i? C link in this design. Also from these connection points the NF through Kon lines, which only carry operating voltages, capacitors can be removed and connected to a common be treated in this way when it is compounded to disturbance 40 output. But you can also supply tension. Due to the above-mentioned design, each individual tube has its own anode or it is achieved that external magnetic interfering exchange cathode resistance switch (Fig. 31), then has fields, including those from an iron chassis - so a total of four AF outputs that you can get with four sheet metal, in which capacitors merge through these neutral lines. Same circuits Loops 45 formed with the current-carrying conductor result in the same with transistors or FETs co-rotating voltages induce the conduction type. The branch signals result for themselves cancel each other out in the live conductor, and that the anode and cathode resistances are opposite Even the magnitude of these tensions due to the tensions cancel each other out. The mixed products wrestling area of the loops kept small but add up according to the third method, will. 50 So that the voltages to be put together are the same

As the transmission equipment is improved in size, the gain at each of the also has to be third method, in that every outputs to be combined are the same, the AnZweig of the receiver the output voltage of a barren and cathode resistors are thus Ent-push-pull branch signal amplifier to dimension a NF-Balance-speaking.

A further circuit possibility is shown in Fig. 32, double triode and four resistors also exist with branch signal amplifiers with single-ended output (A b b. 29). Instead of the double triode, gang. You connect an anode of each transistor or FET to be used here. The four branches with an anode of the other branch and resistors form two voltage dividers 47, 43 and places a counter-48, 44 and 49, 45 and 59, 46 between the two connections, on their divider 6 ° clock transformer, whose center tap with the score the grids are connected. The anode voltage source can now be connected. Here, too, either four resistors per branch or only the branch signals are raised as a result of the balance, two each as a switch or variable resistors. B. as switching transistors, as well as one of the superimposed desistors, FETs, mechanical choppers, optoelectronic voice frequency bands running in opposite directions,
nically variable photoresistors and they in fol- Instead of switch resistors can generally

In the same way, continuously variable resistances were used through an applied control voltage Change the form of the reading frequency: those that are not switched by the reading form, but rather

31 32

are controlled sinusoidally in their resistance value during the transition from conductive to non-conductive

the. This results in a better freedom from harmonics. State to be rendered harmless,

The fine adjustment of the branch signal amplitudes is made, the primary-side winding halves with each

as described earlier, bridged by changing the one capacitor (see Fig. 34). This

Amplification is carried out in the HF part or by means of 5 capacitors is dimensioned in such a way that with rectangular

opposite change of the unbridged Kato-shaped chopping of the branch signal voltages

the resistances according to the example in Fig. 32. When the switches 43, 44 are closed, the respective contact

A fairly simple and advantageous solution to the grounding capacitor in connection with the series resistor is obtained if one only changes the resistances 43 with 46 acting internal resistance of the last branch, so that any interference voltages can easily be caused by a slow signal amplifier stage (= i? C element) can flow off according to mass (e.g. interferences charging a rounding of the rising edge the reading frequency oscillation). The modulation of the switched branch signal causes and that at These switches 43, 44, 45 and 46 are made within the opening of the switches 43, 44, the falling edge of the of a branch with 180 ° and from branch to branch with switched branch signal by briefly further 90 ° Phase shift. This applies to A b b. 29 and 15 current flow from the capacitor into the the following. Transformer can advantageously be flattened as switch resistors. . M. also the recently industrially manufactured optoelectronic The present arrangement is also available as NF-Modutronic Coupling elements are used, useful at lator for transmitter purposes, namely the which a photo resistor encapsulated by a light for folding certain NF of the previous source (Lamp or radiation diode) illuminated 20 towards the secondary side and which is together. If no interference voltages arise, folded NF can be the center tap of the previous primary one such an arrangement is taken immediately after the filters page.

With the help of the circuits described, the NF-Mo make dulation for both transmission and reception purposes, so that branch signal amplifiers, the secondary windings can now coincide and the further gain can be switched to the NF part 25, as A b b. 34 shows. Here lies is being relocated. the two geschal- the connection point in series * $ Venn used as the switch resistors FETs ended secondary windings on the movable Konwerden, the following options are available: clocking a potentiometer at the ends of the

added voltage of both windings prevails.

A. Boost Type FETs with Gate Threshold 30 This allows the magnitude of the secondary voltage to be: No source bias, switching voltages of both branches can be changed in opposite directions impulses must make FET conductive. and they to. Composition exactly the same too

do. The potentiometer also fulfills

B. FETs of the choke type: a) Source or Hch the function of a branch selector switch with the Gate blocking voltage, switching pulses must FET 35 each one of the branches for test purposes other than conducting make, b) no reverse voltages, drift can be set by switching the potentio pulse make FET non-conductive. meter twisted as far as it will go.

It should be noted that instead of a push-pull transformer

The transmission facilities are being improved. also two single-ended transformers in the corresponding circuit, in that 40 parts can be used in each branch for low-frequency modulation. The branch and composition of a push-pull transformer signals can also be used according to A b b. 35 is used together (see Fig. 33), its primary mean-setting. The non-bridged potentiometer in the tap of the last branch signal amplifier stage in the cathode is used to fine-tune the combined-single-ended feed and its primary winding setting by changing the opposite ends through variable resistors 43, 44 decoupling and thus the amplification,
alternating with the reading frequency, i.e. with 180 °. If FETs are used as switches, the phase difference applies.

exercise. As variable resistors, photo resistors, mechanical switches (choppers), span- 50 for receiving amplitude-keyed telegraphy, voltage-dependent resistors, field plates, transi- if particularly simple circuits are required can be used. FETs are used in which the control ends, because the single-ended branch signal amplifiers or switching pulses themselves do not cause any significant interference, only one series resistor (unstressed. With continuously variable. Changeable) 47 and one switching resistor 43, the resistors 43 and 44 can the type of control voltage described. The circuit can also be sinusoidal, so that the branch resistance will also be correspondingly reshaped in each branch with 90 ° phase signal voltages. difference sinusoidal or rectangular changed. The connections of the primary side can also be swapped from the one at the junction of 47 and 43: the center tap of the primary winding on the resulting frequency mixture is the telegraph ground, the ends of the switching resistors 43, 44 are connected to 60 branch signals (low frequencies) through a branch signal amplifier . Secondarily, the high-pass filter (here for example a jRC element 51, 52) modulation products are filtered out one after the other or, if desired, also added by connecting the secondary windings in parallel. In order to eliminate harmonics in switch operation, the harmonics as well as the interference voltage and the rectangular shape of the branch signal pulses from switching transistors are created through the rectangular chopping. The voltage-related parts are converted into an approximate sinusoidal shape here, for example, in a double conversion, but also in the form of short-term interference pulses, triode. .
How they are improved by switching transistors through the base charge the transmission facilities

according to the third method in that an astable multivibrator oscillating at double reading frequency (54 with 62 in the circuit example Fig. 37) supplies control pulses with which two bistable multivibrators (67 with 70 and 75 with 86) are switched alternately, which are at half the reading frequency work because switching can only be done by pulses of one polarity, in the circuit example by negative pulses. Each switching step of outputs 1 and 2 therefore begins in the middle between the beginning and the end of the previous switching step. The exact center can be set with the potentiometer 54. The potentiometer 53 regulates the frequency by changing the base voltage. 63, 64 and 71 with 74 transmit the pulses, 87 with 90 are the base resistors of the switching transistors in the LF modulators. The order of the start of the switching step is therefore la, 2 a, Iß 2β or rotated by 180 ° (other reading direction) la, 2ß, Iß, 2 a. The read frequencies in both branches therefore have exactly 90 ° phase difference, regardless of the frequency, because the pulse or switching step length ratios do not change.

An on / off switch can be inserted in order to always achieve an oscillation in the same reading direction be that one emitter line of the astable multivibrator at the same time with one emitter line each bistable ^ switches multivibrators on or off. There is a capacitance in parallel with this switch, so that there is always the same oscillation in the same reading direction and there are temporal differences do not have any effect during the contact closure process of the switch. As a dimensioning example for the in A b b. 37 specified circuit is given:

Pos./Value 72 Pos./Value 53 IA: 73 OA 72 54 5A 74 OA 72 55 1OA 75 OA 72 56 10A; 76 50 p 57 20 « 77 50 p 58 20 « 78 50 p 59 1.5 * 79 50 p 60 2708 80 1OA 61 2 N 708 81 1OA 62 1.5 A 82 1OA 63 50 p 83 1OA 64 50 p 84 2N708 65 1OA 85 2 W 708 66 1OA 86 2iV708 67 1.5 A 87 2-08 68 1.5 A 88 12 A 69 1.5 A 89 12 A 70 1.5 A 90 12 A 71 OA 72 12 A

The arrangements described are improved in that as a generator for the generation four ring-shaped connected univibrators of known construction serve for the reading frequency. Any univibrator only vibrates on an impulse, carries out an oscillation and then retains its position of rest until the next trigger, after having triggered the next univibrator. A once Any impulse that has taken place moves continuously in a ring through the four univibrators. The circuit will be like this dimensioned so that the rotational frequency of a work process is equal to the desired reading frequency. Each univibrator supplies a switching power to one of the four associated switch resistors in the AF modulators (see Fig. 38) according to the same scheme as described in the previous claim, thus with a 30 ° phase shift from branch to branch.

This circuit is simpler than the previous one, but the duration of the individual work processes or switching ^{steps is only 1} A period of the read frequency, so the signal conversion efficiency is somewhat lower. Instead of the univibrators, the well-known glow lamp circuits can be used in the manner of the "rotating point of light" (Funkschau, 1960, issue 18, title: "Glow tube oscillators", p. 460) or corresponding four-layer diode circuits.

In the circuits mentioned, the frequency can be changed with the operating voltage without the switching step length ratios change. This means that the exact phase shift always remains obtain.

The ring generator is improved especially for telegraph reception, if a simple construction is required is by using a per se known glow lamp or four-layer diode circuit (Funkschau, 1960, issue 18, title: "Glimmröhren-Oszillatoren", p. 460), in which three glow lamps alternate ignite and extinguish. To get two read frequencies shifted by 90 ° from such a circuit

(e.g. for an arrangement according to Fig. 36), resistors 101,102 or transformers are first placed in the base points of glow lamps 91 and 93 (see Fig. 39), from which the control voltage for the two LF modulator branches can be removed. If the glow lamps 91, 92, 93 and the series resistors 97, 98, 99 and the capacitors 94, 95, 96 (which can also be connected in star) are each the same, a "point of light" is created, which is switched on at regular intervals from the glow lamp Glow lamp jumps. This is due to the fact that a glow lamp which reaches the ignition voltage by charging the capacitors via the resistors triggers a strong extinguishing pulse due to the potential drop during ignition which reaches all other glow lamps via the capacitors. The duration of the operation of a glow lamp is Ve of one period. Now, according to the invention, the series resistor 98 of that glow lamp 92, the base point of which does not emit a control voltage, is reduced to half, so that this glow lamp burns for twice as long as each of the other two or for exactly as long as the other two together (A b b. 40) . At the resulting fundamental waves according to A b b. 40 you can see the 90 ° phase shift.

Although the harmonic content of these square-wave switching pulses ( starting from 101 and 102 ) is high, this does not matter, at least in the case of telegraphy. On the contrary, a slightly colored tone is desirable here because it does not tire. By regulating the operating voltage (for example with 100) , the reading frequency can be changed without changing anything in the pulse length ratio, i.e. also in the phase shift. A frequency excitation over larger areas can be done by switching over the capacitors 94, 95, 96 . With this circuit, the sequence of ignition, i.e. also the reading direction, is determined by the

Pos./Value 97 Pos./Value 91 Glimml. 98 IN THE 92 Glimml. 99 500 k 93 Glimml. 100 IN THE 94 In 101 IN THE 95 In 102 10k 96 In 10 k

35 36

differ in the ignition voltages determined. For Tele the phase of the received oscillation in the input circuit graphics with narrow bandwidths, the reading direction is reversed and thus all phase positions are in but meaningless. Dimensioning example for the branch signal amplifier. The switching time itself, Fig. 39: i.e. the transition time from a phase position to the

5 others, should be shorter than the shortest telegraphic character to be transmitted, so that there is no interruption, especially when mechanical switching is used enters the reception. : ._ ■ · ..: ...; ■ -... ■ -

This measure ensures that the ίο central gap disappears in the reception spectrum; even with the most precise coordination and relatively small time constant of the transmission elements In the branch signal amplifier (this can then be regulated, the transmission equipment can be improved), no charging of the coupling can be done the third method by the fact that more than NF members are created. This phase changer can generator for a harmonic-free mixture as possible either work continuously, or it can through the Sinus generator is used, whose principle telegraphic characters are triggered by themselves and only like that (Fig. 41) is known per se. It consists of two long works when a character lasts. It is too constant amplitude phase shifters of 90 ° each by coupling with a tuning display device and a feedback stage with 180 ° phase shifting possible to insert the phase changer only when The main advantage of this arrangement is that the oscillator oscillation approaches zero, thereby enabling it to switch when the difference between receive from the cathodes or anodes of the first two, the two occurring zero points are graded four sinusoidal voltages of arbitrary poles can be avoided.

The same arrangement can also be used for telephony shifts from level to level of a constant 90 °, as long as the polarity reversal frequency is below the level, if the phase shifter elements are the same and is within the audibility range and as long as the transition factor is not set too high times are so short that they cannot be heard.
(Potentiometer in the 180 ° coupling stage). The polarity reversal can also only be done in the HF amplifier

Fig. 42 shows a table executed circuit, but here 30 or when using the superhet principle in the IF - only with control voltages for two variable parts, but only at points for which the resistances in the AF modulators. A frequency shielding of the oscillator still a sufficiently small change can be achieved with these circuits, oscillator radiation guaranteed,
by improving the capacitances or resistances of the transmission facilities

Phase shifter can be changed in synchronism. At 35 with phase changer in that not the Empden Phase shifter elements can either be the catching oscillations, but rather the oscillator oscillation capacities or the resistances at the anode supply is changed in phase by 180 °. this or collectors. The latter version can be used in the oscillator of the mixer because there is a risk of wild oscillations (und) or in the oscillator for the HF-Mogen is smaller. 40 modulators, through the well-known capacity

Dimensioning example for Fig. 42: variation diodes or similar components. One can

make the polarity reversal by either very short and very strong detuning or long and not so strong for it. The latter method 45 offers greater advantages because it is easier without disturbance phenomena is to be realized. For example, one can use a well-known glow lamp multivibrator according to A b b. 45, whose glow lamps light up alternately at regular intervals. In the vicinity 50 one of the glow lamps you bring an electrode that is connected to the oscillator circuit and its Capacity is changed by mass by the glow cover. By more or less close approach the electrode is used to set the size of the effective detuning. To avoid the

A receiving device with low-frequency switching on the phase changer improves the detuning of the branch signal amplifier in that the phase position only goes in one direction, leaving one of the receiving oscillation to a series resistors at the operating voltage, so that tuned oscillator oscillation constantly by 180 ° a quiescent current is changed through the tuning used, namely with a frequency that flows 60 glow lamp. This is about half of the operating pulse current, which is less than the highest frequency to be transmitted, so that the oscillator declines (e.g. the telegraphic characters) and is greater than the lower mood when the phase changer is idle, approximately the cutoff frequency of the LF branch signal amplifier. This is done in the middle between the two states of detuning appropriately with a mechanical or is (because the capacity of the glow path current-dependent electronic pole reversal switch (e.g. relay) 140 in 65 gig). It should be noted that an off-circuit example in Fig. 43, 44, the effect reaching the antenna (avoidance of coupling charges by reversing the polarity of the coupling winding) can also be achieved if the phase shift switches to input circuit 141 in such a way that each time does not is exactly 180 °, but z. Am-

Pos./Value 113 Pos./Value 103 150 k 114 2N708 104 1.5 k 115 100 η 105 150 k 116 100 η 106 1.5 k 117 100 η 107 150 k 118 change 108 5k 119 change 109 10 k 120 1.5 k 110 10 k 121 1.5 k 111 2 N 708 1.5 k 112 2 N 708

as a result of the constantly changing ionization conditions in the glow tube fluctuates over a wide range.

In the case of the short-term but strong detuning, the oscillator frequency is over the transmission range (HF) also changed, e.g. B. with a telegraphy bandwidth of + 20 Hz by +1 kHz. at In the long-lasting but weak detuning, the oscillator frequency is only within the transmission range changed, e.g. B. with a telegraph bandwidth of + 20Hz only by + 5Hz. The total bandwidth On the HF side, it only increases from 40 Hz to 50 Hz.

The transmitting and receiving devices are improved according to the third method by the possibility of to be able to work with frequency shift keying. To do this, the transmitter is keyed symmetrically around the imaginary HF center frequency (which is also emitted to a greater or lesser extent for tuning purposes can be). For example, a character step through a transmission frequency of 1000 Hz shown above the HF center frequency, a separation step by a transmission frequency 1000 Hz below the RF center frequency. The receiver is tuned to the RF center frequency with its oscillator (in Superheterodyne switch to the corresponding IF), so that in the branch signal amplifiers both when writing as in the case of the separation step, the same tone, 1000 Hz in the example mentioned, is produced. That tone always has a phase difference of 90 ° in both branches, but the sign of this phase difference is it determines whether the transmit frequency is above or below the RF center frequency. With others In other words: If, for example, the transmission frequency is above the center frequency, the 1000 Hz oscillation runs in one branch that in the other branch by 90 °, if it is below the center frequency, the 1000 Hz oscillation in one branch in front of that in the other branch.

According to the invention, a phase shifter (see Fig. 46) is inserted after each branch signal amplifier, which splits the audio signal in each branch into two "lines" α and b with a 90 ° phase shift. This phase shift has the same sign in both branches, so you can use the same phase shifters in an identical arrangement in both branches. Now, "lines" that do not correspond to one another are connected via a working resistor or another working arrangement A and B , that is, α with b and b with a. Depending on the sign of the phase difference of the branch signal tones, the double phase shift now neutralizes the tone frequencies in one working arrangement, while they add up in the other. The known arrangements can be used as phase shifter, e.g. B. J? C links according to Fig. 47, which cause a + 45 ° and - 45 ° shift, or tubes with a purely capacitive load according to A b b. 49 (corresponding to claim 5), with one of the "lines" going out directly from the branch signal amplifier.

Work orders can be used that come into action when both of you Input voltages have the same phase relationship with respect to ground or those that are in action occur when their two input voltages are in opposite phase with respect to ground. A working arrangement of the first kind is shown, for example, in Fig. 48. Here the two lead each other inappropriate lines to the two grids of a double triode. If the phasing to the Grid is opposite, the voltages at the output transformer cancel each other out. When the phase positions are equal in terms of mass at the grids, the effects add up. A work arrangement the second type shows, for example, A b b. 49. Here the effects of the audio frequencies stand out Grid voltages occur when their phase position on the grid is the same with respect to ground. The effects add up if the phase position on the grids has a difference of 180 °.

Instead of transformers in the working arrangements described, you can also use known Way AC relays can be used.

The audio frequency alternating voltages coming from the secondary windings of the transformers at A and B can now also be rectified, either with respect to ground to voltages of the same polarity according to both working arrangements or to positive voltage according to one working arrangement and negative voltage to the other. These tensions can then in a manner known per se either separate character step branches and separation

_{Feed a5} step branches or differential circuits. As is well known, the latter have the effect that the effects produced at the same time when broadband disturbances occur in both work arrangements A and B do not trigger any drawing or separation steps, but rather cancel each other out. A magnetic differential circuit of this type is in the output stage according to A b b. 49 shows an electrically operating differential circuit in the output stage of the circuit according to Fig. 50. With the latter there is no effect if the grid voltages have the same polarity and the same size, because the power flow in the relay is then canceled. If grid voltages with opposite polarity are not to have any effects, then the anodes must be connected in parallel and a single-ended transformer must be placed in the anode line.

If the frequency above the center frequency and the frequency below the center frequency are keyed separately on the transmitter side, separate signals also result at the working arrangements A and B. In this way, two channels are obtained which are amplitude-controlled and act independently of one another, because the superimposed stress conditions arising at the working arrangements A and B do not interfere with one another.

The phase shifters can also be made variable, so that setting options for any unbalanced frequency swings are also given.

At the transmitter end, the keying of the frequency is expediently effected in that correspondingly different Audio frequencies are fed into the NF part. At an AF center frequency of 1500Hz For example, emissions of 1000 Hz above and below the HF center frequency, when tones of 500 and 2500 Hz are fed into the NF part.

Shift keying is even easier if, for example, one is continuously in the AF modulators the 1000 Hz oscillation generated (by the already mentioned feed of e.g. 500 Hz) and the Branch connections to the AF modulators swapped in tactile rhythm. Any other type of Keying in which the phase relationships are reversed

39 40

is useful, e.g. B. Exchanging the input power grows steadily (not suddenly)

connections to the ring modulators, etc. speaking of a steadily increasing detuning of

The main advantages of frequency shift keying after 0 Hz up to the amount for which the phase shifter

The third method are the following: is dimensioned.

5 Now one can increase the amplification of this

. _ ·,. . . , _TT,. ^,,: Mood also used difference frequencies through

a) On the transmitter side, no high-frequency means are required for keying _{the telephony branch signal amplifiers themselves. Let the} oscillator meQ, if this is always carried out with a lower limit frequency that is sufficiently lower than the HF center frequency. Then it must be true. The keying takes place z. B. by a _{10 but after} these branch signal amplifiers and LF pole change relays. take out the difference frequencies from the branch signal frequencies before the AF modulators,

b) The transmitter center frequency can be in any z. B. by crossovers, because they would otherwise be broadcast at TeIe-strength and for the automatic Nach- foniespektrum as a sound, z. B. with 1500 Hz, 'audible mood or for additional news. The telephony branch frequencies, that is, ha. Transmission are used. mentioned example the frequencies are above 10 Hz

the NF-Modulatofen, the frequencies below 10 Hz the

^: c) Changes to the frequency deviation can be applied to the sender-keyed part used for tuning (the

and the receiving end by simple niederfre- ^NaCN switching only a few items to other

constant measures take place. On the transmitter side: An ²⁰ values [the phase shifters must then for 90 ° at

^: change of the fed-in tone. At the receiving end: the higher audio frequencies of the frequency shift keying

Readjusting the output phase shifter and being dimensioned] unchanged, for the part

the AF low-pass filter width. graphic frequency shift keying can be used).

; Another option is to use the

j> _, ■ ■,. _. ,. .. _{> T} "25 retuning, the difference frequencies used correspond to

. d) There are no transient processes at NF- _{neither immediately} ^S _{after the filters} or even before the

_; : Oscillating circles because there are no such _{oscillating Ffltem to be separated and si with or without their own}

" _T circles are available. The characters use occurs _{Tiefpaßfflterj oh} * _{s essential} tliche gain equal

. delay. _{to the} phase shifters and work arrangements

30 lead, but not to rectify them according to these,

¹ The reception arrangements are improved for but rather to be assigned after each work arrangement.

Telephony by setting up a with almost arbitrary and only then with or without rectification

Biger accuracy working voting display, on the corresponding known display or

to switch the retuning devices that are also used for automatic retuning. Same method

can be det. For this purpose, the transmitter emits 35 can also be used for retuning when

who apply the carrier in the middle of the spectrum (i.e. the frequency shift keying mode. Here,

HF center frequency) in full strength or as a carrier, a common branch signal amplifier is useful

rest off. On the receiving side, this carrier falls within the range for the keying signals and for the difference frequency

Middle gap (branch signal amplifier with a lower zen used, but separate phase shifter and

Cutoff frequency, for example 10 Hz), is therefore not 40 working arrangements. These are dimensioned so

audible. Now then branches off to the low-pass filter that the already described with the frequency shift keying

(or bandpass filters for very low frequencies) in benen phase relationships and not corresponding

each branch an additional branch signal amplifier compositions at the desired difference

äb for the frequencies that are effective within the center gap frequency.

lie, so in the example mentioned, for frequencies 45 when receiving amplitude-keyed telegraphy

below 10 Hz. If the transmitter carrier frequency deviates, the telegraphic characters can "even be used for tuning

frequency of the (doubled) oscillator frequency can be used. One branches for the

(e.g. by 5 Hz), this difference frequency is dimensioned in frequency deviations (difference frequency)

the additional branch signal amplifiers always 90 ° ned frequency shift keying arrangements directly from the

Have a phase difference, as in the case of the Fre- 5 ° branch signal amplifiers off, so does not need any

frequency shift keying with positive or negative forward crossovers. Although the incoming parts

characters, depending on the upset to high or graphic signals a constantly from character to character

goes to low frequencies. If you can now have the changing phase position, it speaks

Outputs of the additional branch signal amplifiers which always have the same work arrangement for each character.

for the differential frequency dimensioned phase 55 (if detuned in one direction).
Slide and work arrangements switch, according to the circuits in frequency shift keying,

so the Ar application examples responsible for the drawing steps appear

Work orders in effect in the event of disgruntlement "___ _ ,,, _. _{/ Λ} 1 1 «\

in one direction, which is necessary for the separation steps 60 I-SSB-Telefome-Transceiver (A b b. 51)
responsible work orders in the event of disgruntlement

in the other direction. In the example mentioned the input part of the receiver consists of one

So if there is a 5 Hz detuning, a display or HF preamplifier stage will be displayed. The frequency of the HF ring

a retuning device triggered. Since the phase oscillator is equal to the receive and transmit fre-

slide valve and work arrangements without oscillation 65 frequency. Both the HF and the NF modulators

working circuits, the circuits can down to ren and the filters can be in both throughput

almost any small detunings can be operated. The branch signaling

will. The stronger that arises in the work arrangements is switched off when sending.

41 42

2. SSB telephony and telegraphy receiver with an ^ ⁰ * ¹ "} ^eight ' ^{so that} differences in the branch connection for transmitter readjustment (Fig. 52) can be compensated for

The output of the power amplifier has a noise fade. the

In the antenna there is a phase changer with one of the two switches according to the 10 ^ F coupling capacitance alternating frequency of about 15 Hz. The potentiometer 5 would serve to put the branches out of operation The input oscillating circuit is used to regulate the volume individually or together, namely when transmitting, when circulating. The first system of the entrance tube is to connect the reception areas and for testing purposes, death follower switched, the second system as 90 ° - the oscillator oscillates at half the receiving

Phase shifter. In the anode of this system are frequency. In the feedback line before the the switchable capacitors, which is a switch socket for each band io grid of the oscillator tube, give a gain of about one. In the If this with the help of a plug the voltage Cathodes of the phase stage and the RF amplifier of a frequency decade od. Ä. Is supplied, switches there are negative feedback resistances, which the harmonics are the oscillator oscillation by interruption Reduce generation of strong signals. Still -. ■ the feedback, and the oscillator stage acts there is still a sufficient reserve of gain. 15 as an OF amplifier. In addition, the sockets, Those at the anodes of the RF amplifier tubes via between those of the switch socket interrupting capacitors connected glow lamp circuit breaker, a quartz must be plugged in, the zen over the following doubling modulators in front of the oscillator to be oscillated in a known manner high voltages. The doubling modulators stabilize themselves in frequency over a pulling range are equipped with low-noise diodes. ao sated. The 8 pF trimmer is used in conjunction with

The low-pass filters are switchable. The LC filter for the 50 pF block in the oscillating state for telephony has its cut-off frequency at 1200 Hz, setting a weak feedback factor, the .RC telegraph filter at 20 Hz. Nevertheless, this so that the lowest possible harmonics arise. Around .RC filter is only three-part, results in connec-. Amplitude fluctuations of the oscillator oscillation To avoid using the following branch signal amplifiers with 25, the screen grid voltage must then be used the anode capacitance of the first branch signal amplifier of the oscillator tube (here by kerstufe as the fourth ÄC-member already at 500 Hz from the stabilizer). Part of the oscillator voltage stood a weakening of Vsooo. The branch signal becomes a buffer stage to supply the transmitter Amplifiers are supplied with stabilized operating voltages. Their cathode resistance is only one gen fed. Between i. and 2nd stage switches 30 part are bridged, adjustable with a PoE inserted, in telegraphy the upper limit frequency tentiometer so that when you touch the increase in Reduce the branch signal amplifier to 20 Hz and the grid capacitance is compensated for by the capacitance Telephony the amplification to about Vs min- imity-reducing effect of the negative feedback of the to the. ■. '' '..' .. ■ Potentiometer part above the movable tap.

In the following AF modulator, as a switch 35, a completely detuning-free keying is achieved Field effect transistors with operation in the initial range or transmission / reception switchover for telephony Ohmic, none. Rectifier effect) is sufficient. :,

see. They are directly from the branch signal amplifiers ¹ -

Proverb 36 and Fig. 37 fed. The secondary windings take the signals for frequency shift keying, the LF modulator transformers are 40. Here, too, the transmitter from the receiver oscilloscope is not directly connected, but rather controlled by two converters. The keying takes place in the Sen grid of a double triode, so that the. The reading direction is reversed by adding the currents controlled thereby. On the pole changer (not shown in the circuit diagram) in the cathodes is a potentiometer which changes the negative feedback leads to the switching transistors (FETs) of the two tube systems in opposite directions. ■,

For this purpose 4 sheets of drawings

Claims (53)

Patent claims: 1. Single sideband transmission device according to the third method, characterized in that that on the receiving side the high-frequency superhet part only with a small one, that Received signal carried out through the noise voltages of the RF modulators increasing amplification, but an AF amplifier with a very large gain factor is used or between Filters and LF modulators in each branch a DC voltage amplifier is placed, which the Sinale raises over the possible noise and interference voltages of the NF modulators, and that such a low-scatter oscillator is used that the input of the RF modulators The resulting oscillator voltage only has a branch signal voltage component even with volume control which is small compared to the signals to be recorded or due to zero point shift can be compensated (Fig. 3a). 2. Transmission device according to claim 1, characterized in that instead of a superhet high-frequency part a straight amplifier with a small gain factor is used and that the oscillator and the oscillator oscillation leading lines through a particularly effective shielding of a known type at the interspersion on the circuit parts is prevented in front of the HF modulators (Fig. 3b). 3. Single sideband transmission device according to the third method, characterized in that that when using a receiver according to claim 2, the transmitter, in particular in transceiver mode, built in straight-line switching and without frequency conversions from the receiver oscillator can be controlled. 4. Transmission device according to claim 1 with 3, characterized in that transmission and On the receiving side, instead of oscillators with subsequent phase shifters, there are now HF and LF ring oscillators or ring generators are used, their phase shifts between the individual ring members when voting remain constant, and that the oscillation or pulse voltages at the points of the ring oscillator or ring generator that have a 90 ° phase difference (Fig. 4). 5. Transmission device according to the preceding claims, characterized in that the oscillator or RF ring oscillator / generator oscillates on the transmit side and / or on the receive side with half the frequency required by the previous claims, that the RF modulators are designed in self-doubling construction and that the Phase shift of the oscillator frequency in relation to both branches and thus also the phase difference of the ring oscillator / generator outputs is only 45 ^p or odd multiples thereof (A b b. 5). 6. Transmission device according to the preceding claims, characterized in that that in front of the HF modulators each have a buffer stage or instead of a common HF preamplifier stage an RF preamplifier stage is used each and that these stages in such a, on known construction are carried out that the outgoing from the RF modulator of one branch Mixed products cannot pass into the other branch (Fig. 6). 7. Transmission device according to the preceding claims, characterized in that that an RF oscillator with non-phase-shifted voltages is used and that the phase shift of 90 ° required for the HF modulators by inserting a 90 ° - Phase shifter is achieved in the path of the received signal before the RF modulators, the Phase shifter in particular from a purely capacitively or purely inductively loaded tube in one of the signal branches exists, and that the load capacitance or the load inductance or the gain of this tube can be made variable so that it can be used for compositional control after the AF modulators (Fig. 7). 8. Transmission device according to the preceding claims, characterized in that that when using a single oscillator and doubling modulators the oscillator voltages for the two branches can be taken from a common but very low-resistance output of the oscillator. 9. Transmission device according to the preceding claims, characterized in that that in the cathode lines of the two RF amplifier stages and the phase stage before the RF modulators Negative feedback resistors are inserted and that the RF circuits of the RF amplifier be placed immediately in front of the RF modulators. 10. Transmission device according to the preceding claims, characterized in that that the oscillator oscillation in series or in parallel with the received oscillation on a Rectifier diode with charging capacitor is conducted, which means that the opening time is halved an oscillator half-wave is set so that the discharge resistance is about 16 times greater than that Resistance in the diode pass circuit, so that there is a frequency-independent at the charging capacitor DC charging voltage of about 0.71 of the oscillator amplitude peak value results in (A b b. 8). 11. Transmission device according to claim 10, characterized in that two such arrangements are in push-pull mode, that is to say opposite one another with diodes Arranged forward direction, but fed in common mode by the oscillator oscillation the diodes have a common series resistor and the LF output voltage is either taken from the connection point of the two discharge resistors that is not connected to ground, or from the connection point of two capacitors, the other ends of which are connected to the charging capacitors lie (Fig. 9, 10, 11, 12). 12. Transmission device according to the preceding claims, characterized in that that the charging capacitors of the doubling modulators by a cross capacitor higher Capacity can be bridged. 13. Transmission device according to claim 11 and 12, characterized in that each of the diodes connected to the charging capacitors is on Place of the common series resistor receives its own series resistor and on the opposite side the same oscillator voltages is applied, in particular from a single symmetrical inductive coupling winding with center tap (Fig. 14, 15). 14. Transmission device according to claim 13, characterized in that each charging capacitor an additional diode is connected with the same forward direction as the already existing and that the other end of these new diodes each with the connection point of the series resistor and the old diode of the other charging capacitor, whereby the discharge resistances (= bridge resistance) should be reduced by half (Fig. 16). 15. Transmission device according to claim 10 with 14, characterized in that for use As a transmitter RF modulator at the point of the LF output, the LF source (branch signal frequency) of the transmitter and an amplifier stage at the point of the received oscillation input or an oscillating circuit for the resulting double sidebands is connected and that accordingly the third method has two such modulators connected together with their outputs so that the undesired frequencies cancel each other out (Figs. 17 and 18). 16. Transmission device according to claim 10 with 15, characterized in that instead of the Diodes transistors of various conductivity types are used, whose collectors with the common series resistor, its emitter with the respective charging capacitor and its base connections are each connected to the oscillator voltage source via a series resistor (Fig. 19). 17. Transmission device according to claim 1 with 8, in particular in superheterodyne circuit Claim 1 and following, characterized in that a Field effect transistor is used, at whose gate electrode the received oscillation and the same-frequency oscillator oscillation is connected to its drain electrode via a resistor and that the amplified NFr branch signal voltage at the junction of the Resistance removed with the drain electrode and via a high-frequency choke or a screen resistor and a coupling capacitance is fed to the filters (A b b. 20). 18. Transmission device according to claim 11 with 16, characterized in that to each Charging capacitor an LC low-pass filter is connected, its inductors per element are wound on a common ring iron core, but in such a way that the hum in scatter generate opposite voltages on the iron core in the windings and become the premagnetization cancels and that in addition large capacitors from one wire to the other that short-circuit the ripple voltage (A b b. 21). 19. Transmission device according to claim 19, characterized in that parallel to one Part of the bridge resistance is a large capacitance capacitor, between its ends the tap for the bridge output is located, and that this capacitor is shifted the connection points at the bridge resistor are adjusted to zero in their hum potential can (A b b. 22). 20. Transmission device according to claim 1 with 17 with single-core, but multi-element filters, characterized in that the iron cores of each link are opposite to the previous one, but are stored close to it so that external magnetic interference fields move the cores in the same direction enforce, but induce opposite voltages, or that inductances each The link itself can be designed as a toroidal core throttle in a manner known per se (Fig. 23). 21. Transmission device according to the preceding claims, characterized in that that an LF amplifier is used instead of the DC voltage amplifier in each branch, with a lower cutoff frequency equal to half the width of the desired central gap is. 22. Transmission device according to claim 21, characterized in that by the lower limit frequency of the LF branch signal amplifier given the center gap the full amplitude or a remainder of the transmitter carrier frequency (= transmitter RF center frequency) is transmitted, which is amplified in the receiver in the same or in a separate reception path and for voting display, for automatic volume control, for automatic retuning, for diversity switching or is used to transmit information. 23. Transmission device for amplitude-keyed telegraphy according to claim 21 and 22, characterized in that the branch signal amplifier with a much too high lower limit frequency be carried out as they are for the transmission of the edges of the telegraphic character, but not sufficient for its lower frequencies, but that in the end part of the amplification path a mechanical or electronic relay is located, which is already through the steep rise Edge of the telegraphic sign is actuated and thereby additional capacitors or additional resistors or other known means to the transmission links switched so that a very deep lower limit frequency of the branch signal amplifier or any DC voltage amplification for the duration of the telegraphic character is switched on (Fig. 24). 24. Transmission device according to the preceding claims, characterized in that that the switch from telephony to telegraphy in the branch signal amplifier by switching from an anode damping resistor to an anode sieve capacitor, the Anode filter capacitor to the upper limit frequency in telegraphy, the damping resistance is dimensioned for the reduced gain in telephony (A b b. 26). 25. Transmission device according to the preceding claims, characterized in that a CRC element is located in the path of the branch signal amplifier , which at frequencies below the un- The lowest telephony branch signal frequency is fully transparent, while it is at higher than telegraphy branch signal frequencies causes a voltage division that roughly corresponds to the noise ratio of telegraphy and telephony (A b b. 27). 26. Transmission device according to the preceding claims, characterized in that that in the LF currents or LF voltages leading circuit part before the first branch signal amplifier stages the neutral lines are laid twice, on both sides closely along the low-frequency voltages and low-frequency currents leading lines and also along such operating current leading or other lines, absorb the stray magnetic fields and feed them into the input section of the branch signal amplifier can (A b b. 28). 27. Transmission device according to the preceding claims, characterized in that that in each branch the push-pull outputs of a branch signal amplifier each via a resistor with the grids of a double triode (or two equivalent transistors or FETs) and the The grid of the double triodes are connected to ground via a resistor each and all »5 Anodes work in parallel on a common external resistance, those on the grids Lying resistors as controllable, low-interference voltage Resistors or switching elements of a known type are designed so that the clock Reading frequency (90 ° difference from branch to branch) either a switching resistor at the same time to the branch signal amplifier and one to ground or alternately (with 180 ° phase difference) both switching resistors to ground or both switching resistors to the branch signal amplifier changed (A b b. 29). 28. Transmission device according to claim 27, characterized in that in each branch a branch signal amplifier with single-ended output to the parallel-connected inputs of the relevant LF modulator according to claim 27 is switched on, its parallel-connected Outputs in each branch in a triode system from a non-bridged cathode resistor, in the case of the other triode system, an anode resistance of the same size and gain removed (A b b. 30 and 31). 29. Transmission device according to claim 27, characterized in that in each branch the single-ended output of a branch signal amplifier at the two ends of the one on the grids Resistors is connected that each have an anode in a branch with an anode of the other branch is connected and that between these two connections a push-pull transformer connected (A b b. 32). 30. Transmission device according to the preceding claims, characterized in that that only the voltage divider resistors between the grid and ground are in front of the double triodes are designed as variable switching resistors and that field effect transistors are used, which work in the initial (switch) area and whose gate electrodes the Switch opening and closing pulses in the form of square-wave pulses or sinusoidal voltages shifted 180 ° with respect to the grids of a tube and 90 ° with respect to the grids of one branch can be fed to the grids of the other branch. 31. Transmission device according to the preceding claims, characterized in that that photoresistors are used as variable resistors, their lighting in Clock of the control voltages of an LF read generator is changed. 32. Transmission device according to claim 1 with 26, characterized in that in each Branch of the single-ended output of a branch signal amplifier with the primary center tap of a push-pull transformer is connected, the primary winding ends of which can be changed mechanically or electrically by the reading frequency Resistance or electronic switch to ground and its secondary winding with the secondary winding of the push-pull transformer in the other branch either in parallel or is connected in series, and that the mechanically or electrically variable resistors or the electronic switches per branch alternately, i.e. with a phase difference of 180 ° in time with the waveform of the reading frequency and with a 90 ° phase difference from branch to branch changed or switched (A b b. 33, 34). 33. Transmission device according to claim 32, characterized in that parallel to the both winding halves of each primary winding a capacitance is placed and dimensioned in such a way that that in switch mode the chopped branch signal voltages approximated as closely as possible to a sinusoidal curve and that interference voltage peaks resulting from the reading frequency are weakened (A b b. 34). 34. Transmission device according to claim 32 and 33, characterized in that for use As a NF modulator in the transmitter, the NF intended for folding is the previous secondary windings connected in parallel or in series and the folded NF required in the two subsequent branches to the center tap the previous primary winding in each branch is taken (A b b. 33 and 34). 35. Transmission device according to the preceding claims, characterized in that that when the secondary windings of the push-pull transformers are connected in series Connections are at the center tap of a potentiometer, one end of which with the Total winding start and the other end is connected to the total winding end (Fig. 33). 36. Transmission device according to the preceding claims, characterized in that that each secondary winding is grounded on one side, while the other end with one each Grid of a double triode is connected, between whose cathodes a potentiometer for opposing directions Negative feedback change is and their anodes are connected in parallel and above an output transformer or a resistor is connected to the operating voltage source are (Fig. 35). 37. Transmission device for telegraphy according to the preceding claims, characterized characterized in that as a NF modulator according to the Single-ended branch signal amplifiers in each branch only a series resistor with a switch resistor (with switching frequencies of 90 ° phase difference from branch to branch) is used, at the junction of which a high-pass filter element is connected, which is dimensioned in such a way that it does not let through the telegraphic frequencies coming from the branch signal amplifier , probably. but, the. _{audio frequencies created by the NF T} modulation (Fig. 36)., ._ ..;. 38. Transmission device according to the preceding claims, characterized in that that. an LF ring generator, consisting of two bistable. Multivibrators, for. Generation of Square pulses are used, which last half a reading frequency period, and that the use of the next impulse in the middle between the beginning and the end of the previous one Impulse is achieved by a control multivibrator that oscillates at double the reading frequency and is coupled by a push-pull output to the two bistable multivibrators in such a way that these are made to tilt alternately (Fig. 37). 39. Transmission device according to claim 1 as with 37, characterized in that as an LF ring generator known univibrators 'or glow flip-flop circuits or four-layer diode flip-flop circuits can be used with a period of time. of the single square pulse yon a quarter period of the reading frequency, and .that these univibrators and flip-flops in an are connected in a known manner so that only one of these components sends a control pulse which at the same time triggers the next univibrator (Fig. 38). 40. Transmission device according to the preceding claims, characterized in j that as a LF ring generator a known flip-flop with three alternately igniting and extinguishing glow lamps with the same coupling capacities in delta or star connection is used, but in which the burning time of one of the glow lamps is twice the burning time each of the other glow lamps is brought by this one glow lamp with the half the series resistor that each of the other two has, and that the control voltage for the AF modulators of both branches from base point resistors or transformers of the two other glow lamps with the higher series resistances (Fig. 39, 40). 41; Transmission device according to claim 1 with 37, characterized in that two known 90 ° phase shifter as an NF ring generator with frequency-independent amplitude and feedback via a phase inversion stage are used - and that the control voltage for the two LF modulators from the two 90 ° steps are removed (A b b. 41 and 42). 42. Transmission device according to the preceding claims, characterized in that that a mechanical or electrical pole reverser is inserted between the antenna and the input circuit that changes the phase position of an incoming received oscillation by 180 ° with a frequency that is less than the highest branch signal LF to be passed, but greater than the lower limit frequency of the branch signal amplifier, and with a switching time that is short compared to the duration of a polarity (A b b. 43 and 44). 43. Transmission device according to claim 1 with 41, characterized in that a variable inductance or capacitance is connected to the frequency-determining resonant circuit of the oscillator, the value of which is changed in a known manner, namely with a frequency which lies between the upper and lower limit frequency of the branch signal amplifier, and .that the detuning is either large and short or small but long, such that after each detuning process the phase of the oscillator oscillation has rotated by about 180 ° or an odd multiple thereof. : ■■■■■■. yj 44. Transmission device according to claim 43, characterized in that the periodic Detuning of the oscillator oscillation uses two glow lamps in a multivibrator circuit be, where one of the glow paths serves as a variable capacitance, but as long as the Phase changer is not switched on, is biased with a quiescent current (A b b. 45). 45. Transmission device according to the preceding claims, characterized in that that on the transmitter side a frequency shift is carried out by being symmetrical to an imaginary or weakly transmitted HF center frequency, the transmission of character and separator steps takes place that on the receiving side the oscillator according to the third method to the RF center frequency is tuned so that for the drawing and separating steps in the branch signal amplifiers same tone frequencies with a 90 ° phase shift alternating between plus and minus result between the branches and that after the branch signal amplifiers by known, in each branch 90 ^ phase shifters in the same direction per branch two lines are created and that each line of one branch with the unmatched line of the other branch to a work arrangement is connected and that the one work arrangement the drawing steps, the other provides the separation steps (A b b. 46 and 47). 46. Transmission device according to claim 45, characterized in that a working arrangement is used, the character or Separation steps then delivers when both line voltages have the same phase position with respect to Have mass, and that for this purpose a double triode, for example, is used as a working attachment at whose grid the lines lead and in their parallel-connected anode lines a transformer or a relay or some other working resistance is connected (A b b. 48). 47. Transmission device according to claim 45, characterized in that a working arrangement is used, the character or Separation steps then provides when the line voltages are opposite for this working arrangement Have phase relation with respect to mass, and that as a working arrangement, for example Transformer is used or a double triode, on whose grid the lines lead and 309 542/372 their anodes to the outer ends of a push-pull transformer or a push-pull relay winding lead whose center tap is supplied with the anode voltage (Fig. 49). 48. Transmission device according to claim 46 and 47, characterized in that the of vibrations removed from transformers or load resistors (symbols and Separation step frequencies = difference frequency between transmitter RF center frequency and symbol and Separation step emission frequency) can be rectified to voltages that are determined by both work arrangements have the same or opposite polarity and in such a differential circuit further processing that does not lead to a drawing or separating step if both Working arrangements respond simultaneously and approximately in the same strength, and that this differential circuit in particular is that rectified working voltages of the same polarity the grid of a double triode with the anodes in push-pull (with relay in between) or opposite polarity the grids of a double triode with anodes connected in parallel and relays in the anode lead (Fig. 50). »49. Transmission device according to the previous ones Claims, characterized in that, in the case of telephony, a carrier residue is broadcast on the transmitter side and in the receiving circuit with a center gap after the filters or in front of them an additional one Branch signal amplifier per branch with subsequent frequency shift keying parts according to claim 45 is branched off with 48, which in telephony on a response frequency within the Middle gap, i.e. below the lower limit frequency of the branch signal amplifiers for telephony, be dimensioned, and that the work step output to a known device is switched, which indicates or corrects a deviation in the vote on one side, and the separation step output to such a device for a deviation after other side. 50. Transmission device according to claim 49, characterized in that instead of an additional Branch signal amplifier in each branch of the branch signal amplifier for telephony with one lower limit frequency is executed, which is also used for the transmission of the actuation of the retuning indicator or working arrangements necessary frequencies, and that only after the Branch signal amplifiers or after some of the branch signal amplifiers, but in any case before the AF modulators the retuning frequencies from the telephony frequencies by known ones Crossovers are separated and processed further in the manner mentioned in claim 49. 51. Transmission device according to claim 49, characterized in that the for Re-tuning required difference frequencies immediately before or after the filters without substantial amplification of the frequency shift keys provided for the retuning (phase shifters with an unsuitable composition in work arrangements), but not rectified according to these, but are amplified so far that they display or retuning devices mentioned in claim 49 can operate. 52. Transmission device according to claim 45 with 48 (frequency shift keying), characterized in that that the transmitter emits a carrier residue and that in the receiver either the after Claim 49 with 51 mentioned arrangements are incorporated or that the branch signal amplifier also dimensioned for the amplification of the retuning difference frequencies and the retuning shift keying arrangements connected directly to the branch signal amplifier. 53. Transmission device according to the preceding claims, characterized in that that when receiving amplitude-keyed telegraphy, those occurring in the branch signal amplifier Branch signals themselves are used for re-tuning display or for tuning correction, by the frequency shifting parts dimensioned for the intended deviation (difference frequency) are fed directly from the branch signal amplifiers for the telegraph signals.