JP3394574B2 - Single-phase high power factor converter - Google Patents
Single-phase high power factor converterInfo
- Publication number
- JP3394574B2 JP3394574B2 JP31410593A JP31410593A JP3394574B2 JP 3394574 B2 JP3394574 B2 JP 3394574B2 JP 31410593 A JP31410593 A JP 31410593A JP 31410593 A JP31410593 A JP 31410593A JP 3394574 B2 JP3394574 B2 JP 3394574B2
- Authority
- JP
- Japan
- Prior art keywords
- diode
- switching element
- choke coil
- capacitor
- power factor
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Lifetime
Links
- 239000003990 capacitor Substances 0.000 claims description 46
- 238000009499 grossing Methods 0.000 claims description 12
- 238000010586 diagram Methods 0.000 description 8
- 230000007423 decrease Effects 0.000 description 1
- 238000007599 discharging Methods 0.000 description 1
Classifications
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Rectifiers (AREA)
- Dc-Dc Converters (AREA)
Description
【発明の詳細な説明】
【０００１】
【産業上の利用分野】本発明は交流電力を整流し力率を
改善して出力する単相高力率コンバータに関する。
【０００２】
【従来の技術】コンバータを使用して入力電流を正弦波
にする力率改善回路としては、図４に示す昇圧形コンバ
ータを主回路に採用したものが多い。この回路は簡単な
構成で、その入力電流を正弦波状にすることができる。
【０００３】
【発明が解決しようとする課題】図４の提案に係る昇圧
形コンバータでは、電流が流れている状態でスイッチン
グ素子ＴｒのＯＮ−ＯＦＦ動作を行うので、スイッチン
グ損失が多く、力率改善の制御動作がスムーズに行われ
ないと共に、スイッチング素子Ｔｒの動作寿命も比較的
短いという問題がある。
【０００４】本発明は、前述したようなこの種の力率改
善の現状に鑑みてなされたものであり、その目的はスイ
ッチング損失なしに力率改善の制御動作がスムーズに行
われ、動作寿命の延長も可能な力率改善形スイッチング
電源を提供することにある。
【０００５】
【課題を解決するための手段】前記目的を達成するため
に、本発明は単相交流電源Ｓの第１の整流出力端子ｔ１
と第２の整流出力端子ｔ２間に、昇圧用チョークコイル
Ｌｓ、出力ダイオードＤ、及び平滑用コンデンサＣｄの
直列接続回路が接続され、前記昇圧用チョークコイルＬ
ｓ及び出力ダイオードＤの接続点と前記第２の整流出力
端子ｔ２間に、第１スイッチング素子及び第２ダイオー
ドＤｃ２の直列接続回路と、第２スイッチング素子及び
第１ダイオードＤｃ１の直列接続回路とが互いに並列に
接続され、前記第１スイッチング素子及び前記第２ダイ
オードＤｃ２の接続点と、前記第２スイッチング素子及
び前記第１ダイオードＤｃ１の接続点との間に、共振用
コンデンサＣｒが接続され、前記平滑用コンデンサＣｄ
に並列に接続された負荷に、前記単相交流電源Ｓからの
電力が、力率が改善されて供給されるように構成されて
いることを特徴とするものである。
【０００６】
【作用】この構成によると、昇圧用チョークコイルＬｓ
に流れる電流がゼロで、共振用コンデンサＣｒに平滑コ
ンデンサ電圧Ｅｄが貯えられた状態で、第１スイッチン
グ素子と第２スイッチング素子とが同時にＯＮ状態にセ
ットされる。このように、第１スイッチング素子と第２
スイッチング素子とが、同時にＯＮ状態にセットされる
と、単相交流電源Ｓの電圧と前記共振用コンデンサＣｒ
の充電電圧Ｅｄとの和が昇圧用チョークコイルＬｓに印
加され、昇圧用チョークコイルＬｓと共振用コンデンサ
Ｃｒとが共振状態になって、共振用コンデンサＣｒが放
電する。
【０００７】共振用コンデンサＣｒの放電が終了し、充
電電圧がゼロになると、昇圧用チョークコイルＬｓに流
れる電流が、第１スイッチング素子−第２ダイオードＤ
ｃ２、第１ダイオードＤｃ１−第２スイッチング素子の
二つのルートで分流し、この間昇圧用チョークコイルＬ
ｓにはエネルギーが貯えられる。この状態で第１スイッ
チング素子及び第２スイッチング素子をＯＦＦ状態にセ
ットすると、昇圧用チョークコイルＬｓに流れる電流
が、第１ダイオードＤｃ１−共振用コンデンサＣｒ−第
２ダイオードＤｃ２を流れて、共振用コンデンサＣｒが
充電される。
【０００８】そして、共振用コンデンサＣｒが共振用コ
ンデンサ電圧Ｅｄに充電されると、昇圧用チョークコイ
ルＬｓに流れている電流が、負荷側に流れて序々に減少
し、やがて昇圧用チョークコイルＬｓに流れる電流がゼ
ロとなり動作は終了する。
【０００９】この動作で、昇圧用チョークコイルＬｓに
流れる電流は、非連続になるように制御されるので、第
１スイッチング素子と第２スイッチング素子がターンオ
ンする時は、第１スイッチング素子と第２スイッチング
素子の電流はゼロであり、スイッチング損失は発生しな
い。また、第１スイッチング素子と第２スイッチング素
子がターンオフする瞬間は、共振用コンデンサＣｒは完
全に放電しているので、各スイッチング素子の印加電圧
はゼロであり、スイッチング損失は発生しない。
【００１０】
【実施例】以下、本発明の一実施例を図１乃至図３を参
照して説明する。ここで、図１は本実施例の構成を示す
回路図、図２は本発明の各実施例を示す回路図で、
（ａ）〜（ｄ）は各モードでの動作を示す図、図３は本
実施例の電源入力電流の波形図である。
【００１１】図１に示すように、交流電源Ｓの電極端子
間に、フィルター用リアクトルＬｆとフィルター用コン
デンサＣｆとが直列に接続してあり、フィルター用リア
クトルＬｆ及びフィルター用コンデンサＣｆの接続点
と、整流出力端子ｔ１間にダイオード１が、フィルター
用コンデンサＣｆ及び交流電源Ｓの接続点と整流出力端
子ｔ１間にダイオード３が、それぞれカソードを整流出
力端子ｔ１側にして接続してある。また、コンデンサＣ
ｆ及び交流電源Ｓの接続点と、整流出力端子ｔ２間に、
ダイオード４がアノードを整流出力端子ｔ２側にして接
続してあり、フィルター用リアクトルＬｆ及びコンデン
サＣｆの接続点と、整流出力端子ｔ２間に、ダイオード
２がアノードを整流出力端子ｔ２側にして接続してあ
る。
【００１２】また、整流出力端子ｔ１に、昇圧用チョー
クコイルＬｓの一端が接続され、昇圧用チョークコイル
Ｌｓの他端には、第１スイッチング素子としてトランジ
スタＴｒ１のコレクタが接続され、トランジスタＴｒ１
のエミッタには、第２ダイオードＤｃ２のアノード側が
接続され、第２ダイオードＤｃ２のカソード側は整流出
力端子ｔ２に接続してある。また、昇圧用チョークコイ
ルＬｓ及びトランジスタＴｒ１の接続点に、第１ダイオ
ードＤｃ１のアノード側が接続され、第１ダイオードＤ
ｃ１のカソード側には、第２スイッチング素子としての
トランジスタＴｒ２のコレクタが接続され、トランジス
タＴｒ２のエミッタは整流出力端子ｔ２に接続されてい
る。
【００１３】そして、トランジスタＴｒ１及び第２ダイ
オードＤｃ２の接続点と、トランジスタＴｒ２及び第１
ダイオードＤｃ１の接続点間に、共振用コンデンサＣｒ
が接続され、トランジスタＴｒ１及び第１ダイオードＤ
ｃ１の接続点と、整流出力端子ｔ２間に出力ダイオード
Ｄと平滑コンデンサＣｄの直列接続回路が接続され、平
滑コンデンサＣｄに並列に負荷Ｌが接続されている。
【００１４】次に、このような構成の本実施例の動作を
説明する。
【００１５】単相交流電源Ｓからの整流回路への入力電
流Ｉｉｎの波形は、図３に示すように、非連続で正弦波
状に変化している。この入力電流Ｉｉｎは、フィルター
用リアクトルＬｆとフィルター用コンデンサＣｆによっ
て、高調波成分が吸収され完全な正弦波になる。以下各
モード時の動作を図２の回路に対応付けて説明する。
【００１６】昇圧用チョークコイルＬｓに流れる電流が
ゼロで、共振用コンデンサＣｒに平滑コンデンサ電圧Ｅ
ｄが貯えられた状態で、トランジスタＴｒ１とトランジ
スタＴｒ２とが同時にＯＮ状態にセットされる。このよ
うに、トランジスタＴｒ１とトランジスタＴｒ２とが、
同時にＯＮ状態にセットされると、単相交流電源Ｓの電
圧と前記共振用コンデンサＣｒの充電電圧Ｅｄとの和が
昇圧用チョークコイルＬｓに印加され、昇圧用チョーク
コイルＬｓと共振用コンデンサＣｒとが共振状態になっ
て、共振用コンデンサＣｒが放電する（図２（ａ）参
照）。
【００１７】そして、共振用コンデンサＣｒの放電が終
了し、充電電圧がゼロになると、昇圧用チョークコイル
Ｌｓに流れる電流が、トランジスタＴｒ１−第２ダイオ
ードＤｃ２、第１ダイオードＤｃ１−トランジスタＴｒ
２の二つのルートで分流し、この間昇圧用チョークコイ
ルＬｓにはエネルギーが貯えられる（図２（ｂ）参照)
。この状態でトランジスタＴｒ１及びトランジスタＴ
ｒ２をＯＦＦ状態にセットすると、昇圧用チョークコイ
ルＬｓに流れる電流が、第１ダイオードＤｃ１−コンデ
ンサＣｒ−第２ダイオードＤｃ２を流れて、共振用コン
デンサＣｒが充電される（図２（ｃ）参照）。
【００１８】そして、共振用コンデンサＣｒが平滑コン
デンサ電圧Ｅｄまで充電されると、昇圧用チョークコイ
ルＬｓに流れている電流が、負荷Ｌ側に流れ昇圧用チョ
ークコイルＬｓに流れる電流がやがてゼロとなり動作を
終了する（図２（ｄ）参照）。
【００１９】この動作で、昇圧用チョークコイルＬｓに
流れる電流は、非連続になるように制御されるので、ト
ランジスタＴｒ１とトランジスタＴｒ２がターンオンす
る時は、トランジスタＴｒ１とトランジスタＴｒ２の電
流はゼロであり、スイッチング損失は発生しない。ま
た、トランジスタＴｒ１とトランジスタＴｒ２がターン
オフする瞬間は、印加電圧がゼロであり、スイッチング
損失は発生しない。
【００２０】また、トランジスタＴｒ１、Ｔｒ２のＯＮ
〜ＯＦＦのデューティは、商用電源の１サイクルに渡っ
て一定の値に保持され、デューティを一定にすることに
より、入力電流ｉｓの波形は自動的に図３の包絡線に示
すようになり、交流入力電流Ｉｉｎは交流入力電圧と同
相の正弦波になる。この場合、トランジスタＴｒ１、Ｔ
ｒ２のデューティを大きく、ＯＦＦのデューティを小さ
くし過ぎると、昇圧用チョークコイルＬｓの電流がゼロ
にならない内にトランジスタＴｒ１、Ｔｒ２がＯＮして
しまい、入力電流ｉｓが非連続にならなくなるので、Ｏ
Ｎのデューティは余り大きくすることはできない。
【００２１】実施例によると、昇圧用チョークコイルＬ
ｓの電流を不連続にし、トランジスタＴｒ１、Ｔｒ２の
ターンオンはゼロ電流スイッチング（ＺＣＳ）動作を行
うので、スイッチング損失は発生しない。また、トラン
ジスタＴｒ１、Ｔｒ２には、共振用コンデンサＣｒが充
電されるまでは電圧は印加されず、トランジスタＴｒ
１、Ｔｒ２がターンオフする瞬間には、トランジスタＴ
ｒ１、Ｔｒ２の印加電圧はゼロで、ゼロ電圧スイッチン
グ（ＺＶＳ）動作を行うので、スイッチング損失は発生
しない。このように、実施例によると回路構成が簡単
で、入力電流に歪みがなく力率を大幅に改善した状態
で、ゼロ電流スイッチング（ＺＣＳ）動作とゼロ電圧ス
イッチング（ＺＶＳ）動作とを行って、スイッチング損
失と高周波ノイズを削減し、動作寿命を延長することが
可能になる。
【００２２】
【発明の効果】本発明によると、共振用コンデンサＣｒ
に平滑コンデンサ電圧Ｅｄが貯えられた状態で、第１ス
イッチング素子と第２スイッチング素子とが同時にゼロ
電流スイッチングでＯＮにされ、電源電圧と前記共振用
コンデンサＣｒの充電電圧との和が昇圧用チョークコイ
ルＬｓに印加され、昇圧用チョークコイルＬｓと共振状
態になった共振用コンデンサＣｒが放電を開始し、充電
電圧がゼロになると、昇圧用チョークコイルＬｓの電流
が、第１スイッチング素子−第２ダイオートＤｃ２、第
１ダイオードＤｃ１−第２スイッチング素子の二つのル
ートで分流し、昇圧用チョークコイルＬｓにはエネルギ
ーが貯えられ、第１スイッチング素子及び第２スイッチ
ング素子が、ゼロ電圧スイッチングでＯＦＦされ、昇圧
用チョークコイルＬｓに流れる電流が、第１ダイオード
Ｄｃ１−共振用コンデンサＣｒ−第２ダイオードＤｃ２
を流れて、共振用コンデンサＣｒが充電されて充電電圧
が平滑コンデンサ電圧Ｅｄに達すると、昇圧用チョーク
コイルＬｓに流れる電流が負荷側に流れ、スイッチング
損失なしに入力電流の力率改善が行われ、スイッチング
損失と高周波ノイズを削減し、動作寿命も延長すること
が可能になる。Description: BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a single-phase high power factor converter for rectifying AC power and improving the power factor for output. 2. Description of the Related Art In many cases, a booster type converter shown in FIG. 4 is used as a main circuit as a power factor improving circuit for converting an input current into a sine wave using a converter. This circuit has a simple configuration and can make its input current sinusoidal. [0004] In the boost converter according to the proposal of FIG. 4, the switching element Tr is turned on and off while a current is flowing, so that the switching loss is large and the power factor is improved. Is not smoothly performed, and the operating life of the switching element Tr is relatively short. The present invention has been made in view of the above-mentioned current situation of the power factor improvement, and has as its object the control operation of the power factor improvement is smoothly performed without switching loss, and the operating life is shortened. An object of the present invention is to provide a power factor correction type switching power supply that can be extended. [0005] To achieve the above object, the present invention provides a first rectified output terminal t1 of a single-phase AC power supply S.
And a second rectification output terminal t2, a series connection circuit of a boost choke coil Ls, an output diode D, and a smoothing capacitor Cd is connected.
A series connection circuit of a first switching element and a second diode Dc2 and a series connection circuit of a second switching element and a first diode Dc1 are provided between the connection point of the output diode D and the second rectification output terminal t2. A resonance capacitor Cr connected between the connection point of the first switching element and the second diode Dc2 and the connection point of the second switching element and the first diode Dc1; Smoothing capacitor Cd
The power from the single-phase AC power supply S is supplied to the load connected in parallel with an improved power factor. According to this structure, the boost choke coil Ls
Is zero and the smoothing capacitor voltage Ed is stored in the resonance capacitor Cr, the first switching element and the second switching element are simultaneously set to the ON state. Thus, the first switching element and the second
When the switching elements are simultaneously set to the ON state, the voltage of the single-phase AC power supply S and the resonance capacitor Cr
Is applied to the boosting choke coil Ls, the boosting choke coil Ls and the resonance capacitor Cr enter a resonance state, and the resonance capacitor Cr is discharged. When the discharge of the resonance capacitor Cr is completed and the charging voltage becomes zero, the current flowing through the boosting choke coil Ls is changed from the first switching element to the second diode D.
c2, the first diode Dc1 and the second switching element are shunted by two routes.
Energy is stored in s. When the first switching element and the second switching element are set to the OFF state in this state, the current flowing through the boost choke coil Ls flows through the first diode Dc1-the resonance capacitor Cr-the second diode Dc2, and the resonance capacitor Cr is charged. When the resonance capacitor Cr is charged to the resonance capacitor voltage Ed, the current flowing through the boosting choke coil Ls flows to the load side and gradually decreases, and eventually flows into the boosting choke coil Ls. The flowing current becomes zero, and the operation ends. In this operation, the current flowing through the boost choke coil Ls is controlled so as to be discontinuous, so that when the first switching element and the second switching element are turned on, the first switching element and the second switching element are turned off. The current of the switching element is zero, and no switching loss occurs. Further, at the moment when the first switching element and the second switching element are turned off, since the resonance capacitor Cr is completely discharged, the voltage applied to each switching element is zero, and no switching loss occurs. An embodiment of the present invention will be described below with reference to FIGS. Here, FIG. 1 is a circuit diagram showing the configuration of this embodiment, and FIG. 2 is a circuit diagram showing each embodiment of the present invention.
(A) to (d) show the operation in each mode, and FIG. 3 is a waveform diagram of the power supply input current of the present embodiment. As shown in FIG. 1, a filter reactor Lf and a filter capacitor Cf are connected in series between electrode terminals of an AC power supply S, and a connection point between the filter reactor Lf and the filter capacitor Cf is The diode 1 is connected between the rectification output terminal t1 and the diode 3 is connected between the connection point of the filter capacitor Cf and the AC power supply S and the rectification output terminal t1, with the cathode having the rectification output terminal t1 side. The capacitor C
f and the connection point of the AC power supply S and the rectification output terminal t2,
The diode 4 is connected with the anode on the rectification output terminal t2 side, and the diode 2 is connected between the connection point of the filter reactor Lf and the capacitor Cf and the rectification output terminal t2 with the anode on the rectification output terminal t2 side. It is. One end of a boost choke coil Ls is connected to the rectification output terminal t1, and the other end of the boost choke coil Ls is connected to the collector of a transistor Tr1 as a first switching element.
Is connected to the anode side of the second diode Dc2, and the cathode side of the second diode Dc2 is connected to the rectification output terminal t2. Further, an anode side of the first diode Dc1 is connected to a connection point between the boost choke coil Ls and the transistor Tr1, and the first diode Dc1
The collector of the transistor Tr2 as a second switching element is connected to the cathode side of c1, and the emitter of the transistor Tr2 is connected to the rectification output terminal t2. The connection point between the transistor Tr1 and the second diode Dc2 is connected to the transistor Tr2 and the first diode Dc2.
A resonance capacitor Cr is connected between the connection points of the diode Dc1.
Are connected, the transistor Tr1 and the first diode D
A series connection circuit of an output diode D and a smoothing capacitor Cd is connected between the connection point of c1 and the rectification output terminal t2, and a load L is connected in parallel to the smoothing capacitor Cd. Next, the operation of this embodiment having such a configuration will be described. As shown in FIG. 3, the waveform of the input current Iin from the single-phase AC power supply S to the rectifier circuit changes discontinuously and in a sinusoidal manner. The input current Iin becomes a complete sine wave by absorbing higher harmonic components by the filter reactor Lf and the filter capacitor Cf. The operation in each mode will be described below in association with the circuit of FIG. When the current flowing through the boost choke coil Ls is zero, the smoothing capacitor voltage E is applied to the resonance capacitor Cr.
With d stored, the transistors Tr1 and Tr2 are simultaneously turned on. Thus, the transistor Tr1 and the transistor Tr2 are
When set to the ON state at the same time, the sum of the voltage of the single-phase AC power supply S and the charging voltage Ed of the resonance capacitor Cr is applied to the boost choke coil Ls, and the boost choke coil Ls and the resonance capacitor Cr Are in a resonance state, and the resonance capacitor Cr is discharged (see FIG. 2A). When the discharge of the resonance capacitor Cr ends and the charging voltage becomes zero, the current flowing through the boosting choke coil Ls is reduced by the transistors Tr1 to Dc2 and the first diode Dc1 to the transistor Tr1.
The energy is stored in the boost choke coil Ls during this time (see FIG. 2B).
. In this state, the transistors Tr1 and T
When r2 is set to the OFF state, the current flowing through the boost choke coil Ls flows through the first diode Dc1-the capacitor Cr-the second diode Dc2, and the resonance capacitor Cr is charged (see FIG. 2C). . When the resonance capacitor Cr is charged to the smoothing capacitor voltage Ed, the current flowing through the boosting choke coil Ls flows to the load L, and the current flowing through the boosting choke coil Ls eventually becomes zero. (See FIG. 2D). In this operation, the current flowing through the boost choke coil Ls is controlled so as to be discontinuous. Therefore, when the transistors Tr1 and Tr2 are turned on, the currents of the transistors Tr1 and Tr2 are zero. No switching loss occurs. Further, at the moment when the transistor Tr1 and the transistor Tr2 are turned off, the applied voltage is zero, and no switching loss occurs. Further, the transistors Tr1 and Tr2 are turned on.
The OFF duty is maintained at a constant value over one cycle of the commercial power supply, and by keeping the duty constant, the waveform of the input current is automatically becomes as shown by the envelope in FIG. The input current Iin is a sine wave in phase with the AC input voltage. In this case, the transistors Tr1, T
If the duty of r2 is large and the duty of OFF is too small, the transistors Tr1 and Tr2 are turned on before the current of the boost choke coil Ls does not become zero, and the input current is no longer discontinuous.
The duty of N cannot be made too large. According to the embodiment, the boost choke coil L
Since the current of s is discontinuous and the transistors Tr1 and Tr2 are turned on to perform a zero current switching (ZCS) operation, no switching loss occurs. No voltage is applied to the transistors Tr1 and Tr2 until the resonance capacitor Cr is charged.
1. At the moment when Tr2 is turned off, the transistor T
Since the applied voltages of r1 and Tr2 are zero and a zero voltage switching (ZVS) operation is performed, no switching loss occurs. As described above, according to the embodiment, the zero current switching (ZCS) operation and the zero voltage switching (ZVS) operation are performed in a state where the circuit configuration is simple, the input current is not distorted, and the power factor is greatly improved. Switching loss and high-frequency noise can be reduced, and the operating life can be extended. According to the present invention, the resonance capacitor Cr
With the smoothing capacitor voltage Ed stored therein, the first switching element and the second switching element are simultaneously turned on by zero current switching, and the sum of the power supply voltage and the charging voltage of the resonance capacitor Cr is a boost choke. When the resonance capacitor Cr, which is applied to the coil Ls and is in resonance with the boost choke coil Ls, starts discharging and the charging voltage becomes zero, the current of the boost choke coil Ls is changed from the first switching element to the second Diode Dc2, the first diode Dc1 and the second switching element shunt, and energy is stored in the boost choke coil Ls, the first switching element and the second switching element are turned off by zero voltage switching, The current flowing through the boost choke coil Ls is equal to the first diode Dc1 Capacitors Cr- second diode Dc2
When the resonance capacitor Cr is charged and the charging voltage reaches the smoothing capacitor voltage Ed, the current flowing through the boost choke coil Ls flows to the load side, and the power factor of the input current is improved without switching loss. In addition, switching loss and high-frequency noise can be reduced, and the operating life can be extended.
【図面の簡単な説明】
【図１】本発明の一実施例の構成を示す回路図である。
【図２】本発明の各実施例の回路図で、（ａ）〜（ｄ）
は各モードでの動作を示す図である。
【図３】同実施例の電源入力電流の波形図である。
【図４】従来の昇圧形コンバータの構成を示す回路図で
ある。
【符号の説明】
１〜４ ダイオード
Ｔｒ１、Ｔｒ２ トランジスタ第１スイッチング素子
Ｌｓ 昇圧用チョークコイル
Ｃｒ 共振用コンデンサ
Ｃｄ 平滑用コンデンサ
Ｄｃ１ 第１ダイオード
Ｄｃ２ 第２ダイオードBRIEF DESCRIPTION OF THE DRAWINGS FIG. 1 is a circuit diagram showing a configuration of one embodiment of the present invention. FIGS. 2A to 2D are circuit diagrams of respective embodiments of the present invention.
FIG. 4 is a diagram showing an operation in each mode. FIG. 3 is a waveform diagram of a power supply input current of the embodiment. FIG. 4 is a circuit diagram showing a configuration of a conventional boost converter. [Description of References] 1-4 Diodes Tr1, Tr2 Transistor First Switching Element Ls Boosting Choke Coil Resonant Capacitor Cd Smoothing Capacitor Dc1 First Diode Dc2 Second Diode
フロントページの続き (56)参考文献 特開 平３−289359（ＪＰ，Ａ) 特開 平３−27772（ＪＰ，Ａ) 実開 平５−70191（ＪＰ，Ｕ) (58)調査した分野(Int.Cl.7，ＤＢ名) H02M 7/217 H02M 3/155 H02M 7/06 Continuation of front page (56) References JP-A-3-289359 (JP, A) JP-A-3-27772 (JP, A) JP-A-5-70191 (JP, U) (58) Fields surveyed (Int .Cl. 7 , DB name) H02M 7/217 H02M 3/155 H02M 7/06
Claims (1)
１と第２の整流出力端子ｔ２間に、昇圧用チョークコイ
ルＬｓ、出力ダイオードＤ、及び平滑用コンデンサＣｄ
の直列接続回路が接続され、 前記昇圧用チョークコイルＬｓ及び出力ダイオードＤの
接続点と前記第２の整流出力端子ｔ２間に、第１スイッ
チング素子及び第２ダイオードＤｃ２の直列接続回路
と、第２スイッチング素子及び第１ダイオードＤｃ１の
直列接続回路とが互いに並列に接続され、 前記第１スイッチング素子及び前記第２ダイオードＤｃ
２の接続点と、前記第２スイッチング素子及び前記第１
ダイオードＤｃ１の接続点との間に、共振用コンデンサ
Ｃｒが接続され、 前記平滑用コンデンサＣｄに並列に接続された負荷に、
前記単相交流電源Ｓからの電力が、力率が改善されて供
給されるように構成されていることを特徴とする単相高
力率コンバータ。(57) [Claim 1] The first rectified output terminal t of the single-phase AC power supply S
Between the first and second rectification output terminals t2, a boost choke coil Ls, an output diode D, and a smoothing capacitor Cd.
A series connection circuit of a first switching element and a second diode Dc2 is provided between a connection point of the boost choke coil Ls and the output diode D and the second rectification output terminal t2. A switching element and a series connection circuit of the first diode Dc1 are connected in parallel with each other; the first switching element and the second diode Dc
2 and the second switching element and the first
A resonance capacitor Cr is connected between the connection point of the diode Dc1 and a load connected in parallel with the smoothing capacitor Cd.
A single-phase high power factor converter, wherein the power from the single-phase AC power supply S is supplied with an improved power factor.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP31410593A JP3394574B2 (en) | 1993-11-19 | 1993-11-19 | Single-phase high power factor converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP31410593A JP3394574B2 (en) | 1993-11-19 | 1993-11-19 | Single-phase high power factor converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH07143755A JPH07143755A (en) | 1995-06-02 |
| JP3394574B2 true JP3394574B2 (en) | 2003-04-07 |
Family
ID=18049303
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP31410593A Expired - Lifetime JP3394574B2 (en) | 1993-11-19 | 1993-11-19 | Single-phase high power factor converter |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP3394574B2 (en) |
Families Citing this family (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR20020074245A (en) * | 2001-03-19 | 2002-09-30 | 주식회사 파웰 | High efficiency soft-switching AC-DC boost converter using coupled inductor and energy recovery circuit having power factor correction function |
| JP3759515B2 (en) * | 2003-07-04 | 2006-03-29 | 株式会社京三製作所 | Rectifier |
| KR100674713B1 (en) * | 2005-07-04 | 2007-01-25 | 삼성전기주식회사 | Low loss power factor correction circuit |
| JP2014236658A (en) * | 2013-06-05 | 2014-12-15 | 東芝三菱電機産業システム株式会社 | Soft switching circuit |
| CN107947572B (en) * | 2017-12-11 | 2019-12-03 | 三峡大学 | A series hybrid multi-port DC/DC converter suitable for energy storage unit access |
| CN107911024B (en) * | 2017-12-11 | 2019-12-03 | 三峡大学 | A High Efficiency Series Hybrid Multiport DC/DC Converter |
-
1993
- 1993-11-19 JP JP31410593A patent/JP3394574B2/en not_active Expired - Lifetime
Also Published As
| Publication number | Publication date |
|---|---|
| JPH07143755A (en) | 1995-06-02 |
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