JP3463015B2 - Pilot signal that can confirm synchronization in mobile communication system - Google Patents

Description

Detailed Description of the Invention

[0001]

FIELD OF THE INVENTION The present invention relates to communication systems, and more particularly to cellular communication systems.

[0002]

2. Description of the Related Art Code division multiple access (CDMA)
The modulation technology using the ivision multiple access method is used as a technology for easy communication in various systems. FIG. 1 illustrates a general system 10 that uses CDMA modulation techniques in the communication between each user equipment 12a, 12b, including cellular telephones, and base stations (BTS) 14a, 14b.

The base station controller (BSC) 16 is a base station 14
It includes interlace and processing circuitry to provide system control to a, 14b. The base station controller 16 is a public switched telephone network (PSTN) for transmission of appropriate user equipment.
Control the routing of telephone calls from the mobile station to the base station as appropriate. The base station controller 16 also controls the routing of calls from the user equipment via at least one base station to the public switched telephone network. The base station controller 16 can also support calls between user equipments through appropriate base stations. This is because the user device cannot generally directly communicate with other user devices. The base station controller 16 is typically coupled to the base stations 14a, 14b by various means including dedicated telephone lines, fiber optic links, or microwave communication links.

The arrows 13a-13d define possible communication links between the base station 14a and the user equipments 12a, 12b. Arrows 15a-15d define possible communication links between the base station 14b and the user equipments 12a, 12b.

On the reverse channel or uplink (channel or link from the user equipment to the base station), the user equipment signal is received by the base station 14a and / or the base station 14b, demodulated and combined and then the base of the combining point. The signal is transmitted to the station controller 16.

On the forward channel or downlink (channel or link from the base station to the user equipment), base station signals are received by user equipment 12a and / or user equipment 12b. The system is described in US Pat.
1,501, 5, 103,459, 5,10
No. 9,390, and No. 5,416,797, the entire disclosures of which are incorporated herein by reference.

The radio channel is inherently difficult to predict its habit, and is designed in a total manner using actual radio wave measurement information. Generally, signal fading in a wireless environment is caused by the presence or absence of a visible distance between a transmitter and a receiver, and an intermediate-scale slow-varying component having a log-normal distribution and a large-scale path loss component, and Rici
an) It is decomposed into small-scale fast-changing components with Rayleigh distribution.

FIG. 2 shows these three different radio wave phenomena. Sudden changes in the transmission path between transmitters and receivers are found, and these changes can range from direct visibility to being disturbed by buildings, mountains, trees, etc. The phenomenon of reduction in received power due to reflection, diffraction and refraction around the object, and reduction of the received power with increasing distance is known as path loss.

As shown in FIG. 2, the transmitted signal is reflected by obstacles between the transmitter and receiver to create a multipath channel. Due to multipath interference with different delay times, the received signal is subject to frequency selective multipath fading. For example, a carrier frequency of 2 GHz is used,
When a car with user equipment is running at a speed of 100 km / h, the maximum fading Doppler frequency is 18
It is 5 Hz. Coherent detectio
Although n) is used to increase the link capacity, channel estimation for coherent detection under fast fading as described above is generally difficult to achieve. Due to the fading channel, it is difficult to obtain a phase reference for coherent detection of the modulated information signal. Therefore, it is further useful to have a separate pilot channel.

Generally, the channel estimate for coherent detection is obtained from the common pilot channel. However, the common pilot channel transmitted by the unidirectional antenna has a different radio channel than the traffic channel signal transmitted via the narrow beam. It has been found that the common control channel often causes problems in the downlink when adaptive antennas are used. The above problem can be solved by a user-dedicated pilot symbol used as a reference signal for channel estimation. The dedicated pilot symbols may be time or code multiplexed.

FIG. 3 is a block diagram of a transmitter and a receiver for time-multiplexed pilot symbols for the re-selected channel estimation technique under the environment where the slow fading is changed to the fast fading. Conventional pilot symbols are periodically multiplexed into the transmitted data sequence. The pilot symbol and the data symbol are composed of one slot as shown in FIG.

Further, the information signal is modulated with a spreading code in a direct spreading code division multiple access (DS-CDMA) transmitter and correlated to the same code in the receiver. Therefore, low cross-correlation between users and interfering users is important in suppressing multiple access interference. Good autocorrelation properties are needed for stable initial synchronization, because large sidelobes of the autocorrelation function can lead to erroneous code synchronization decisions. Moreover, good autocorrelation properties are important for stable separation of multipath components.

Since the autocorrelation function of the spread code should be as similar as possible to the autocorrelation function of white Gaussian noise, the direct spread code sequence is also called a pseudo noise sequence.

The autocorrelation function and the cross-correlation function are connected in a manner that it is difficult to obtain a preferable auto-correlation value and cross-correlation value at the same time. This can be seen by noting that those with good autocorrelation properties also exhibit good arbitrariness to the sequence. Arbitrary codes exhibit poorer cross-correlation properties than deterministic codes.

Such mobile communication systems have undergone different stages of development and different countries have used different standards. First generation mobile systems of the 1980s used analog transmission for voice services. Advanced Mobile Phone Service (AMPS: Advanced Mobile Phone)
Service), UK Full Access Communication System (TAC
S: Total Access Communication System), Scandinavian Northern European Mobile Telephone (NMT: Nordic Mobile)
Telephone) and Nippon Telegraph and Telephone Service of Japan (NT
T: Nippon Telephone and Telegraph) belongs to the first generation system.

Second generation systems using digital transmission were introduced in the late 1980s. The system provides higher spectral efficiency than the first generation system, more data service and improved roaming.
ing). Global System for Mobile Communicati (GSM) in Europe
on), Japan's personal digital cellular system (PDC: P
Personal Digital Cellular) and American International Standard-95 (IS-95) belong to the second generation system.

Recently, research on the second generation mobile radio set work has been actively conducted, and the results are expected. International Telecommunications Union (ITU)
3rd generation network is IMT-2000 (International Mobile Telecom)
munication-2000), which is a universal mobile communication system (UMTS: Universal Mobi) in Europe.
le Telecommunication System). IMT
-2000 will provide a number of services including multimedia and high bit rate Pekit data.

Wideband code division multiple access (W-CDM
A) has emerged as a solution for mainstream wireless interfaces for third generation networks. W-CDMA is currently
European Telecommunications Standards Institute (ETSI)
Telecommunications Standard Institute), Japan Radio Industry and Business Association (ARIB)
dustry and Business), T of the American TIA Technical Association
R45, TR46, T1P T1P and Korea TTA
I, TTAII, (International CDMAI, International CDMAII, respectively
It was renamed to) and is in the process of standardization.

The background of the above contents and various systems is 19
T. Ojanpe, published by Artech House Publisher in 1998
It is disclosed in "Broadband Code Division Multiple Access for Third Generation Mobile Communications" by Ra et al, and the contents of the announcement therein are included in the present specification as reference materials.

Recently, the Japan Radio Industry Association, the European Telecommunications Standards Institute in Europe, the T1 in the United States,
The Korean TTA has planned a third generation mobile communication system based on GSM's wireless connection technology and core network, which provides various services including multimedia such as video and data. In order to present the technical specifications of the advanced next-generation mobile communication system, they agreed to the joint research, and the projector for this was designated as "Third Generation Partnership Project:".
3GPP).

The 3GPP is divided into the following three technical research departments. The first is the 3GPP system and service sector, which studies the system structure and service capabilities based on the 3GPP specification. The second is the research department for the Universal Radio Access Network (UTRAN). Here, the UTRN is a wideband-CDMA based on a frequency division duplex (FDD) mode.
And time division duplex (TDD: Time Divisio
n Duplex) mode based TD-CDMA applied wireless access network (RAN: Radio Access Network)
k). The third is a research department for core networks that evolved from the second generation Mobile Communications Globalization System (GSM) to have third generation networking capabilities such as mobility management and global roaming.

UTR among the 3GPP technical research departments
The Department of Research on AN defines and describes transmission channels and physical channels. This technical specification (TS S
1, 11 v1.1.0) was distributed in March 1999. The general disclosure contents of the technical specifications are included in the present specification as reference materials.

The physical channel is a dedicated physical channel (DPCH: Dedi) used in uplink and downlink.
including cated Physical Channel). Each dedicated physical channel (DPCH) typically comprises three layers: superframes, radio frames and time slots. 3GP
In the P radio access network (RAN) standard, a superframe has a maximum frame unit of 720 ms period.
From the viewpoint of the number of system frames, the superframe is composed of 72 radio frames. Each radio frame has a period of 10 ms, and one radio frame includes 16 time slots. Each time slot contains a field with the information bits according to a dedicated physical channel (DPCH).

FIG. 4 shows a 3GPP wireless connection network (R
Uplink dedicated physical channel (D) based on the AN standard
It is drawing which shows the frame structure of PCH). The uplink dedicated physical channel (DPCH) comprises two types of channels, namely, a dedicated physical data channel (DPDCH) and a dedicated physical control channel (DPCCH). The uplink dedicated physical data channel (DPDCH) is suitable for carrying dedicated data, and the uplink dedicated physical control channel (DPCCH) is suitable for carrying control information.

An uplink dedicated physical control channel (DPCCH) for transmitting control information is an N _pilot bit pilot field 21, an N _TPC bit transmission power control (TPC) field 22, and an N _FBI bit feedback information (FBI). Field 23 and N _TFCI
Bit Optional Transmission Coupling Indicator (TFC
I) It is composed of various fields such as the field 24.

The pilot field 21 contains N _pilot bits which aid in channel estimation for coherent detection. Optional transmission coupling indicator (TFC
I) 24 supports simultaneous provision of multiple services by the system. Uplink dedicated physical control channel (DPCC
H) Optional Transmission Coupling Indicator (TFCI)
The absence of 24 means that the services involved are fixed ratio services. The parameter k determines the number of bits per uplink DPDCH / DPCCH slot, which is related to the spreading factor (SF) of the physical channel, such as SF = 256/2 ^k . The spreading factor (SF) can range from 256 to 4.

FIG. 5 is a table showing various information of an uplink dedicated physical control channel (DPCCH).
The channel bit rate and channel symbol rate are the rates immediately before spreading. (At the time of such a technical explanation, the upward field dedicated physical control channel (DPC) of FIG. 4 (N _pilot , N _TPC , N _FBI , N _{TF CI} ) different from
The exact number of bits in the CH) field has not been determined. )

FIG. 6 is a table showing pilot bit patterns of the uplink DPCCH, and particularly shows 6-bit and 8-bit pilot bit patterns for each slot. In FIG. 6, the non-shadow sequence is used for channel estimation and the shadow sequence is used as a frame sync word or frame sync sequence. The pilot bit excluding the frame synchronization word, that is, the channel estimation word has a bit value of "1".

For example, if each slot contains 6 pilot bits (N _pilot = 6), slot #
1 through slot # 16, bit # 1 (C1),
Bit # 2 (C2), Bit # 4 (C3), Bit # 5
The sequence formed in (C4) is used as a frame synchronization word. When the number of pilot bits in each slot is 6 bits or 8 bits, a total of 4 sequences are used as a frame synchronization word. As a result, since one radio frame has 16 time slots, the number of pilot bits used as a frame synchronization word is 64 bits per frame.

FIG. 7 shows a 3GPP wireless connection network (R
Uplink dedicated physical channel (D) based on the AN standard
2 is a diagram illustrating a spreading and scrambling apparatus for PCH). The apparatus shown in FIG. 7 has an uplink dedicated physical data channel (DPDCH) and a dedicated physical control channel (DP).
Quadrature phase shift keying (CCH) is mapped to the I and Q channel tributaries, respectively.
hift Keying; QPSK).

Spreading is the task of converting all symbols into multiple chips through each channel tributary. I and Q
Each channel tributary has two different Orthogonal Variable Spreading Factors (OVSF).
r), that is, a different channelization code ( _CD or C
Diffuse with a chip ratio based on _C ). The orthogonal variable spreading factor (OVSF) represents the number of chips per symbol on each channel tributary. These two spread channel tributaries are summed and again the particular complex scrambled result is separated into real and imaginary numbers, put on their respective carriers and then transmitted.

FIG. 8 shows a 3GPP wireless connection network (R
Downlink dedicated physical channel (D) based on the AN standard
It is drawing which shows the frame structure of PCH). The number of pilot bits (or symbols) in the uplink dedicated physical channel (DPCH) is 6 bits or 8 bits, because the uplink dedicated physical channel (DPCH) operates at a fixed rate of 16 Kbps. . However, since the downlink dedicated physical channel (DPCH) operates at a variable rate, it has a pilot symbol pattern as shown in FIG.

In FIG. 8, the downlink dedicated physical channel (D
PCH is also an uplink dedicated physical channel (DPCH)
Similarly, a dedicated physical data channel (DPDCH) and dedicated
Two types of physical control channel (DPCCH)
Equipped with flannel. Downlink for transmission of control information
Dedicated physical control channel (DPCCH) is N_pilot B
Pilot field 27, N_TPCBit transmission
Power control (TPC) field 26 and N_TFCIBit of
Optional Transmission Coupling Indicator (TFCI) fee
Field 25 and various fields. Previous
The pilot field 27 is for coherent detection.
N for channel estimation_pilot Including symbols
Mu.

FIG. 9 is a table showing patterns of pilot symbols included in the downlink dedicated physical control channel (DPCCH), where the patterns are different according to different symbol rates of the downlink dedicated physical control channel (DPCCH). It is classified. For example, if the symbol rate is 16, 32, 64 or 128 kbps, each slot contains four pilot symbols for one channel tributary and four symbols for the Q channel tributary, so the total number of symbols is eight.
It is an individual.

In FIG. 9, the non-shadow sequence is used for channel estimation and the shadow sequence is used as a frame sync word. The pilot symbols other than the frame synchronization word, that is, the channel estimation word has a bit value of "1". For example, if the symbol rate is 16, 3
In the case of 2, 64 or 128 kbps, the sequence formed in the symbols # 1 and # 3 by the pilot symbols from slot # 1 to slot # 16 is used as the frame synchronization word. Therefore, since the number of pilot symbols used as a frame synchronization word is 4 for each slot, 64 pilot symbols are used for each radio frame.

FIG. 10 is a diagram showing a spreading and scrambling apparatus for a downlink dedicated physical channel (DPCH) based on the 3GGP radio access network (RAN) standard. The apparatus of FIG. 10 has a downlink dedicated physical channel (DPCH) and a common control physical channel (CCPC).
H: Common Control Physical Channel (H) is provided for spreading and scrambling. The QPSK operation is such that the symbols are serial to parallel converted, respectively, and then mapped to the I and Q channel tributaries.
Perform on a pair of symbols in two channels.

[0037] I channel branch and Q channel branch diffuses respectively to the chip rate based on the same two channelization code (C c _h). The spread two channel tributaries are summed and again complex _scrambled by the particular complex scrambling code C _scramb . The complex scrambled result is separated into a real number and an imaginary number, put on respective carrier waves, and then transmitted. In particular, the same scrambling code is used for all physical channels of one cell, while different channelization codes are used for different physical channels. The data and various control information are transmitted to the receiver via the uplink and downlink dedicated physical channels (DPGHs) that have been subjected to the spreading and scrambling described above.

The TS S1.11 v1.1.0 specification states that
Main common control physical channel (PCCP) of fixed rate downlink physical channels used to carry broadcast channels
CH: Primary Common Control Physical channel) and forward access channel (FAC) at a fixed rate
H) and an auxiliary common control physical channel (SCCPCH: Seco) that carries a paging channel (PCH)
ndary Common Control Physical channel) is specified.

11A and 11B are views showing frame structures of PCCPCH and SCCPCH having pilot fields, respectively. TS S1.11 v1.
The 1.0 specification recommends pilot patterns for PCCPCH and SCCPCH. Also, TS S1.11 v
1.1.0 In the specification, space-time block coding (Space
Transmission diversity based on time block coding (S
TTD) and dedicated physical channel (DPCH) pilot patterns for diversity antennas with open loop antenna diversity with diversity antenna pilot patterns for PCCPCH and SCCPCH are recommended.

The autocorrelation function for frame synchronization should be performed based on the pilot pattern sequence. In designing pilot sequences, it is important to find the autocorrelation of the sequence with the lowest correlation result in order to reduce the probability of false alarms for synchronization. False alarms are determined when peaks are detected where they should not be.

Optimally, the autocorrelation result values for one frame having one sequence with a given pilot bit are the maximum values of the same magnitude but different polarities at 0 time shift and intermediate time shift of one correlation period. Have. Then, the time shift of the remaining side lobes except for the 0 time shift and the intermediate time shift of the correlation period should have a correlation value of 0. However, TS S1.11 v1.
The various pilot patterns in uplink and downlink recommended in 1.0 do not meet the above conditions.

An article entitled "Synchronized Sequence Design with Dual-Critical Value for Digital Cellular Phones" co-authored by the inventor of the present invention, Young Joon Song (1998).
(August 18th to 20th of the year), a correlator circuit for the GSM code is described. The correlation result value is the first in the circuit.
The time shifts except for the 0 time shift having the peak and the second peak and the middle time shift are all 9, wherein the first peak and the second peak have opposite polarities and are not the same in magnitude. . Also, in the above article, the minimum correlation result values of +4 and -4 are described. However, the article does not disclose how such sequences and autocorrelation are used to achieve the optimal results described above, and is satisfied about whether the sequences can achieve minimum autocorrelation sidelobes. It doesn't provide an explanation.

As described above, the pilot pattern used as a frame synchronization word or sequence did not give an optimum result value, and the existing pilot pattern could not perform quick and accurate frame synchronization. Moreover, the pilot pattern and frame synchronization sequence do not provide optimal cross-correlation and auto-correlation results. Moreover, neither the TS specification nor the above article presents a solution to the use of pilot patterns for frame synchronization techniques capable of double-checking on a slot-by-slot basis, as well as a frame synchronization sequence for estimation. No use is disclosed.

[0044]

SUMMARY OF THE INVENTION An object of the present invention is to solve at least the problems and disadvantages of the prior art. It is an object of the present invention to provide a frame sync word with which an optimum autocorrelation result can be obtained. Another object of the present invention is to
It is to remove or prevent side lobes. Another object of the present invention is to provide maximum values at zero time shifts and intermediate time shifts. Yet another object of the present invention is to provide a frame sync word for fast and / or accurate frame sync.
Another object of the present invention is to provide a frame synchronization technique capable of double checking on a slot-by-slot basis. Another object of the present invention is to provide a frame synchronization word used for channel estimation. Yet another object of the present invention is to simultaneously provide better cross-correlation and auto-correlation results.

[0045]

According to the present invention, (1) the pilot symbol of each slot in a frame is received via each physical channel in a communication link, and (2) the received position of each pilot symbol and its correspondence. (3) Combine and add more than one correlation result, derive the final result from the correlation of side lobes offset from the correlation result, and (4) use the final result to perform frame synchronization. , A method of frame synchronization using optimal pilot symbols, comprising:
It can be reached by using it in whole or in part. The pilot symbols are combined into each pilot sequence so that the final result of the correlation shows side lobes with a "0" value, except for the special positions of the correlation period. The special positions are the start point (x = 0) of the correlation period (x) and "
x "points / integer. The pilot symbol is a combination of pilot symbols of the form (a, / a). The pilot sequence is at the starting point and at positions other than half the starting point of the correlation period. , Which provides the least correlation result. The pilot symbols, except the pilot symbols used in the correlation, are used for the channel that predicts coherent detection. The pilot symbols for each slot in the frame are transmitted and the pilot symbols are used for the communication link. It is included in the pilot field of the dedicated physical control channel in each dedicated channel above.
Different pilot sequences on the uplink communication link are used for correlation based on the bit value contained in the pilot field of the dedicated physical control channel. The different pilot sequences on the downlink communication link are
Used for correlation based on the symbol rate of the dedicated physical control channel. The invention also (1) receives pilot symbols for each slot in a frame via each physical channel in a communication link, and (2) correlates the received position of each pilot symbol with the corresponding pilot sequence. , (3) combining and adding more than one correlation result to obtain a correlation result having a minimum value, and a sidelobe correlation from a correlation result between a start point and an intermediate point of a correlation period having maximum values of different polarities. It can be reached by using the method of frame synchronization with optimal pilot symbols, wholly or partly, comprising the steps of deriving a final result from the relationship and (4) using the final result to perform frame synchronization. The present invention is a method for removing side lobes in a communication channel between a base station and a mobile station, comprising a control signal having a first sequence of L bits and a second sequence of L bits, and a data signal, Generating in the communication channel, a set of first predetermined values and a predetermined first
Generating a set of first predetermined values based on the related first sequence, a second set of predetermined values and a second predetermined set.
Using the method in whole or in part, comprising generating a second set of predetermined values based on a related second sequence and combining the first and second predetermined values. Can be reached by.

The present invention is a method for setting a communication channel, which comprises the steps of generating a plurality of frames and L slots for each frame, each slot having a length L. Of N pilot signals forming N words having sequence pilot bits and steps having corresponding bits of two pilot bits that are the same between two adjacent words of 1 to L slots. The number of bit values, minus the number of bit values of the two pilot bits different between two adjacent words 1 to L, is zero or a predetermined number close to zero,
The method can be reached in whole or in part. The present invention is a method for setting a communication channel having at least one of frame synchronization and channel estimation, which comprises a step of generating a plurality of frames and a step of generating L slots for each frame. A slot comprises N bits of pilot signal forming N words having sequence pilot bits of length L and stages having corresponding bits, with two time shifts of 0 used for synchronization. The property that the cross-correlation value is 0 between adjacent sequences, and the cross-correlation between one word used for frame synchronization at every time shift and one word used for channel estimation. It can be reached by using in whole or in part a method that has at least one property whose value is zero. The present invention generates a plurality of frame sync words,
Each frame sync word having a plurality of bits; performing an autocorrelation function on the set of frame sync words to produce a set of predetermined values;
Combining one set of said set of predetermined values such that the two peak values reach equal and opposite polarities with zero time shifts and intermediate time shifts. The method of removal can be reached by using wholly or partly. The present invention is a method for generating a pilot signal of a predetermined pattern in a frame having L slots, wherein N pilot bits are generated for each slot, and L bits based on the step are generated. and a step to form N words, a predetermined number of words are used as frame synchronization words, each frame synchronization word, such as b ₁ -b ₀ is equal to a value close to zero or zero, bit the first predetermined number b ₀ the value is _0, and the bit value is a method having a second predetermined number b ₁ is 1, can be reached by using in whole or in part. The present invention is a communication link between a user equipment and a base station, comprising multiple layers, one of the multiple layers for establishing communication between the user equipment and the base station. The physical layer has at least one piece of data and control information, one of the control information being L so as to form N words of L bits.
A pilot field of N bits transmitted for N slots, the cross-correlation between two adjacent words used for frame synchronization is zero time shift, zero, or used for frame synchronization. The cross-correlation between the word and the word used for channel estimation can be reached by using the communication link wholly or partially, which is zero at all time shifts. The present invention comprises a plurality of latch circuits for latching a word formed by pilot bits from a plurality of slots, a plurality of correlators coupled to the latch circuit and correlating the word with a set of predetermined values, each correlator. At least a user equipment and a base station, which combine the sets from the user equipment so that maximum peak values of the same magnitude but opposite polarities are formed with a 0 time shift and an intermediate time shift. It can be reached by using, in whole or in part, a correlation circuit configured for one. The present invention is
A communication device comprising means for transmitting at least one data and control information and means for receiving at least one data and control information, said receiving means comprising a word formed by pilot bits from a plurality of slots. A plurality of latch circuits for latching, a plurality of correlators coupled to the latch circuits for correlating the word with a set of predetermined values, and a plurality of buffers, each for storing a set of predetermined values. Combining buffers and sets from each buffer, coupled to the corresponding correlators, such that maximum peak values of the same magnitude but opposite polarities are formed with 0 and intermediate time shifts. , A combiner, in whole or in part. Additional advantages, objects, and features of the present invention are described below and will be apparent to those skilled in the art based on the following tests, and may be learned from the practice of the invention. The objects and advantages of the invention will be realized and attained by means of the appended claims.

[0047]

BEST MODE FOR CARRYING OUT THE INVENTION The new frame sync word according to the preferred embodiment of the present invention has a zero shift.
And a minimum shift result value of the autocorrelation function having two peak values having opposite polarities and the same magnitude in the middle shift. The frame sync word is suitable for frame sync confirmation, which is simply adding the autocorrelation function of the word to obtain double maximum correlation values of equal magnitude at zero shift and intermediate shift and with opposite polarity. Because you can This characteristic is used to double check the timing of frame synchronization and reduce the time for synchronization search.

The user equipment sets downlink chip synchronization and frame synchronization based on the initial common control physical channel synchronization time and frame offset group and the slot offset group reported from the network. The frame synchronization can be confirmed using a frame synchronization word. The network sets uplink channel chip synchronization and frame synchronization based on the frame offset group and the slot offset group. The frame sync can also be verified using the frame sync word.

When a long scrambling code is used in the uplink channel or the downlink channel, failure to confirm the frame synchronization using the frame synchronization word always means loss of frame and chip synchronization, which means long scrambling. This is because the code cycle is repeated for each frame.

On the other hand, in the case of a short scrambling code on the Uplink Dedicated Control Physical Channel (DPCCH), a failure of frame synchronization confirmation does not always mean a loss of chip synchronization, which is the length of the short scrambling code. Is 256 and its length is 25
This is because it corresponds to one symbol period of the uplink dedicated control physical channel of 6. Therefore, the frame synchronization word of the pilot pattern can estimate the state of synchronization, and the estimated information can be used in the layer 2 RRC connection setup and release process.

FIG. 12A is a table showing frame sync words C ₁ through C _{i-th according} to a preferred embodiment of the present invention. Each of the frame sync words includes N _pilot bits (N _pilot bits) from each of the L slots.
L of pilot bits from a predetermined bit position of> 0)
Sequence (L> 1). In the following first embodiment, the number i of synchronization words is 8, the number L of slots is 16, and the number N of pilots in each slot is N.
_pilot is between 4 and 16. However, the present invention is applicable to other numbers of i, L and N _pilots .

Sync Words C ₁ -C in the Preferred Embodiment
₈ are divided into the following four types (preferred correlation sequence pairs (E to H, referred to as PCSP)) according to the autocorrelation function of the synchronization word. E = {C ₁ , C ₅ } F = {C ₂ , C ₆ } G = {C ₃ , C ₇ } H = {C ₄ , C ₈ }

FIG. 12B shows 1 to 16 of each of the frame synchronization words classified into four types of E, F, G and H within one correlation period of the time shift from 0 to 15.
6 is a table showing an autocorrelation function of a pilot bit sequence. As shown in FIGS. 12A and 12B, each type includes two sequences, and sequences of the same type have the same autocorrelation function. As can be seen from FIG.
The sync words have the same magnitude and have the minimum phase offset of the autocorrelation when they have two peak values of opposite polarity at a shift of 1 and an intermediate shift. Furthermore, the result values R1 and R2 of the autocorrelation function are complements of each other. The relationships between the respective autocorrelation functions can be expressed by the following equations (1) to (4). R _E (τ) = R _F (τ) = R _G (τ) = R _H (τ), τ is an even number (1) R _E (τ) = − R _F (τ), τ is an odd number (2) R _{G (τ) = - R H} (τ), τ is odd _{(3) R i (τ)} + R i (τ + 8) = 0, i∈ {E, F, G, H}, for all tau ( 4) The following equation is obtained from the equations (1), (2) and (3). R _E (τ) + R _F (τ) = R _G (τ) + _RH (τ), for all τ (5)

Two autocorrelation functions R _E (τ) and R
Adding _F (τ), or adding R _G (τ) and R _H (τ), the two magnitudes are the same at 0 and the middle shift, but opposite in polarity, as shown in FIG. 13A. It becomes a function having a peak value and all 0 values except 0 and an intermediate shift, where the two peak values are 2 * L or -2L.
Is. In the preferred embodiment, the two peak values in FIG. 13A are 32 and −32 because L is 16.

(R _E (τ) + R _G (τ)), (R
_E (τ) + _RH (τ)), (R _F (τ) + R
_G (τ)) and other combinations such as (R _F (τ) + _RH (τ)) do not have the same values as in FIG. 13A. In this way, the following characteristics are obtained by using the characteristics of the derived frame synchronization word.

[Equation 1] Here, R _i (τ) is an autocorrelation function of the sequence Ci, and 1 ≦ i ≦ 8.

The sum of the four autocorrelation functions is shown in FIG. 13B.
In the above case, the maximum value is 4 * L or -4 * L.
It is the same as the value in FIG. 13A except that it is doubled.
(Thus, the maximum value for the preferred embodiment is 64 and
And -64.) The reason why the maximum value is doubled is the formula (5).
And (6) by (R_E(Τ) + R_F(Τ) + R
_G (Τ) + R_H(Τ)) = 2 (R_E(Τ) + R
_F(Τ)). Due to these characteristics,
Double check the frame sync time, reduce sync search time
It

(First Embodiment for Uplink Dedicated Physical Control Channel) FIGS. 14A and 14B show N
₉ is a table showing pilot patterns according to a preferred embodiment of the present invention for uplink dedicated physical control channels in which pilots are 5, 6, 7 and 8. The shading patterns of FIGS. 14A and 14B are used for frame synchronization (and also for channel estimation), and pilot bits that are not frame synchronization words (ie, channel estimation) have a value of 1. FIG. 14C illustrates the mapping relationship between the eight sync words C1 through C8 of FIG. 12A and the shaded pilot bit patterns of FIGS. 14A and 14B. Here, the frame synchronization words C1, C2, C3 to C4 are elements of the set {E, F, G, and H}, respectively. The values in FIGS. 13A and 13B are expressed in equation (6) as α
= 1 and 2 which gives N
The timing of frame synchronization on the uplink dedicated physical control channels of _pilots 5, 6, 7 and 8 can be double-checked and the synchronization time can be reduced.

For example, the frame sync word (C1) at bit # 1, the frame sync word (C2) at bit # 2, the frame sync word (C3) at bit # 4, and the frame sync word (C4) at bit # 5 are: When N _pilot is 6, it is used in the autocorrelation process for frame synchronization. If N _pilot is 8, the frame sync word (C
1), the frame sync word (C
2), frame sync word in bit # 5 (C3)
And the frame sync word (C4) at bit # 7 is used in the autocorrelation process for frame sync. If N _pilot is 5, 6, 7 and 8 in each slot, a total of 4 frame sync words are used.
Consequently, since one radio frame has 16 time slots, the number of pilot bits used for frame synchronization is only 64 per frame in the preferred embodiment. As can be predicted from this, the number of words used for frame synchronization is N
It can be changed by changing the _pilot . For example, if N _pilot is 1, then one of the C1 to C8 frame sync words is used for frame sync and channel estimation, according to a new feature of the preferred embodiment.

FIG. 14D shows a correlation circuit for frame synchronization based on the pilot bits of the uplink dedicated physical control channel according to the preferred embodiment of the present invention when the frame synchronization words C1 to C4 are used. The frame sync words C1 to C4 are latched by the latch circuits 31 to 34, respectively. Correlators 41 to 4
4 performs a correlation function R (x) on each of the frame sync words C1 to C4 to produce correlation result values A1 to A4 stored in buffers 51 to 53, where x = L-1. It is 0.

FIG. 14E is a table showing the sum of the correlation result values at the points A1 to A4 and the correlation result values at the point B.
As shown, the resulting value has maximum values of opposite polarities with a time shift R (0) of 0 and an intermediate time shift R (8). Furthermore, other side lobes in other time shifts that are not 0 and intermediate time shifts have a 0 value after the summation at point B. The side lobes are deleted or minimized, and the result value at the point B corresponds to the optimum result value of FIG. 13B.

FIG. 14F is a table showing various result values obtained by adding the correlation result values at points A1 to A4 based on the uplink pilot patterns of the frame synchronization words C1 to C4 according to the preferred embodiment of the present invention. (A
1 + A2), (A3 + A4), (A1 + A4) and (A
The individual sum of the autocorrelation result values at points such as 2 + A3) exhibits the same characteristics as the optimum result value shown in FIG. 13A.

FIG. 14G shows a correlation circuit for frame synchronization based on a pilot bit sequence of an uplink dedicated physical control channel according to another embodiment. The elements are the same as the correlation circuit of FIG. 14D. (C1 and C
2), (C2 and C3), (C3 and C4) or (C
4 and C1) frame sync words are correlated and summed to provide the resulting value at point D. As for the summation result value at the point D shown in FIG.
2 * L corresponding to the result value of 4F and the optimum result value of FIG. 13A
It is similar to the correlation circuit of FIG. 14D except that it is (32) and -2 * L (-32).

FIG. 14H shows the receiver circuit 60 of the base station or user equipment for recovering the received spread signal containing the frame sync word of the pilot field.
After collecting the spread signals received by the focusing circuit 61, the channel estimator and frame synchronizer 62 performs channel estimation and frame synchronization based on the pilot field. The rake combiner 63 uses the resulting values of the channel estimator and the frame synchronizer, and after rake combining, the data is deinterleaved by the deinterleaving circuit 64 in the reverse order of the transmission side. The data is then recovered after being decoded by the decoder 65.

The advantage of the present invention is that TS S1.11v
1.1.0 It is easy to understand by comparing with the frame sync word recommended in the specification and the frame sync word of N _pilot = 6, for example. Applying the same principles of equations (1) to (6) and the correlation circuit of FIG. 14D, the resulting values presented in FIG. 14I can be obtained for the pilot patterns pointed out in the technical description. When the summation result at the point B is mapped on the time shift graph, the problem of the side lobe immediately appears as shown in FIG. 14J. In other words, there is no maximum value of opposite polarity at 0 and the intermediate time shift, and side lobes exist at time shifts other than 0 and the intermediate time shift.

As explained in the prior art, it is difficult to obtain good cross-correlation and auto-correlation. Here, cross-correlation is the use of different words for different time-shifts and auto-correlation is the same sequence of time-shifted versions. The good cross-correlation and auto-correlation of the present invention is due to the unique nature of the frame sync word.

The unique characteristics of the frame sync word according to the preferred embodiment are made clear from the perspective of FIGS. 12, 14A and 14B. Each frame sync word has substantially the same number of 1's and 0's, as shown in frame sync words C ₁ through C ₈ of FIG. That is, when the pilot bit number (b ₀ ) of the frame synchronization word having the 0 value is subtracted from the pilot bit number (b ₁ ) of the frame synchronization word having the 1 value, the value becomes 0 or a value close to 0. If the number of slots is even in the preferred embodiment, b ₁ -b ₀ will be ₀ because the number of pilot bits with 1 and 0 values in a single frame sync word is the same. As predictable here, if the number of pilot bits in a single frame sync word is even, then b ₁ −
b ₀ is ± 1, that is, a value close to 0.

A second feature of the frame sync word is between a pair of adjacent frame sync words (when N _{pil ot} is 5, 6, 7 and 8 the shaded and non-shadowed portions of FIGS. 14A and 14B), or (when N _{pi lot} is 5, 6, 7 and 0, shaded and unshaded portions in FIGS. 14A and 14B) a pair of adjacent frame synchronization word and channel estimation word intelligible to consider between. Generally, the number (b ₃ ) of identical bit values (0, 0 and 1, 1) between a pair of adjacent words (ie between two adjacent frame sync words or adjacent frame sync words and the channel estimation word). ) To adjacent words (i.e., between two adjacent frame sync words or adjacent frame sync words and the channel estimation word), the number of different bit values (b ₄ ) is subtracted from 0 or a predetermined value close to 0. Becomes a number.

In the preferred embodiment, the number of identical pilot bit values (b ₃ ) between two adjacent words.
Is the same as the number of different pilot bit values (b ₄ ) between two adjacent words, and b ₃ −b ₄ = 0. In a preferred embodiment, as shown in FIG. 14A, N
_{When pilot} is 5, the number of identical pilot bit values (0, 0 and 1, 1) between sync word C1 at bit # 0 and sync word C2 at bit # 1;
The number of different pilot bit values (1,0 and 0,1) in slots # 1 to # 16 is the same. Similarly,
The same number of pilot bit values (0,0 and 1,1) between the sync word C2 at bit # 1 and the channel estimation word at bit # 2 and slots # 1 through # 1.
Up to 6 different pilot bit values (1, 0 and 0,
The number of 1) is the same. The same rule applies between two adjacent words of bits # 2 and # 3 and between two adjacent words of bits # 3 and # 4. The law is N
It can also be applied to adjacent words with _pilots of 6, 7 and 8. As can be predicted in the above, the result value of the odd number of slots are used b ₃ -b ₄ is several close to ± 1, that is 0.

As a result of the above characteristics, the cross-correlation between two adjacent words used for frame synchronization is 0 (orthogonal) with 0 time shift. Furthermore, the cross-correlation between the words used for frame synchronization and the sequences used for channel estimation is 0 (orthogonal) for all time shifts. That is, N _pi with L bits
Even though the words used for frame synchronization within the _lot words are even, all words perform channel estimation, where there is a substantial cross-correlation between adjacent words used for frame synchronization. Is 0. Also, the word used for frame synchronization has a cross-correlation of substantially 0 with the word for channel estimation at every time shift.

Furthermore, since each of the N _pilot words corresponds to a predetermined number of autocorrelation functions, a pair of values of the series of autocorrelation result values corresponding to the words used for frame synchronization are combined. While two peak values having the same magnitude but opposite polarities are obtained by 0 and the intermediate time shift, side lobes are substantially removed by the shifts other than 0 and the intermediate time shift. An autocorrelation according to the present invention is generally a correlation between a word and a time-shifted copy (including a copy with 0 time shift), where correlation is the same bit value between two words. Is subtracted from the number of different bit values between the two words. Further, as shown in FIG. 12B, R1 and R2 are complements of each other.

First Embodiment for Downlink DPCH FIG. 15A shows a pilot symbol pattern for the downlink DPCH when N _pilot = 4, 8, and 16. Here, the two pilot bits form one symbol. This is because the right bit is used as the I channel tributary and the left bit is used as the Q channel tributary.

In the preferred embodiment, N _pilot =
The pilot pattern of 4 is 8 ksps (kilo symbols p
er second: 10 ³ symbols per second) and the pilot pattern of N _pilot = 8 is 16,
Used for 32, 64, and 126 ksps, 25 pilot patterns with N _pilot = 16
Used for 6, 512, and 1024 kspsdp.

The symbol in the shaded area in FIG. 15A is the same as the frame.
Used for synchronization, these frame sync words are
Excluded pilot symbols, i.e. for channel estimation
The available channel estimation word is "11". Figure 15
The result of A is in the formula (6) for the downlink DPCH.
, N_pilot= 4 for α = 1, N_pilot =
Α = 2 for 8 and N_pilot= 16
And then α = 4 is applied.

FIG. 15B shows the mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 15A. For example, in the preferred embodiment with N _pilot = 4, symbol # 1 is C ₁ (I channel tributary I-CH, ie the right sequence in the bit string from slot # 1 to slot # 16) and C
₂ (Q channel tributary Q-CH, that is, the right sequence in the bit string from slot # 1 to slot # 16). N _pilot = 8,
Then, the correspondence of the word and channel to the symbol when N _pilot = 16 is shown in FIG. 15B.

Similarly, in the uplink DPCCH, double checking of the frame synchronization timing in units of slots and reduction of the frame synchronization search time can be realized by using the autocorrelation characteristic of the pilot symbol pattern based on Equation 6.

Since the downlink DPCH frame sync word is based on the frame sync word of FIG. 12A,
The characteristics described above for the uplink DPCCH can also be applied to the downlink DPCH. For example, between adjacent words (between an I-channel tributary synchronization word and a Q-channel tributary synchronization word for frame synchronization symbols, or adjacent Q-channel tributary channel estimation words and I-channel tributary frame synchronization). From the same (0,0 and 1,1) b ₃ bit value between the frame synchronization word of the Q channel tributary and the channel estimation word of the I channel tributary adjacent to each other or adjacent words Between (between an I channel tributary channel estimation word and an I channel tributary frame synchronization word for a frame synchronization symbol, or between adjacent Q channel tributary frame synchronization words and I channel tributary channel estimation words). different (1,0 and a) 0,1) when catching Bitch value of _{b 4,} 0 also 0 becomes a value close to.

For example, when N _pilot = 8, the number of adjacent bit pairs between symbol # 0 and symbol # 1, that is, a symbol having a bit value of "1 1" and "0 0" The number of one bit of the Q channel tributary which is # 0 and one bit of the I channel tributary which is the symbol # 1 is the same as the number of adjacent bit pairs having the bit values "1 0" and "0 1". is there. In other _words, b 3 _-b 4 =
It is 0. As described above, if the number of slots (L) is an odd _number, b ₃ -b ₄ results given number close to 0, that is, ± 1.

FIG. 15C shows the downlink DPCCH according to the preferred embodiment of the present invention when N _pilot = 8.
3 shows a correlator circuit for frame synchronization based on the pilot bits of the. Its operation and components are
It is the same as the correlator circuit for the uplink DPCCH shown in FIG. 14D, except for the reception of the synchronization words for the I and Q channel tributaries.

The result at the points A ₁ -A _{4 and} the result at the point B are the same as shown in FIG. 14E. Similarly, side lobes have been removed or minimized, and the resulting values are shown in FIG.
This corresponds to the optimum correlation result of 3B.

Since the number of pilot symbols (or pilot bits) used for frame synchronization is 2 symbols per slot (or 4 bits per slot), 32 pilot symbols (or 64 pilot bits) are used for frame synchronization. Used in radio frames.

When N _pilot = 4, downlink D
The correlator circuit of Figure 14G is used on the PCCH. In such a case, the frame synchronization words of the I channel tributary and the Q channel tributary are input to the correlator circuit. The summation result shown in FIG. 14F corresponds to the optimum result of FIG. 13A. In this case, the number of pilot symbols (or pilot bits) used for frame synchronization is 1 symbol per slot (or 2 bits per slot), and 16 symbols (or 32 pilot bits) for each frame synchronization. Used in radio frames.

When N _pilot = 16, on the downlink DPCCH, the correlator circuit of FIG. 15C can accept and extend additional frame sync words for the I and Q channel tributaries of pilot symbols # 5 and # 7.
The summation result is the same as the optimum result of FIG. 13B, but the maximum peak values of opposite polarities are 128 (8 * L) and -128 (-
8 * L). Also, the number of pilot symbols (or pilot bits) used for frame synchronization is 4 symbols per slot (or 8 bits per slot) and 64 symbols (or 128).
Pilot bits) are used in each radio frame for frame synchronization.

(Downlink PCCPCH and SCCPCH
FIG. 16A shows a pilot symbol pattern of PCCPCH. The shaded symbols are used for frame synchronization, and the value of the remaining pilot symbols excluding the frame synchronization word is "1".
It is 1 ".

FIG. 16B shows the eight sync words C of FIG. 12A.
It illustrates the mapping relationship between the shadows of the pilot symbol pattern shown in ₁ -C ₈ and FIG 16A. Double checking of frame synchronization timing and reduction of synchronization search time can be realized when α = 1 or α = 2 in equation (6).

FIG. 16C shows a pilot symbol pattern of SCCPCH. The shaded symbols are used for frame synchronization, and the value of the remaining pilot symbols excluding the frame synchronization word is "1 1".

FIG. 16D shows the eight sync words C of FIG. 12A.
It illustrates the mapping relationship between shades of pilot symbol pattern shown in ₁ -C ₈ and FIG 16C.

As described above, PCCPCH and SCCP
The CH frame sync word is the frame sync word C ₁ −.
Based on C _8, also be applied in the detailed description for the uplink DPCCH and downlink DPCH. Therefore, a more detailed description of various features including cross-correlation and auto-correlation, operation and implementation is omitted. A person having ordinary skill in the art of the present invention can easily understand the present invention based on the uplink DPCCH and the downlink DPCH.

As described above, the non-shaded symbols are not used for frame synchronization, and include "1 1" symbols. The shaded symbols are then used for frame synchronization. The frame sync word of the pilot pattern is used for frame sync confirmation, and the sum of the autocorrelation values of the frame sync word is required. The summation characteristic of the autocorrelation values of this frame word is very important.

The frame correlation word autocorrelation function according to a more detailed embodiment of the present invention for DPCH and PCCPCH and the current pilot pattern (TS S1.1).
1 v1.1.0) and the autocorrelation function (shown in the specification) are shown in FIGS. 17A to 17C. As can be seen here, the existing pilot patterns and the like have the maximum autocorrelation function with a time delay of 0, but do not have a correlation value of 0 with other time delays. On the other hand, the frame synchronization word according to the more detailed embodiment of the present invention is 0.
Have the two largest autocorrelation functions of the same magnitude but different polarities for the time delays and the intermediate time delays, and have a correlation value of 0 for the other time delays.

Correlation to a predetermined frame sync word is the optimal method for frame sync.
This is because the frame sync word of the pilot pattern is used to confirm the frame sync. The following events and parameters are used to improve the performance of frame sync confirmation using the pilot pattern of the present invention and the frame sync word of existing pilot patterns. H ₁ : the frame sync word in the received shadow column,
Correspondingly, an event where the output of the autocorrelator exceeds a predetermined critical value when the code phase offset with the frame sync word stored in the receiver is zero. H ₂ : the frame sync word in the received shadow column,
Correspondingly, an event in which the output of the autocorrelator exceeds a predetermined critical value when the code phase offset with the frame sync word stored in the receiver is non-zero. H ₃ : The event of H ₁ is once during one frame, and H ₂
There is no event. H ₄ : a frame sync word in the received shadow column,
Correspondingly, an event where the output of the correlator is less than "-1x (predetermined threshold value)" when the code phase offset with the frame sync word stored in the receiver is 0 or 8, respectively. H ₅ : the frame sync word in the received shadow column,
Correspondingly, an event where the output of the correlator is less than "-1x (predetermined threshold value)" when the code phase offset with the frame sync word stored in the receiver is neither 0 nor 8. H ₆ : The event of H ₄ is once in one frame, and H ₅
There is no event. P _D : detection probability. P _FA: false alarm (false alarm) probability. P _S : Success probability of confirmation of frame synchronization during one frame.

When the existing pilot pattern is used for confirmation of frame synchronization, the detection probability and the false alarm probability in the above definition are expressed by the following equations 7 and 8. P _D = Prob (H ₁ ) ... (7) P _FA = Prob (H ₂ ) ... (8) The success probability of confirming frame synchronization during one frame is P _S
= Prob (H ₃ ), which is represented by the following Expression 9. P _S = P _D (1-P _FA ) ¹⁵ (9)

Considering the case of a frame synchronization word according to a more detailed embodiment of the present invention, the double critical value is necessary for double inspection frame synchronization, and the detection probability and the false alarm probability are expressed by the following equations (10) and (11). As shown. P _D = Prob (H ₄ ) ... (10) P _FA = Prob (H ₅ ) ... (11) Similarly, in the case of the frame synchronization word according to the embodiment of the present invention, during one frame. The success probability of confirming the frame synchronization of is P _S = Prob (H ₆ ), which is expressed by the following Expression 12. P _S = P _D (1-P _FA ) ¹⁴ (12)

From Equations 9 to 12, it is possible to confirm the frame synchronization.
The recognition probability is greatly affected by the false alarm probability, which is
P_SAnd P_DAnd (1-P_FA)¹⁴, Or (1-P_FA)
¹⁵ Because it is proportional to For example, P_FA= 10^-1
At the time of (1-P_FA)¹⁴= 0.2288, (1-P
_FA)¹⁵= 0.2059. P_FA= 10^-3 of
Time is (1-P_FA)¹⁴= 0.9861 and (1-P
_FA)¹⁵= 0.9851. Frame synchronization performance
Is P_FAIs (1-P_D) Smaller than
It can be sufficiently improved by selecting.

The parameters of FIG. 18A are the same as those of the uplink DPCCH under the additive white gaussian noise (AWGN) and the P on the downlink DPCCH.
Used to obtain _D , P _FA and P _S. FIG. 18B shows a downlink DPCC under additive white Gaussian noise AWGN.
Shows the detection probability of P _D on the H. Figure 18C shows a false alarm (falsealarm) probability _{P FA} on downlink DPCCH under additive white Gaussian noise AWGN. Then, FIG. 18D shows the success probability of a frame synchronization confirmation of _{P D} on downlink DPCCH under additive white Gaussian noise AWGN. Where P _D , P _FA , and P
_S is the Eb / No ratio (Eb = energy per bit,
No = noise power spectral density) function. According to a more detailed embodiment of the present invention, P _D and P _S of the pilot pattern are P _{D of the} existing pilot pattern.
Higher than _{P S.} Furthermore, P _FA of the pilot pattern according to an embodiment of the present invention is less than P _FA of the existing pilot pattern. The theoretical equations 9 to 12 are the same as the simulation result of FIG. 18D. Therefore,
There is a significant difference in the frame synchronization performance between the pilot pattern of the present invention and the existing pilot pattern. For example, in FIG. 18D, there is a 3 dB gain at PS = 0.93 by using the pilot pattern of the present invention.

The frame sync word of the present invention is particularly suitable for confirming frame sync. By adding the autocorrelation function of the shaded frame sync word, etc., two maximum values with the same magnitude but different polarities are obtained with a time delay of 0 and an intermediate time delay. Such a characteristic can be used for each slot, and can be used for frame synchronization timing of double check. Further, it can be used to reduce the synchronization search time. The confirmation performance of frame synchronization under AWGN using a pilot pattern appears due to a significant difference in frame synchronization performance between the pilot pattern of the present invention and an existing pilot pattern.

(Downlink DPCH for STTD,
First Embodiment of PCCPCH and SCCPCH) FIG.
A is space-time block coding based on space-time transmission diversity (STTD)
FIG. 7 is a diagram showing a pilot symbol pattern of a downlink DPCH for a diversity antenna that uses a. For the diversity pilot symbol pattern on the downlink DPCH, STTD is N _pilot
= 8, in shaded pilot symbols # 1 and # 3,
It is applied to shaded pilot symbols # 1, # 3, # 5, and # 7 when N _pilot = 16. N
Non-shadowed pilot symbols # for _pilot = 8
0, # 2, and non-shaded pilot symbols # 0, # 2, # 4, and # 6 when N _pilot = 16 are shown in FIG.
It is encoded orthogonally to the A pilot symbol. However, the diversity pilot pattern for the downlink DPCH when N _pilot = 4 is STTD encoded. Here, STTD coding requires two symbols.

FIG. 19B shows the mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 19A, and FIG. 19C shows the diversity antenna pilot symbol pattern for the PCCPCH. The pilot symbols of FIG. 19C are orthogonally encoded with the pilot symbols of FIG. 16A. FIG. 19D shows the eight sync words of FIG. 12A and FIG. 19C.
3 shows the mapping relationship between the shaded pilot symbol patterns shown in FIG. FIG. 19E shows a new pilot symbol pattern for a diversity antenna when using space-time block coding on the SCCPCH. For diversity pilot symbol pattern on SCCPCH, STT in FIG. 19E
D is applied to the shaded pilot symbols # 1 and # 3 when N _{pi lot} = 8 and to the shaded pilot symbols # 1, # 3, # 5 and # 7 when N _pilot = 16. On the other hand, non-shaded pilot symbols # 0 and # 2 when N _pilot = 8 and non-shaded pilot symbols # 0, # 2, # 4, and # 6 when N _pilot = 16 are pilots in FIG. 16C. It is encoded orthogonally to the symbol. FIG. 19F shows the mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 19E.

Since the above description is based on the words C ₁ -C ₈ , the uplink DPCCH, downlink DPCH,
The above contents related to PCCPCH and SCCPCH can be easily applied. In addition, a person having ordinary skill in the art can easily understand the characteristics of the downlink using the diversity antenna based on the above-mentioned details. Therefore, a more detailed description will be omitted.

(Uplink DPCCH and Downlink DP
Other Embodiments for CH and PCCPCH) FIG. 20A
Is a frame sync word C according to another embodiment of the present invention.
₁ -C ₁₆ (i = ₁₆₎ and a table showing the autocorrelation function. The frame synchronization words C _{1 to} C ₁₆ are classified as follows by the PCSP of the first embodiment. _{E = {C 1, C 3} , C 9, C 11} F = {C 2, C 4, C 10, C 12} G = {C 5, C 7, C 13, C 15} H = {C 6 , C ₈ , C ₁₄ , C ₁₆ } The other partitioning of the frame sync word C ₁ -C ₁₆ is applicable to equations 1-6. And, it has the same characteristics and features as the first embodiment.

FIG. 20B shows each frame divided by PCSP.
Demonstrate the autocorrelation function of the pilot bits of the sync word
It's a table. In such a case, each class
Includes 4 sequences, sequences of the same class are the same
With an autocorrelation function of. 20C is N_pilot= 6
And N_pilot= 8 uplink DPCCH pilots
FIG. 20D shows another bit pattern of FIG. 20A.
Lame sync word C₁ -C₁₆And the shadow shown in FIG. 20C
The mapping relationship between frame synchronization words is shown.
20E and 20F are 8, 16, 32, 64, 128,
256, 512, 1024, 2048, and 4096
ksps downlink DPCH pilot symbol pattern
Shows the turn. FIG. 20G is another frame of FIG. 20A.
Sync word C₁-C₁₆And shown in FIGS. 20E and 20F.
Shows the mapping relationship between shaded frame sync words
There is. FIG. 20H shows a pilot of downlink PCCPCH
FIG. 20I shows another symbol pattern of FIG. 20A.
Lame sync word C₁-C₁₆And the shadow shown in FIG. 20H
The mapping relationship between frame synchronization words is shown.

Since the above description is based on the words C ₁ -C ₁₆ , it has the same characteristics as the words C ₁ -C ₈ of the first embodiment. Uplink DPCC of the first embodiment
H, downlink DPCH, PCCPCH and SCCPC
The above contents relating to H can be easily applied. Further, a person having ordinary skill in the art will readily understand the characteristics of the downlink using the diversity antenna based on the above-mentioned details. Therefore, a more detailed description will be omitted. The frame sync word and the like of more detailed embodiments of the present invention are particularly suitable for confirming frame sync. The addition of the autocorrelation function etc. of the shaded frame sync words gives a double maximum with the same magnitude but different polarities with a time delay of 0 and an intermediate time delay. Such a characteristic can be used for each slot, and can be used for frame synchronization timing of double check. It can also be used to reduce the synchronization search time. Furthermore, the invention further simplifies the structure of the correlator used in the receiver. As a result, the complexity of the receiver can be reduced. Due to various advantages of the present invention, the first embodiment is TS2 announced in June 1999.
Incorporated by 3GPP as shown in 5.211 v2.0.1. The contents of this announcement are included in the reference material of the present invention.

(Detailed Embodiment for L = 15) The pilot pattern and the like according to the more detailed embodiment of the present invention have various advantages including confirmation of frame synchronization. However, other pilot patterns and the like are necessary for 15 slots (L = 15). This is OHG (Ope
ration Harmonization Group). FIG. 21 shows a new frame sync word C according to an embodiment of the present invention.
_1- C _i-th is shown. It has an autocorrelation function with a minimum correlation coefficient, and the smallest magnitude cross-correlation function with a negative maximum at an intermediate time delay (i = 8).
These frame synchronization words are used to design the general pilot pattern and the uplink DPCH, and the diversity antenna pilot pattern of the downlink DPCH and SCCPCH of the embodiment of the present invention. The use of two correlation functions allows double-check frame synchronization with zero and intermediate time delays.

Words C ₁ -C ₈ of FIG. 21 are suitable for confirmation of frame synchronization when performing performance evaluation of confirmation of frame synchronization of single inspection and double inspection under the AWGN environment. The frame synchronization words C ₁ -C ₈ have two autocorrelation functions as shown in Expression 13 below.

[Equation 2] Here, R _i (τ) is the autocorrelation function of the frame synchronization word C _i . As in the case of L = 16, the words in FIG. 21 are divided into the following four classes. _{E = {C 1, C 2} } F = {C 3, C 4} G = {C 5, C 6} H = where _{{C 7, C 8},} 2 a word belonging to the same class are PCSP .

Equations 14 and 15 below are suitable pairs {C ₁ ,
_{C 2}, {C 3,} C 4}, {C 5, C 6}, {C 7, C
₈ } for the cross-correlation function.

[Equation 3] R _{i, j} (τ) in the above equation is the cross-correlation function between the two words of the appropriate pair of E, F, G, H, where i, j =
1, 2, 3, ...

By combining such an autocorrelation function and a cross-correlation function, the following equations 16 and 17 are obtained.

[Equation 4] In the above equations 16 and 17, when α = 2, FIG.
The sum of two autocorrelation functions is shown. FIG. 22B shows the sum of two cross-correlation functions between two frame sync words belonging to the same class. Similarly, in Equations 16 and 17, when α = 4, FIG. 22C shows the sum of four autocorrelation functions. FIG. 22D shows the sum of four cross-correlation functions between four frame sync words belonging to classes E and F. Since the autocorrelation function of the frame sync words C ₁ -C ₈ according to a more detailed embodiment of the present invention has the smallest correlation coefficient, the confirmation of frame sync of a single check is shown in the autocorrelation function output ( It can be realized by applying a negative critical value in a). Further, confirmation of the frame synchronization of the double inspection is realized by setting a negative critical value in (b) of the cross-correlation function output shown in FIG. 22D.

FIG. 23A shows the pilot bit pattern on the uplink DPCCH for N _pilot = 2, 3, 4 and FIG. 23C is N _pilot = compared to FIG. 23A.
3 shows pilot bit patterns on 2, 3, and 4 uplink DPCCHs. 23E to 23F show N
₃ shows pilot bit patterns on the uplink DPCCH for _pilot = 5, 6, 7, 8. FIG. 23A,
The shaded portions of Figures 23C, 23E, and 23F can be used as frame sync words. The pilot bit value excluding the frame synchronization word is 1.

FIGS. 23B and 23D show the mapping relationship between the frame synchronization words of FIG. 21 and the shaded frame synchronization words shown in FIGS. 23A and 23C, respectively. Also, FIG. 23G shows the frame synchronization word of FIG. 21 and FIGS.
3F shows the mapping relationship between shaded frame sync words shown in 3F.

When L = 16, the uplink DPCCH is paired
The above description is generalized with some modified correlator circuits
Features, and when L = 15, a more detailed implementation of the invention
It is easily applicable to the form. For example, the frame in FIG.
Sync word C₁-C₈Each word has the same number as shown in
With bit values of 1 and 0. More detailed implementation of the present invention
In the form of₁-B₀Results in a positive or negative value
Is. For example, the value is close to 0. Also the number of slots
When is 15, b_Three-B_FourResults in a positive value near 0 or negative
Is the value of. Furthermore, N_pilot= 2, 3, 4
Two frames in 15 time slots of one radio frame
Used for synchronization frame by frame because sync word is used
The number of pilot bits to be processed is 30. On the other hand, N
_pilot = 5, 6, 7, 8 for one radio frame
Uses 4 frame sync words in 15 time slots
Pilot used for synchronization every frame
The number of bits is 60. 2 or 4 flavors
Two or four autocorrelation functions between the synchronization words and the mutual
The results of adding the correlation functions are as shown in FIGS. 22A to 22D.
It

RACH (Random Access Channel) is an uplink transmission channel used to carry control information from a user equipment (UE). RACH is also used to carry short user packets. RACH is always received from all cells.

FIG. 23H shows the structure of a random access channel. The 10 ms message is divided into 15 slots and each length is T _SLOT = 2560 chips. Each slot has a data portion carrying second layer information and a control portion carrying first layer control information. The data part and the control part are transmitted in parallel. The data part is 10 * 2
Including ^k bits. Where k = 0, 1, 2, 3
This is 256, 12 each for the data part of the message.
Based on diffusion factors of 8, 64, and 32. The control part is a coherent detector known as 8.
and a pilot bit to support channel estimation for the channel and 2-bit rate information. It is based on a 256 spreading factor for the control part of the message.

FIG. 23I shows the Random Access Message Control field, which always contains 8 pilot symbols per slot for channel estimation. Due to unique features such as frame sync words according to more detailed embodiments of the present invention, frame sync words C ₁
-C ₈ can be used in RACH pilot bit pattern for channel estimation.

FIG. 23J shows a pilot bit pattern of RACH (Random Access Channel), and its mapping relationship is similar to that shown in FIG. 23G when N _pilot = 8. The unique features of which can be used for only the channel estimates frame synchronization words C ₁ -C _8, a pilot pattern so as to have a commonality between different uplink channels are easy to reuse.

FIG. 24A shows that N _pilot = 2, 4, 8, 1
6 shows a pilot symbol pattern on 6 downlink DPCHs. The shaded area in FIG. 24A can be used as a symbol for frame synchronization. Each of these symbols has one frame sync word for the tributary of the I channel and another frame sync word for the tributary of the Q channel. The value of the pilot symbol excluding the frame synchronization word is "11". FIG. 24B shows a mapping relationship between the frame sync word of FIG. 21 and the shaded frame sync word of FIG. 24A, and FIG. 24C shows a pilot symbol pattern of the downlink DPCH for a diversity antenna using STTD. . For the diversity pilot symbol pattern on the downlink DPCH, STTD is N
_{When pilot} = 8, shaded pilot symbol # 1,
# 3, and when N _pilot = 16, apply to shaded pilot symbols # 1, # 3, # 5, and # 7. N
Non-shadowed pilot symbols when _pilot = 8 #
FIG. 24 shows the non-shaded pilot symbols # 0, # 2, # 4, and # 6 when 0 pilot # 0 and N _pilot = 16.
It is encoded orthogonally to the A pilot symbol. However, when N _pilot = 4, the diversity pilot pattern for the downlink DPCH is STTD encoded. STTD coding requires two symbols.

Since the STTD coded pilot symbol pattern is orthogonal to the general pilot symbol pattern, the STTD coded pilot pattern can be used for diversity mode antenna checking in feedback mode. FIG. 24D shows the mapping relationship between the frame sync word of FIG. 21 and the shaded frame sync word of FIG. 24C.

FIG. 25A shows a pilot symbol pattern on the downlink SCCPCH with N _pilot = 8,16, and FIG. 25B shows the frame synchronization words C ₁ -C of FIG.
8A and _8B show the mapping relationship between the shaded frame sync words shown in FIG. 25A. Further, FIG. 25C shows a case where N _{pilot t is} compared with the diversity antenna using STTD.
= Indicates a pilot symbol pattern on downlink SCCPCH 8, 16, Figure 25D shows the mapping relationship between shaded frame synchronization words shown in frame synchronization words _C 1 -C ₈ and Figure 25C in FIG.

The above description for the downlink DPCH when L = 16 includes some modified correlator circuits and general features, and is easily applied to more detailed embodiments of the invention when L = 15. It is possible. Further, the addition results of the two or four auto-correlation functions and the cross-correlation functions between the two or four frame synchronization words are as shown in FIGS. 22A and 22D.

To improve the performance of the frame sync word in a more detailed embodiment for 15 slots per frame, the following events and parameters are first defined. H ₁ : An event in which the output of the autocorrelator exceeds a predetermined critical value when the code phase offset is 0. H ₂ : When the code phase offset is 0, the output of the autocorrelator exceeds a predetermined critical value, or when the code phase offset is 7, the output of the cross correlator is smaller than “−1 × (predetermined critical value)”. Event. H _3: When the code phase offset is not 0, the event that the output of the autocorrelator exceeds a predetermined threshold value. H ₄ : An event in which the output of the cross-correlator is smaller than “−1 × (predetermined threshold value)” when the code phase offset is not 7. P _S : Success probability of confirmation of frame synchronization. P _FA: false alarm (false alarm) probability.

Frame sync is confirmed when the output of the correlator using the frame sync word exceeds a predetermined critical value. The success of the frame synchronization confirmation is determined when the synchronization is confirmed in a continuous S _R frame. Therefore, the success probability of confirmation of frame synchronization is defined by the following Expression 18.

[Equation 5] The false alarm probability is expressed by the following equation 19.

[Equation 6]

The parameters of FIG. 26A are used to improve the performance of pilot bit patterns on the uplink DPCCH under AWGN. Figure 26B shows the success probability of a frame synchronization confirmation _{P S} on uplink DPCCH is _{N pilot} = 6 under additive white Gaussian noise AWGN, Figure 26C is added white Gaussian noise (AWGN)
_Shown below is the false alarm probability of P _FA on the uplink DPCCH with N _pilot = 6. P _S and P _FA are Eb
/ No ratio (Eb = energy per bit, No = noise power spectral density) given as a function. When S _R = 3 for the uplink DPCCH, P _S for confirming the frame synchronization of the single check and P _S for confirming the frame synchronization of the double check are respectively smaller than 0.945 and smaller than 0.99 at -5 dB. Also, the gain obtained by using the double inspection technique which is similar to the single inspection technique is about 4 dB. From FIG. 26C, when the critical value normalized by −5 dB is 0.6,
The false alarm probability is smaller than 2.5 × 10 ⁻⁴ . Eb / No = 0d when the double check frame synchronization confirmation technique is used
The pilot pattern can be used for confirmation of frame synchronization, since a successful confirmation of perfect frame synchronization with a false alarm of 0 in B is detected.

FIG. 27 is a table showing a comparison between the respective embodiments for 15 slots and 16 slots. L = 1
The pilot bit / symbol pattern for L = 15 according to a more detailed embodiment of the present invention, including the 6 hour advantage, has additional advantages.

[0121]

According to the present invention described above, a dual check frame synchronization technique is obtained by using the characteristics and features of these frame synchronization words. Also, by using the double check frame synchronization confirmation technique compared to the single check technique, a significant gain of about 4 dB is obtained. However, in the case of 15 slots, the complexity of the correlator circuit is high, which is due to the use of an autocorrelator for the detection of the positive maximum and a cross-correlator for the detection of the negative maximum. Because. Since the autocorrelation function of the 15-slot frame sync word has the smallest correlation coefficient, a single check frame sync confirmation technique can be used. In the case of 16 slots, there are some problems due to the correlation coefficient of +4 or -4, whereas the pilot pattern of 15 slots is suitable for confirming frame synchronization. This is the Eb on the uplink DPCH when the double check frame synchronization confirmation technique is used.
This is because a successful confirmation of perfect frame synchronization having a false alarm of 0 is detected at / No = 0 dB. Due to various advantages according to more detailed embodiments of the present invention, a 15-slot pilot bit / symbol pattern has been re-introduced into 3GPP.

[Brief description of drawings]

FIG. 1 illustrates a general system that uses CDMA modulation technology in communication between each user equipment (UE) and a base station (BS).

FIG. 2 is a diagram showing three different radio wave phenomena.

FIG. 3 is a block diagram of a transceiver and a receiver for time-multiplexed pilot symbols.

FIG. 4 is a diagram showing a frame structure of an uplink dedicated physical channel (DPCH) according to a 3GPP radio access network (RAN) standard.

FIG. 5 is a diagram showing various information for an uplink DPCCH.

FIG. 6 shows a pilot bit pattern for an uplink DPCCH.

FIG. 7 is a diagram showing a spreading and scrambling device for an uplink dedicated physical channel (DPCH) according to the standard of the 3GPP radio access network (RAN).

FIG. 8 is a diagram showing a frame structure of a downlink dedicated physical channel (DPCH) according to a 3GPP radio access network (RAN) standard.

FIG. 9 is a downlink dedicated physical control channel (DPCC).
The figure which shows the pilot symbol pattern contained in H).

FIG. 10 is a diagram showing a spreading and scrambling device for a downlink dedicated physical channel (DPCH) according to a 3GPP radio access network (RAN) standard.

FIG. 11A is a diagram showing a frame structure of PCCPCH and SCCPCH.

FIG. 11B is a diagram showing a frame structure of PCCPCH and SCCPCH.

FIG. 12A is a table showing a frame synchronization word according to an embodiment of the present invention.

FIG. 12B is a table showing autocorrelation for a sequence of pilot bits.

FIG. 13A is a diagram showing a result of summing two autocorrelation functions.

FIG. 13B is a diagram showing a result of summing four autocorrelation functions.

FIG. 14A is an uplink DPC according to an embodiment of the present invention.
A table showing pilot patterns for CH.

FIG. 14B is an uplink DPC according to an embodiment of the present invention.
A table showing pilot patterns for CH.

FIG. 14C is a table showing a mapping relationship between the eight sync words of FIG. 12A and the shaded pilot bit patterns shown in FIGS. 14A and 14B.

FIG. 14D is an uplink DPC according to an embodiment of the present invention.
The figure which shows the correlator circuit for frame synchronization based on the pilot bit of CH.

FIG. 14E is a table showing the correlation results at the points A ₁ -A ₄ and showing the result of the correlation results at the point B in FIG. 14D.

FIG. 14F is a table showing various summation results of correlation result values based on an uplink pilot pattern of a frame synchronization word according to an embodiment of the present invention.

FIG. 14G shows a selective correlator circuit for frame synchronization based on an uplink DPCCH pilot bit sequence.

FIG. 14H is a diagram illustrating a receiver circuit of a base station or a user equipment for recovering a reception spread signal including a frame synchronization word in a pilot field.

FIG. 14I is a diagram showing an output of a correlator circuit using a technical specification pilot pattern.

14J is a diagram showing a time shift with respect to the sum of the outputs of FIG. 14I.

FIG. 15A is a diagram showing a pilot symbol pattern for a downlink DPCH.

15B is a table showing a mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol patterns shown in FIG. 15A.

FIG. 15C shows a correlator circuit for downlink DPCCH pilot bit based frame synchronization according to an embodiment.

FIG. 16A is a diagram showing a pilot symbol pattern of PCCPCH.

16B shows a mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 16A.

FIG. 16C is a diagram showing a pilot symbol pattern of SCCPCH.

16D shows a mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 16C.

FIG. 17A illustrates a sum of autocorrelation functions of frame sync words according to an embodiment, showing current pilot patterns (TS S1.11v1.
1.0 described in the specification).

FIG. 17B illustrates the sum of auto-correlation functions of frame sync words according to an embodiment, showing current pilot patterns for TSCH 1.11v1.
1.0 described in the specification).

FIG. 17C illustrates the sum of auto-correlation functions of frame sync words according to an embodiment and present pilot patterns (TS S1.11v1.
1.0 described in the specification).

FIG. 18A is a diagram showing additive white Gaussian noise (AWGN: Additive).
The figure which shows the parameter used in order to obtain P _D , P _FA , and P _S on the uplink DPCCH and the downlink DPCH under White Gaussian Noise).

Figure 18B illustrates the probability of detection of additive white Gaussian noise (AWGN) _{P D} on downlink DPCCH below.

Figure 18C illustrates a false alarm probability of additive white Gaussian noise (AWGN) _{P FA} on downlink DPCCH below.

Figure 18D] additive white Gaussian noise (AWGN) illustrates a frame synchronization confirmation success probability of _{P D} on downlink DPCCH below.

FIG. 19A is a space-time block coding based on space-time transmission diversity (STTD).
FIG. 6 is a diagram showing a pilot symbol pattern of a downlink DPCH for a diversity antenna using oding).

19B is a diagram showing a mapping relationship between the eight synchronization words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 19A.

FIG. 19C shows a diversity antenna pilot symbol pattern for PCCPCH.

FIG. 19D shows a mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 19C.

FIG. 19E shows a pilot symbol pattern for a diversity antenna when space-time block coding is used on the SCCPCH.

FIG. 19F illustrates a mapping relationship between the eight sync words of FIG. 12A and the shaded pilot symbol pattern shown in FIG. 19E.

FIG. 20A is a table showing a frame synchronization word and an autocorrelation function according to another embodiment of the present invention.

FIG. 20B is a table showing an autocorrelation function of pilot bits of each frame synchronization word partitioned by PCSP.

FIG. 20C is a diagram showing a pilot bit pattern for an uplink DPCCH with N _pilot = 6 and N _pilot = 8.

20D illustrates a mapping relationship between the selective frame sync word of FIG. 20A and the shaded frame sync word of FIG. 20C.

FIG. 20E is a diagram showing a pilot symbol pattern of a downlink DPCH.

FIG. 20F is a diagram showing a pilot symbol pattern of a downlink DPCH.

FIG. 20G illustrates a mapping relationship between the selective frame sync word of FIG. 20A and the shaded frame sync word of FIGS. 20E and 20F.

FIG. 20H is a diagram showing a pilot symbol pattern of the downlink PCCPCH.

20I illustrates a mapping relationship between the selective frame sync word of FIG. 20A and the shaded frame sync word of FIG. 20H.

FIG. 21 shows a new frame sync word according to an embodiment of the invention.

FIG. 22A is a diagram showing the sum of two autocorrelation functions.

FIG. 22B is a diagram showing the sum of two cross-correlation functions between two frame synchronization words belonging to the same class.

FIG. 22C is a diagram showing the sum of four autocorrelation functions.

FIG. 22D shows the sum of four cross-correlation functions between four frame sync words in two classes.

FIG. 23A shows a pilot bit pattern on the uplink DPCCH with N _pilot = 2, 3, and 4.

23B is a diagram showing a mapping relationship between the frame sync word of FIG. 21 and the shaded frame sync words shown in FIGS. 23A and 23C, respectively.

FIG. 23C is N _pilot = 2,3, compared to FIG. 23A.
FIG. 6 is a diagram showing a pilot bit pattern on the uplink DPCCH that is 4.

23D is a diagram showing a mapping relationship between the frame sync word of FIG. 21 and the shaded frame sync words shown in FIGS. 23A and 23C, respectively.

FIG. 23E is a diagram showing pilot bit patterns on the uplink DPCCH with N _pilot = 5, 6, 7, and 8.

FIG. 23F is a diagram showing pilot bit patterns on the uplink DPCCH with N _pilot = 5, 6, 7, and 8.

FIG. 23G is a diagram showing a mapping relationship between the frame sync word of FIG. 21 and the shaded frame sync words shown in FIGS. 23E and 23F, respectively.

FIG. 23H is a diagram showing a structure of a random access channel.

FIG. 23I is a diagram showing a random access message control field.

FIG. 23J is a diagram showing a pilot bit pattern of RACH (Random Access Channel).

FIG. 24A shows a pilot bit pattern on the downlink DPCH with N _pilot = 2, 4, 8, and 16.

24B is a diagram showing a mapping relationship between the frame synchronization words of FIG. 21 and the shaded frame synchronization words shown in FIG. 24A.

FIG. 24C is a diagram showing a downlink DPCH pilot symbol pattern for a diversity antenna using STTD.

24D is a diagram showing a mapping relationship between the frame sync word of FIG. 21 and the shaded frame sync word of FIG. 24C.

FIG. 25A shows a pilot symbol pattern on the downlink SCCPCH with N _pilot = 8 and 16.

25B is a diagram showing a mapping relationship between the frame sync word of FIG. 21 and the shaded frame sync word of FIG. 25A.

FIG. 25C shows a pilot symbol pattern on the downlink SCCPCH with N _pilot = 8, and 16 for diversity antennas with STTD.

FIG. 25D is a diagram showing a mapping relationship between the frame synchronization words C ₁ -C ₈ of FIG. 21 and the shaded frame synchronization words shown in FIG. 25C.

FIG. 26A shows the parameters used to improve pilot bit pattern performance on the uplink DPCCH under additive white Gaussian noise (AWGN).

FIG. 26B: N under additive white Gaussian noise (AWGN)
It illustrates a frame synchronization confirmation success probability _{P S} on uplink DPCCH is _pilot = 6.

FIG. 26C shows N under additive white Gaussian noise (AWGN)
shows a false alarm probability of _{P FA} on uplink DPCCH is _pilot = 6.

FIG. 27 is a chart showing a comparison between embodiments for 15 slots and 16 slots.

─────────────────────────────────────────────────── ─── Continuation of the front page (31) Priority claim number 1999-15722 (32) Priority date April 30, 1999 (April 30, 1999) (33) Country of priority claim Korea (KR) (31) Priority claim number 1999-19505 (32) Priority date May 28, 1999 (May 28, 1999) (33) Priority claim country South Korea (KR) (31) Priority claim number 1999-34212 (32) Priority date August 18, 1999 (August 18, 1999) (33) Priority claiming country Korea (KR) (31) Priority claim number 1999-23140 (32) Priority date June 19, 1999 ( June 19, 1999 (33) Priority claiming country Korea (KR) (31) Priority claim number 1999-23141 (32) Priority date June 19, 1999 (1999.6.19) (33) Priority Claiming country South Korea (KR) (31) Priority claim number 1999-2356 (32) Priority date June 22, 1999 (June 22, 1999) (33) Priority claiming country Korea (KR) (31) Priority claim number 1999-23937 (32) Priority date June 1999 24th (June 24, 1999) (33) Priority claiming country South Korea (KR) (31) Priority claim number 1999-19506 (32) Priority date May 28, 1999 (May 28, 1999) ( 33) Priority Claim Country Korea (KR) (31) Priority Claim Number 1999-19610 (32) Priority Date May 29, 1999 (May 29, 1999) (33) Priority Claim Country Korea (KR) (31) Priority claim number 1999-26689 (32) Priority date July 2, 1999 (July 2, 1999) (33) Priority claiming country Korea (KR) (56) Reference JP-A-10- 327126 (JP, A) Special Table 10-505477 (JP, A) Kohno R et al. , Combinations of an adaptive array ante nana and a canceller of interference for Direct-Serial 1985, United States of America, United States of America, United States of America, United States of America, United States of America, 1985, United States of America, 1985 (Int.Cl. ⁷ , DB name) H04B ^7/ 24-7/26 H04Q ⁷ /00-7/38

Claims (8)

(57) [Claims] 1. A pilot signal in a mobile communication system, wherein the pilot signal has a significant autocorrelation value at a time shift of zero and an insignificant autocorrelation value at a time shift other than the zero time shift.
The code sequence and the first code sequence have a significant cross-correlation value at a predetermined time shift, and a second code sequence having a non-significant cross-correlation value with the first code sequence except at the predetermined time shift. A mobile communication pilot signal capable of confirming synchronization, comprising at least one pair of signals. 2. The second code sequence has a significant autocorrelation value at a time shift of zero and an insignificant autocorrelation value at other than the time shift of zero. Pilot signal. 3. The pilot signal according to claim 1, wherein the significant cross-correlation value has a polarity opposite to that of the significant auto-correlation value. 4. The first code sequence has a maximum autocorrelation value with a time shift of zero, and the second code sequence has a minimum cross-correlation value with the first code sequence at the predetermined time shift. The pilot signal according to claim 3, further comprising: 5. The pilot signal according to claim 1, wherein the predetermined time shift for the cross-correlation value is a time shift in the middle of a correlation period. 6. The pilot signal according to claim 1, wherein the pair of pilot sequences can double confirm synchronization. 7. The pilot signal according to claim 1, wherein the insignificant autocorrelation value has a value equal to or less than half of the significant autocorrelation value. 8. The pilot signal according to claim 1, wherein the non-significant cross-correlation value expressed as an absolute value has a value that is less than half of the significant cross-correlation value expressed as an absolute value. .