JP4073467B2 - Adaptive array antenna - Google Patents

Description

  The present invention relates to an adaptive array antenna, and more particularly to a radio base station used in a radio communication system and a radio communication system, and an adaptive array antenna used in a radio base station.

  Currently, development of a technology for configuring a direct communication path to a subscriber at low cost using a radio called a wireless local loop (WLL) has started. Among these, the form of a system that can accommodate a plurality of terminal stations for one base station is called point-to-multipoint (PTMP). FIG. 37 shows an explanatory diagram of this PTMP-type WLL.

  In general, in PTMP, it is necessary to communicate with a plurality of terminal stations having different directions as viewed from the base station, and therefore, the base station antenna uses an antenna having a relatively large half-value angle such as 60 degrees to 120 degrees. On the other hand, the terminal station generally uses an antenna with a small half-value angle of about 10 degrees and a large gain. Therefore, in PTMP, interference from other base stations other than a desired terminal station at the time of base station reception becomes a big problem. FIG. 38 shows an arrival state of an interference wave when a sector antenna having a half-value angle of 120 degrees is used. In particular, the control channel for making calls to the base station is a random access method that cannot be scheduled by the base station, so there is a high possibility that many interference waves will occur, and calls can be accepted through the control channel. There is a possibility that communication will be lost.

  Therefore, when a general sector antenna is used, a transmission interval from a terminal having a sharp directional antenna may reach a very far base station, so a distance interval for frequency repetition is required. . Specifically, about 4 to 7 cells are used as one unit, and frequency channels are divided in this unit, and the frequency is spatially reused by repeating the frequency for each unit. FIG. 39 shows the arrival state of interference waves in the case of 4-cell frequency repetition. However, in this case, there is a disadvantage that the capacity of subscribers that can be accommodated in the system as a whole is reduced because the frequency channel assigned to the system is limited due to restrictions on the repeated use of frequencies.

  In order to avoid interference at the same time without frequency repetition or by reducing the number of repetitions, together with an interference canceller that removes signals from other interference stations from the original received signal by signal processing, antennas to other interference stations The use of an adaptive array antenna with the null direction is considered.

  However, like the control channel of the PTMP system, an interference signal is generated at an unpredictable random timing, and the duration of the interference signal is very short, from several microseconds to several tens of microseconds. Therefore, it is very fast to detect the interference wave from this terminal and its direction of arrival at its own base station and perform control using digital signal processing or the like for directing null to the direction of the terminal. There was a problem of requiring signal processing speed.

  As shown in FIG. 40, in the case of a DBF (Digital Beam Forming) type adaptive antenna which has been mainly studied in recent years, real-time reception is performed when the transmission rate becomes faster, such as 1 Mbaud or more which is studied in the PTMP system. For this purpose, there is a problem that very fast digital signal processing is required.

  On the other hand, in the case of the PTMP system, as in mobile communication, in order to suppress the occurrence of unnecessary interference waves, it is conceivable to control the transmission power from the mobile station and make the reception power at the base station as constant as possible. However, even in such a case, the actual received power may not be constant due to the influence of fading and shadowing. Therefore, in order to make the signal level at the final stage of the receiver almost constant, an adaptive array The AGC function is required for the base station including the antenna. For example, as shown in FIG. 41, it is conceivable to provide an AGC function by inserting a variable gain amplifier 3801 into the combined output of the adaptive array antenna. However, for example, when the signal from other than the desired terminal is stopped in the cell and the phase shift amount is continuously changed by the phase shifter and the null point is scanned, the dynamic range of the combined signal level is considerably large. On the other hand, it is predicted that the intensity of the signals from the respective antennas before the synthesis becomes a substantially constant level. In this case, if the gain of the variable gain amplifier 3801 for AGC inserted in the combined signal line is increased as shown in FIG. 41 even if the level of the received signal after combining is lowered, the pre-combined signal level is increased. There is a problem that saturation occurs in a part of the signal flow.

  On the other hand, when the synthesis is performed such that the beam direction is directed after the terminal direction can be identified or converged to the optimum weighting factor, the signal strength after synthesis is stable. Fluctuation is reduced. On the other hand, the level of the signal strength from each antenna before combining may increase due to the combination of signals from a plurality of terminal stations. In this case, since the AGC function hardly operates, there is a problem that saturation occurs in a part of the signal flow before the synthesis.

  Further, when an adaptive array antenna is used for transmission, transmission power control is performed only by the variable gain amplifier 3901 before distribution to each element as shown in FIG. 42, or after distribution as shown in FIG. When transmission power control is performed only by a plurality of variable gain amplifiers 4001 inserted in the signal path for each element, the effective radiation power (ERP-Effective Radiation Power-) is determined in consideration of the directional gain of the adaptive array antenna. However, there is a problem that a high frequency circuit element for each individual element may be saturated.

  As described above, the conventional technique has a problem that a very high signal processing speed is required when an adaptive array antenna is used in order to reduce interference from a terminal station in PTMP.

  Further, in the case of a DBF (Digital Beam Forming) type adaptive array antenna, which has been mainly studied in recent years, if the transmission rate is increased, very fast digital signal processing is required for real-time reception. There was a problem.

  In addition, when an AGC function is provided by inserting a variable gain amplifier into the combined output of an adaptive array antenna, the gain of the AGC amplifier is increased simply because the level of the received signal after combining is lowered. There is a problem that saturation occurs in a part of the signal flow before synthesis.

  In addition, when an adaptive array antenna is used for base station transmission, transmission power is controlled only by a variable gain amplifier before distribution to each element, or a plurality of variable variables inserted into a signal path for each element after distribution. When transmission power control is performed only with a gain amplifier, the effective radiated power taking into account the directional gain of the adaptive array antenna may exceed a predetermined value, or the high-frequency circuit for each individual element will be saturated. There was a problem that there was.

  In order to solve the above problems, the present invention uses a plurality of individual element signal intensities detected by the individual element signal intensity detecting means and a combined signal intensity detected by the combined signal intensity detecting means to use real weights of the evaluation function. It is possible to perform real number weight control based on the steepest descent method and obtain a simple circuit configuration as compared with the case of using the demodulated signal of each antenna element as in the prior art. An object of the present invention is to provide an adaptive array antenna that can be used.

  In the present invention, in an adaptive array antenna including a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency synthesis circuit that synthesizes outputs of the plurality of high-frequency circuits, the output signal level after synthesis is constant. It is an object of the present invention to provide an adaptive array antenna that can be controlled in width and can be controlled so that a high-frequency circuit for each individual element is not saturated.

  The present invention further includes a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency distribution circuit that distributes output to the plurality of high-frequency circuits, and the amplitude or phase of each antenna element is included in the high-frequency circuit. A weight control circuit for weighting is provided, and the effective radiated power considering the directivity gain from the antenna is controlled so as not to exceed a predetermined value, and the high frequency circuit for each individual element is not saturated. It is another object of the present invention to provide an adaptive array antenna that can be controlled.

  In order to achieve the above object, an adaptive array antenna according to a first basic configuration of the present invention receives a reception signal including a control signal input from the outside, and transmits a transmission signal to the outside, and a plurality of antenna elements. A plurality of signal blocking means provided corresponding to the antenna element for passing or blocking each of the received signal and the transmitted signal to a subsequent circuit according to a control signal input from outside; and the plurality of signal blocking Provided in correspondence with the antenna element for controlling the phase of the received signal that has passed through the means according to the set phase shift amount and for controlling the phase of the transmission signal according to the set phase shift amount, respectively. A plurality of phase shifting means; a signal combining / distributing means for synthesizing the reception signals phase-controlled by the plurality of phase shifting means and distributing the transmission signal; and Calculating a phase shift amount of the received signal or the transmission signal based on intensity or information input with respect to the transmission signal, and setting the calculated phase shift amount in the phase shift unit; and the combining In the adaptive array antenna comprising: the signal strength detecting means for detecting the signal strength of the received signal received at the counterpart station based on the received signal synthesized by the means or information including the notification from the counterpart station of communication. The amount control means includes: a signal selection means for selectively switching the plurality of signal cutoff means so that any two of the signal cutoff means are set on the passing side and the rest are set on the cutoff side; and the plurality of signals Based on the received signal strength (P) detected by the signal strength detection means with any two of the cutoff means set to the passing side and the rest set to the cutoff side The phase shift amount calculating means for calculating the amount of phase shift that minimizes the degree (P), and the one connected to the signal blocking means set on the passing side by the signal selecting means among the plurality of phase shift means, And a phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculating means.

  The adaptive array antenna according to the second basic configuration of the present invention receives a reception signal including a control signal input from the outside and a plurality of antenna elements that transmit a transmission signal to the outside, and is input from the outside A plurality of signal blocking means provided corresponding to the antenna element for passing or blocking each of the reception signal and the transmission signal to a subsequent circuit according to a control signal, and the signal that has passed through the plurality of signal blocking means A plurality of phase shift means provided corresponding to the antenna elements for controlling the phase of the received signal according to the set phase shift amount and controlling the phase of the transmission signal according to the set phase shift amount, respectively. A signal combining / distributing unit that combines the reception signals phase-controlled by the plurality of phase shifting units and distributes the transmission signal; and the strength of the reception signal or the transmission The phase shift amount control means for calculating the phase shift amount of the received signal or the transmission signal based on the information input with respect to the signal and setting the calculated phase shift amount in the phase shift means, and the synthesis means In the adaptive array antenna comprising a signal strength detecting means for detecting the signal strength of the received signal received at the counterpart station based on the received signal or information including the notification from the counterpart station of communication, the phase shift amount control means comprises: In a state in which the transmission signal is transmitted by the antenna element, first signal strength storage means for storing the first strength (P1) of the received signal detected by the signal strength detection means, and the transmission signal by the antenna element A second signal strength storage means for storing a second strength (P2) of the received signal detected by the signal strength detection means in a state of not transmitting; Any two of the signal blocking means are set on the passing side, the signal selecting means for setting the rest on the blocking side, and any two of the plurality of signal blocking means are set on the passing side, and the rest are set on the blocking side. A phase shift amount calculation means for calculating a phase shift amount that minimizes the difference (P1−P2) based on the first intensity (P1) and the second intensity (P2) in the set state; A phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculation means to one connected to the signal blocking means set on the passing side by the signal selection means among the plurality of phase shift means. And.

  The adaptive array antenna according to the first or second basic configuration passes the plurality of antenna elements and received signals respectively received by the antenna elements to a subsequent circuit according to a control signal input from the outside. Alternatively, the plurality of signal blocking means provided corresponding to the antenna elements for blocking, and the antenna elements for phase control of the received signals that have passed through the signal blocking means according to the set phase shift amounts, respectively. The plurality of phase shifting means provided correspondingly, the synthesizing means as the synthesizing / distributing means for synthesizing the reception signals phase-controlled by the phase shifting means, and the intensity of the synthesized reception signal are detected. Based on the signal strength detection means and the received signal strength detected by the signal strength detection means, the phase shift amount is calculated and the calculated phase shift amount is A phase shift amount control means for setting said phase shifting means, may be provided with.

  The adaptive array antenna according to the first or second basic configuration includes a distribution unit as the combination distribution unit that distributes a transmission signal, and a transmission signal distributed by the distribution unit according to a set phase shift amount. The plurality of phase shifting means for phase control, and the plurality of signal blocking means for passing or blocking the transmission signals phase-controlled by the phase shifting means to the subsequent circuit according to the control signals input from the outside, respectively In order to transmit the transmission signals that have passed through the signal blocking means, the antenna elements provided corresponding to the signal blocking means and the phase shift amount are calculated based on the input information and the calculated phase shift amount is The signal for detecting the signal strength of the received signal received by the partner station based on the information including the notification from the partner station of communication and the phase shift amount control means set in each of the phase shift means And intensity detecting means, may be provided with.

  As described above in detail, according to the present invention, the real number of the evaluation function is obtained using the plurality of individual element signal intensities detected by the individual element signal intensity detecting means and the combined signal intensity detected by the combined signal intensity detecting means. Real number weight control based on the steepest descent method can be performed by obtaining the derivative with respect to the weight, so that it is realized with a simple circuit configuration as compared with the case where the demodulated signal of each antenna element is used as in the prior art. Can do.

  Further, since the phase shift amount control based on the partial differential coefficient with respect to the phase shift amount of the evaluation function can be performed using only the signal strength detected by the signal strength detection means, the signal for each antenna element as in the prior art. Compared with the case of using, it can be realized with a simple circuit configuration.

  Also, by using only the signal strength detected by the signal strength detection means, the phase shift amount for receiving the signal in the same phase by taking into account the phase shift deviation in the local station or the communication partner station by simple processing. Therefore, unlike the prior art, it is not necessary to set the amount of phase shift so as to compensate for the phase deviation, which can be realized with a simple circuit configuration and has an advantage of shortening the processing time.

  In addition, in an adaptive array antenna used in a radio communication system that provides service within a region by arranging a plurality of radio base stations for accommodating terminal stations, each direction of a base station group other than its own base station or one of the directions. By controlling the antenna beam quickly by adding a constraint condition that directs the null to the remaining directions except for the direction of the terminal that the base station communicates with, the direction of the part is small. The null restraining direction can be determined, and the control processing during communication can be reduced.

  The present invention also includes a plurality of antenna elements and a high-frequency circuit connected to each antenna element, and the local signal applied to the frequency conversion circuit in the high-frequency circuit is changed for each high-frequency circuit for each antenna element. In the adaptive array antenna, characterized in that a quadrature modulator that receives a local frequency signal and a control signal is used as the signal phase shift circuit or a part thereof, a part of the signal from each antenna element in the high frequency circuit By providing a coupler for branching and a quadrature demodulator for individual elements to which a signal from the coupler is input, real-time reception can be easily performed even when the transmission rate is high.

  According to the present invention, in an adaptive array antenna including a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency synthesis circuit that synthesizes outputs of the plurality of high-frequency circuits, RF or IF from a plurality of individual elements Among the signals, at least one first RSSI circuit that monitors at least one signal level, a second RSSI circuit that monitors the signal level of the RF or IF signal after combining the signals from the individual elements, and N At least (N-1) first variable gain circuits capable of changing the relative levels of all the RF or IF signals of each individual element, and the signal of the RF or IF signal after combining the signals from the individual elements The second variable gain circuit capable of varying the level, the RSSI signal from the first RSSI circuit and the second RSSI circuit Therefore, the output signal level after the synthesis is controlled to a constant width, and the first variable gain circuit and the second variable gain circuit are controlled so that the high frequency circuit for each individual element is not saturated. By providing such a gain control circuit, it is possible to control the combined output signal level to a certain width and to prevent the high frequency circuit for each individual element from being saturated.

  The present invention further includes a plurality of antenna elements, a high-frequency circuit connected to each antenna element, and a high-frequency distribution circuit that distributes output to the plurality of high-frequency circuits, and the amplitude or phase of each antenna element is included in the high-frequency circuit. In an adaptive array antenna including a weight control circuit for performing weighting, at least (N-1) first variable gain circuits capable of varying the relative levels of all RF or IF signals of N individual elements, and individual A second variable gain circuit element that can vary the signal level of the RF or IF signal before distribution to the element, and an effective radiated power in consideration of the directivity gain from the adaptive array antenna estimated from the output of the weight control circuit Is controlled so as not to exceed the specified value, and the high frequency circuit element for each individual element is not saturated. Thus, by providing the gain control circuit for controlling the first variable gain circuit and the second variable gain circuit, the effective radiated power taking into account the directional gain from the adaptive array antenna does not exceed a predetermined value. It is possible to control the high frequency circuit element for each individual element so as not to be saturated.

  DESCRIPTION OF EXEMPLARY EMBODIMENTS Hereinafter, preferred embodiments of an adaptive array antenna according to the invention will be described in detail with reference to the accompanying drawings. Prior to describing a specific embodiment, the basic concept of the present invention will be described with reference to FIG. FIG. 1 explains the basic principle of an adaptive array antenna as a superordinate concept of the first and second embodiments.

  Referring to FIG. 1, the adaptive array antenna includes first to n-th antenna elements 111 to 11n and a first phase control of received signals received by the antenna elements 111 to 11n in accordance with a set phase shift amount. Thru | or nth phase shift means 121-12n, the synthetic | combination means 130 which synthesize | combines the received signal phase-controlled by these phase shift means 121-12n, and the signal which detects the intensity | strength of the received signal synthesize | combined by this synthetic | combination means 130 A phase shift amount control that calculates a phase shift amount based on the strength detection unit 150 and the received signal strength detected by the signal strength detection unit, and sets the calculated phase shift amount in each of the phase shift units. Means 160. The output of the combining means 130 is demodulated by a normal demodulator 140.

  The phase shift amount control means 160 calculates a plurality of cycles of the phase shift amounts in the plurality of phase shift means 121 to 12n based on various signal intensities output from the signal strength detection means 150 and a plurality of phase shift amounts. Output phase shift amount calculation means 161, initial value storage means 162 for storing initial values of the plurality of phase shift means 121 to 12n, and the initial values stored in the initial value storage means 162, respectively. A first phase shift amount storage unit 163 for storing a first phase shift amount calculated as a value to be set in each of the plurality of phase shift units 121 to 12n by the phase shift amount calculation unit 161 based on the value; Storing a second phase shift amount in the plurality of phase shift means calculated by the calculation means 161 so as to increase the first phase shift amount by a predetermined angle X, respectively; A phase amount storage unit 164 and a third phase storage unit for storing a third phase shift amount in the plurality of phase shift units calculated by the calculation unit so as to decrease the first phase shift amount by a predetermined angle X. Phase shift amount storage means 165.

  The phase amount control unit 160 is further calculated by the phase shift amount calculation unit 161 based on the phase shift amount stored in any one of the first to third phase shift amount storage units 163 to 165. The first to n-th phase shift amount setting means 1661 to 166n for setting the phase shift amounts of the plurality of phase shift means, respectively, and the second phase shift amount to the plurality of phase shift means 1661 to 166n are set. In this state, the first signal strength storage unit 167 that stores the first signal strength detected by the signal strength detection unit 150, and the third phase shift amount is set in the plurality of phase shift units. Second signal strength storage means 168 for storing the second signal strength detected by the signal strength detection means in the state.

  When the difference between the first signal strength and the second signal strength is input, the phase shift amount calculation unit 161 increases the first phase shift amount by a value proportional to the difference. The phase shift amount is calculated and input to the first phase shift amount, and the calculation for a plurality of cycles is repeated until the difference is eliminated. The adaptive array antenna also includes an update stop unit 170 that stops the operation of the phase shift amount control unit 160 based on a predetermined condition.

  The signal strength detecting means 150 may be configured to detect the signal strength of the received signal as it is, but a reference signal generating means 151 as indicated by a broken line in FIG. 1 is provided to detect an error from this reference signal. The signal strength of the error signal output from the subtracter 152 may be detected. In this case, although details will be described in the second embodiment, the first and second signal strength storage means 167 and 168 function as error signal strength detection means, respectively.

  This basic principle is a summary of the highest concept of the present invention and is a superordinate concept of the following first to tenth embodiments. The intermediate concept is the following first and second concepts. An adaptive array antenna according to the second embodiment is conceivable. This will be described in detail below.

(First embodiment)
FIG. 2 is a configuration diagram of the adaptive array antenna according to the first embodiment of the present invention. In FIG. 2, 11 to 1n are antenna elements, 21 to 2n are amplifiers for amplifying received signals received by the antenna elements 11 to 1n, and 41 to 4n are phase shift amount control means to be described later for the amplified received signals. 3, a variable phase shifter that performs phase control in accordance with the phase shift amount set by 3, 5 is a combiner that combines the phase-controlled reception signals, and 6 is a demodulator that demodulates the combined reception signal, 71 is a signal strength detection means for detecting the strength of the received signal synthesized by the synthesizer 5, 3 is based on the detected strength of the received signal, and calculates a newly set phase shift amount, and calculates them Reference numeral 8 denotes phase shift amount control means for setting the phase shift amounts in the variable phase shifters 41 to 4n, and 8 denotes update stop means for stopping the operation after the operation of the phase shift amount control means 3 is repeated a predetermined number of times.

  Reference numerals 341 to 34n denote first phase shifts respectively storing phase shift amounts Φ1 (k) to Φn (k) (n is the number of antenna elements and k is the number of times of phase shift amount update) set in the variable phase shifters 41 to 4n, respectively. The phase amount storage means 351 to 35n calculate phase shift amounts Φ1 ′ (k) to Φn ′ (k) obtained by increasing the stored phase amounts Φ1 (k) to Φn (k) by 90 degrees, The second phase shift amount storage means 361 to 36n to store the phase shift amounts Φ1 (k) to Φn (k) stored by the first phase shift amount storage means 341 to 34n respectively reduced by 90 degrees. The third phase shift amount storage means 371 to 37n for calculating and storing the phase shift amounts Φ1 ″ (k) to Φn ″ (k) are the first phase shift amount storage means 341 to 34n or the second phase shift amount storage means 341 to 34n. Phase shift amount stored in any one of the phase amount storage means 351 to 35n or the third phase shift amount storage means 361 to 36n The phase shift amount setting means 311 to be set in the variable phase shifters 41 to 4n, respectively, Φ1 (k), Φ2 (k),..., Φi−1 (k), Φi ′ ( k), Φi + 1 (k),..., Φn (k) (1 ≦ i ≦ n) are set, the first signal for storing the received signal strength Pi ′ detected by the signal strength detection means 71 The intensity storage means 321 is connected to the variable phase shifters 41 to 4n by Φ1 (k), Φ2 (k),..., Φi−1 (k), Φi ″ (k), Φi + 1 (k),. ) Is set, second signal strength storage means 331 for storing the received signal strength Pi ″ detected by the signal strength detection means 71 is a value proportional to the difference between Pi ′ and Pi ″. A new phase shift amount Φi (k + 1) obtained by increasing Φi (k) stored in the i-th phase shift amount storage means, The phase shift amount calculation means 381 to 38n input to the i phase shift amount storage means respectively store the initial values Φ1 (0) to Φn (0) of the phase shift amount, and the phase shift amount control means 3 operates for the first time. Sometimes, initial value storage means for inputting these Φ1 (0) to Φn (0) to Φ1 (k) to Φn (k) of the first phase shift amount storage means 341 to 34n, respectively.

The operation of the adaptive array antenna configured as described above will be described. FIG. 3 is a flowchart showing the operation of the adaptive array antenna. First, the phase shift amount Φ1 (0) stored by the initial value storage unit 381 is input to the first phase shift amount storage unit 341. Based on this, Φ1 (0) is stored in Φ1 (k) as follows by the phase shift amount storage means 341 (step S1).
Φ ₁ (k) = Φ ₁ (0)

Subsequently, the phase shift amount Φ1 (k) stored by the first phase shift amount storage unit 341 is input to the second phase shift amount storage unit 351. Based on this, Φ1 ′ (k) is obtained as follows by the second phase shift amount storage means 341 (step S2).
Φ ₁ ′ (k) = Φ ₁ (k) +90

Subsequently, the phase shift amount Φ1 (k) stored by the first phase shift amount storage unit 341 is input to the third phase shift amount storage unit 361. Based on this, Φ1 ″ (k) is obtained as follows by the third phase shift amount storage means 361 (step S3).
Φ ₁ ″ (k) = Φ ₁ (k) −90

  S2 to S3 may be processed in the order of S3 → S2. Subsequently, the phase shift amount Φ1 (k) stored by the first phase shift amount storage unit 341 is input to the phase shift amount setting unit 371. This phase shift amount is set in the variable phase shifter 41 by the phase shift amount setting means 371 (step S4). Subsequently, the phase shift amounts Φ2 (0) to Φn (0) stored by the initial value storage means 382 to 38n are similarly set to the variable phase shifters 42 to 4n by the phase shift amount setting means 372 to 37n. .

  The initial value Φ1 (0) to Φn (0) of the phase shift amount may be set to the phase shift amount for synthesizing the desired wave in phase. Next, in step S5, it is determined whether i is n or more. If i is not n or more, the processes in steps S1 to S4 are repeated. If i is n or more, k = 1 is set in step S6. Is set.

と表される。この合成された受信信号ｙ（ｔ）は信号強度検出手段７１に入力される。これに基づいて、信号強度検出手段７１により検出される受信信号の強度Ｐは、

と表される。ただし、Ｅ［・］：期待値演算、＊：複素共役である。期待値演算は実際には時間平均演算に置きかえられる。これは、信号強度検出手段７１の時定数を十分大きい値に設定することで求めることができる。 At time t, the received signals received by the antenna elements 11 to 1n and amplified by the amplifiers 21 to 2n are defined as S1 (t) to Sn (t). These signals are phase-controlled by the variable phase shifters 41 to 4 n and synthesized by the synthesizer 5. If the phase shift amounts set in the variable phase shifters 41 to 4n are Φ1 (k) to Φn (k), the combined received signal y (t) is

It is expressed. The synthesized received signal y (t) is input to the signal strength detecting means 71. Based on this, the received signal strength P detected by the signal strength detection means 71 is:

It is expressed. However, E [•]: Expected value calculation, *: Complex conjugate. The expected value calculation is actually replaced with a time average calculation. This can be obtained by setting the time constant of the signal intensity detecting means 71 to a sufficiently large value.

  The feature of this embodiment is that the signal strength detection means 71 calculates the partial differential coefficient of the signal strength of the received signal detected by the signal strength detection means 71 with respect to the phase shift amount set in each of the variable phase shifters 41 to 4n. It is a point which can be calculated | required only using the signal strength of the received signal detected by (1). Based on this partial differential coefficient, phase shift amount control is performed. The phase shift amounts set in the variable phase shifters 41 to 4n are calculated by the phase shift amount control means 3 one by one. Here, a method of updating the phase shift amount of the variable phase shifter 41 will be described.

  The phase shift amount Φ′1 (t) stored by the second phase shift amount storage unit 351 is input to the phase shift amount setting unit 371. This phase shift amount is set in the variable phase shifter 41 by the phase shift amount setting means 371 (step S8). In this setting state, the received signal strength P1 'detected by the signal strength detection means 71 is input to the first signal strength storage means 311 (step S9). Subsequently, the phase shift amount Φ ″ 1 (t) stored by the third phase shift amount storage unit 361 is input to the phase shift amount setting unit 371. This phase shift amount can be changed by the phase shift amount setting unit 371. The phase shifter 41 is set (step S10) In this setting state, the received signal strength P1 "detected by the signal strength detection means 71 is input to the second signal strength storage means 321 (step S11). . S8 to S11 may be processed in the order of S10 → S11 → S8 → S9.

Subsequently, the received signal strength P 1 ′ stored in the first signal strength storage unit 311, the received signal strength P 1 stored in the second signal strength storage unit 321, and the first phase shift amount storage unit 341. The stored phase shift amount Φ1 (k) is input to the phase shift amount calculation means 331. Based on these inputs, a new phase shift amount Φ1 (k + 1) is calculated by the phase shift amount calculation means 331 as follows (step S12).
Φ ₁ (k + 1) = Φ ₁ (k) + α (P ₁ ′ −P ₁ ″)
Where α is a real number.

Subsequently, the new phase shift amount Φ1 (k + 1) calculated by the phase shift amount calculation unit 331 is input to the first phase shift amount storage unit 341. Based on this, Φ1 (k + 1) is stored in Φ1 (k) as follows by the first phase shift amount storage means 341 (step S13).
Φ ₁ (k) = Φ ₁ (k + 1)

Subsequently, the phase shift amount Φ1 (k) stored by the first phase shift amount storage unit 341 is input to the second phase shift amount storage unit 351. Based on this, Φ1 ′ (k) is obtained as follows by the second phase shift amount storage means 351 (step S14).
Φ ₁ ′ (k) = Φ ₁ (k) +90

Subsequently, the phase shift amount Φ1 (k) stored by the first phase shift amount storage unit 341 is input to the third phase shift amount storage unit 361. Based on this, Φ1 ″ (k) is obtained as follows by the third phase shift amount storage means 361 (step S15).
Φ ₁ ″ (k) = Φ ₁ (k) −90

  S14 to S15 may be processed in the order of S15 → S14. Subsequently, the phase shift amount Φ1 (k) stored in the first phase shift amount storage unit 341 is input to the phase shift amount setting unit 371. This phase shift amount is set in the variable phase shifter 41 by the phase shift amount setting means 371 (step S16).

  Subsequently, the same procedure is performed to update the phase shift amount of the variable phase shifters 42 to 4n. After the phase shift amount update operation of the variable phase shifters 41 to 4n by the phase shift amount control means 3 is repeated K times, the operation is stopped by the update stop means 8 (steps S17 to S18). In the present invention, since the amount of phase shift greatly fluctuates during the operation of updating the amount of phase shift, the intensity of the received signal input to the demodulator 6 also varies greatly, making demodulation processing difficult. Therefore, it is necessary to stop after repeating the operation of updating the amount of phase shift a predetermined number of times.

  Therefore, in step S17, it is determined whether i is n or more. If i is n or more, it is determined in step S18 whether k is K or less, and k is K or less. In this case, the process of steps S7 to S17 is repeated by incrementing one numerical value. When k is not less than K, the update process is stopped.

と表される。但し、ｉ：０≦ｉ≦ｎを満たす整数、Ｉｍ｛｝：虚部である。 Here, the operation is stopped by counting the number of repetitions of the phase shift amount update. However, the operation is not limited to this. For example, when Pi′−Pi ″ becomes a predetermined value or less, the operation is stopped. Conceivable.
Pi'-Pi "is

It is expressed. However, i: an integer satisfying 0 ≦ i ≦ n, Im {}: an imaginary part.

と表される。 On the other hand, the partial differential δP / δΦi of P by Φi is

It is expressed.

と等価の処理を行なっていることになる。 From the above, δP / δΦi = (Pi′−Pi ″) / 2 is established. Therefore, the process of step S12 is as follows.

Is equivalent to the process.

  When the real number α is a negative value, the phase shift amount of the variable phase shifters 41 to 4n is updated so as to reduce the output signal strength of the adaptive array antenna, and finally the phase shift amount at which δP / δΦi = 0. Is set, it is possible to suppress this when there is only an interference wave. For example, when such phase shift amount control is applied to a receiving adaptive array antenna of a base station, the phase shift amount of the variable phase shifter is controlled before giving a communication channel to a terminal station that has requested communication. Then, the phase shift amount for suppressing the co-channel interference is calculated, and then the communication channel is given to the terminal station, and the phase shift amount for suppressing the co-channel interference is set in the variable phase shifters 41 to 4n. A method of receiving a signal transmitted by the terminal station is conceivable.

  When the desired wave and the interference wave exist simultaneously, suppression of the desired wave can be avoided by fixing the phase shift amount of one or more variable phase shifters to the initial value.

  On the other hand, when the real number α is a positive value, the amount of phase shift of the variable phase shifters 41 to 4n is set so as to increase the output signal strength of the adaptive array antenna. Can be synthesized in phase. For example, when such phase shift amount control is applied to a receiving adaptive array antenna of a base station, when there is no co-channel interference, a signal is transmitted to one terminal station, and the phase shift amount of the variable phase shifter To calculate the phase shift amount to be in-phase combined, and then when the terminal station performs communication, the terminal station sets the phase shift amount to be in-phase combined in the variable phase shifters 41 to 4n. It is conceivable to receive a signal to be transmitted.

  Although the case where the phase shift amount is increased or decreased by 90 degrees has been described in the present embodiment, the same effect can be obtained when the phase shift amount is increased or decreased by X degrees.

と表される。 Pi′−Pi ″ when the amount of phase shift is increased or decreased by X degrees is

It is expressed.

と等価の処理を行なっていることになる。 As a result, δP / δΦi = (Pi′−Pi ″) / (2sin (X)) is satisfied.

Is equivalent to the process.

  In particular, when X is 90 degrees, the difference between Pi ′ and Pi ″ is maximized, so that δP / δΦi can be obtained with high accuracy.

  As described above, according to the first embodiment of the present invention, only the signal strength detected by the signal strength detection means 71 is used, and the partial differential of the received signal strength synthesized by the synthesizer 5 with respect to the phase shift amount. Since the phase shift amount control based on the coefficient can be performed, it can be realized with a simple circuit configuration as compared with the case where a signal is used for each antenna element as in the prior art.

(Second Embodiment)
Next, a second embodiment of the present invention will be described. FIG. 4 is a configuration diagram of an adaptive array antenna according to the second embodiment of the present invention. The difference from the first embodiment is that reference signal generation means, error detection means, error signal strength detection means, first error signal strength storage means, second error signal strength storage means, and phase shift amount calculation means are used. In the point.

  In FIG. 4, reference numeral 91 is a reference signal generating means for generating a reference signal, and reference numeral 92 is an error detecting means for outputting the difference between the received signal synthesized by the synthesizer 5 and the reference signal generated by the reference signal generating means 91. , 72 is an error signal intensity detecting means for detecting the intensity of the output error signal, and 312 is a variable phase shifter 41 to 4n with Φ1 (k), Φ2 (k),. ), Φi ′ (k), Φi + 1 (k),..., Φn (k) (1 <= i <= n) are set, and the intensity Qi ′ of the received signal detected by the error intensity detecting means 72 is set. The first error signal strength storage means for storing, reference numeral 322, is stored in the variable phase shifters 41 to 4n as Φ1 (k), Φ2 (k),..., Φi−1 (k), Φi ″ (k), Φi + 1 ( k),..., Φn (k) are set by the signal intensity detecting means 72. Second signal strength storage means for storing the intensity Pi ″ of the received signal to be output, reference numeral 332 is stored in the first phase shift amount storage means i by a value proportional to the difference between Qi ′ and Qi ″. This is a phase shift amount calculation means for calculating a new phase shift amount Φi (k + 1) by increasing Φi (k) and inputting it to the first phase shift amount storage means i. The other configuration is the same as in FIG. The overlapping description is omitted.

  The operation of the adaptive array antenna configured as described above will be described in more detail. FIG. 6 is a flowchart showing the operation of the adaptive array antenna.

と表される。この出力された誤差信号Ｅ（ｔ）は、誤差信号強度検出手段７２に入力される。これに基づいて、誤差信号強度検出手段７２により検出される誤差信号の強度Ｑは、

と表される。 First, steps S1 to S7 are performed in the same procedure as in the first embodiment. At time t, the received signals received by the antenna elements 11 to 1n and amplified by the amplifiers 21 to 2n are defined as S1 (t) to Sn (t). These signals are phase-controlled by the variable phase shifters 41 to 4 n and synthesized by the synthesizer 5. On the other hand, the reference signal generated by the reference signal generation unit 91 is D (t). A difference between the received signal synthesized by the synthesizer 5 and the reference signal generated by the reference signal generating means 91 is output by the error detecting means 92. For example, as illustrated in FIG. 5, the error detection unit 92 includes a 180-degree phase shift circuit 921 that shifts the reference signal by 180 degrees, a synthesis circuit 922 that combines the reference signal shifted by 180 degrees and the received signal, Consists of. If the phase shift amounts set in the variable phase shifters 41 to 4n are Φ1 (k) to Φn (k) (where n is the number of antenna elements and k is the number of times the phase shift amount is updated), the error detection unit 92 The output error signal E (t) is

It is expressed. The output error signal E (t) is input to the error signal strength detection means 72. Based on this, the error signal strength Q detected by the error signal strength detection means 72 is:

It is expressed.

  The feature of the second embodiment is that the partial differential coefficient of the signal strength of the error signal detected by the error signal strength detection means 72 with respect to the phase shift amount set in each of the variable phase shifters 41 to 4n is expressed as an error signal. This is a point that can be obtained using only the signal intensity of the error signal detected by the intensity detecting means 72. Based on this partial differential coefficient, phase shift amount control is performed. The phase shift amounts set in the variable phase shifters 41 to 4n are calculated by the phase shift amount control means 3 one by one. Here, a method of updating the phase shift amount of the variable phase shifter 41 will be described.

  Step S8 is performed in the same procedure as in the first embodiment. In this setting state, the error signal strength Q1 'detected by the error signal strength detection means 72 is input to the first error signal strength storage means 312 (step S101). Subsequently, the phase shift amount Φ ″ 1 (t) stored in the third phase shift amount storage unit 361 is input to the main phase shift amount setting unit 371. This phase shift amount is input by the phase shift amount setting unit 371. The variable phase shifter 41 is set (step S102) In this setting state, the error signal strength Q1 "detected by the error signal strength detection means 72 is input to the second error signal strength storage means 322 ( Step S103).

但し、α：実数である。 Subsequently, the error signal strength Q 1 ′ stored in the first error signal strength storage unit 312, the error signal strength Q 1 ″ stored in the second error signal strength storage unit 322, and the first phase shift amount storage unit 341. Is input to the phase shift amount calculation means 332. Based on these inputs, the new phase shift amount Φ1 (k + 1) is calculated by the phase shift amount calculation means 332 as follows. (Step S104).

Where α is a real number.

  Subsequently, steps S13 to S16 are performed in the same procedure as in the first embodiment. Subsequently, the same procedure is performed to update the phase shift amount of the variable phase shifters 42 to 4n. Subsequently, step S18 is performed in the same procedure as in the first embodiment.

と表される。 Qi'-Qi "

It is expressed.

と表される。 On the other hand, the partial differential δQ / δΦi of Q by Φi is

It is expressed.

と等価の処理を行なっていることになる。 From the above, δQ / δΦi = (Qi′−Qi ″) / 2 is satisfied.

Is equivalent to the process.

  When the real number α is a negative value, the phase shift amounts of the variable phase shifters 41 to 4n are updated so as to reduce the error between the output of the adaptive array antenna and the reference signal, and finally δQ / δΦi = 0. Therefore, when a desired wave and an interference wave exist, the interference wave can be suppressed. For example, when such phase shift amount control is applied to a receiving adaptive array antenna of a base station, the terminal station transmits a known signal before starting communication, and the base station transmits the same signal as the known signal. Using the signal as a reference signal, the phase shift amount of the variable phase shifter is controlled, the phase shift amount for suppressing the co-channel interference is calculated, and then the terminal station starts communication. A method of receiving a signal transmitted by the terminal station by setting a phase shift amount for suppressing the co-channel interference in the variable phase shifters 41 to 4n is conceivable.

  In the present embodiment, the case where the phase shift amount is increased or decreased by 90 degrees has been described. However, the same effect can be obtained when the phase shift amount is increased or decreased by X degrees.

と表される。 Qi′−Qi ″ when the phase shift amount is increased or decreased by X degrees is

It is expressed.

と等価の処理を行なっていることになる。 As a result, δQ / δΦi = (Qi′−Qi ″) / (2sin (X)) is satisfied.

Is equivalent to the process.

  In particular, when X is 90 degrees, the difference between Qi ′ and Qi ″ is maximized, so that δQ / δΦi can be obtained with high accuracy.

  As described above, according to the second embodiment of the present invention, in the adaptive array antenna that minimizes the strength of the difference between the received signal synthesized by the synthesizer and the reference signal as an evaluation function, the phase shift amount control is performed. Since the partial differential coefficient of the evaluation function necessary for performing the calculation can be obtained using only the signal strength detected by the error signal strength detection means 72, when the signal for each antenna element is used as in the prior art. In comparison, it can be realized with a simple circuit configuration.

(Third embodiment)
FIG. 7 is a configuration diagram of an adaptive array antenna according to the third embodiment of the present invention. In FIG. 7, reference numerals 11 to 1n denote antenna elements, and 711 to 71n denote signal cutoffs for passing or blocking received signals received by the antenna elements to subsequent circuits in accordance with control signals respectively input by signal selection means 75 described later. Means 21 to 2n are amplifiers for amplifying the received signals that have passed through these signal blocking means. 41 to 4n correspond to the phase shift amounts respectively set by the phase shift amount control means 3 to be described later. 5 is a synthesizer for synthesizing the phase-controlled received signals, 6 is a demodulator for demodulating the synthesized received signal, and 7 is a received signal synthesized by the synthesizer 5. The signal intensity detecting means 3 for detecting the intensity of the signal 3 calculates a phase shift amount based on the detected intensity of the received signal, and sets the calculated phase shift amounts in the variable phase shifters 41 to 4n, respectively. That is the amount of phase shift control means.

  For example, the signal cut-off means 711 to 71n may be power switches of amplifiers 21 to 2n. 75 is a signal selection means for setting any two of the signal blocking means 1101 to 110n to the passing side and the rest is set to the blocking side, and 331 is any one of the signal blocking means 711 to 71n being set to the passing side. Based on the received signal strength P detected by the signal strength detection means 7 with the others set to the cutoff side, phase shift amount calculation means 371 to calculate the phase shift amount that minimizes the P 37n is a variable phase shifter i connected to the signal blocking means i (1 ≦ i ≦ n) set on the passing side by the signal selection means 75 among the variable phase shifters 41 to 4n. This is a phase shift amount setting means.

  The operation of the adaptive array antenna according to the third embodiment configured as described above will be described. FIG. 8 is a flowchart showing the operation of the adaptive array antenna.

  When a terminal station newly starts operation or when an existing terminal station restarts operation only after changing its position, the terminal station transmits a first control signal to the base station, and a communication channel Is free, the base station designates one or more communication channels for subsequent transmission / reception using the second control signal, and the terminal station uses the communication channel designated by the base station to Transmission is performed with transmission power (steps S1001 to S1004).

  Subsequently, the signal selection means 75 sets the first signal blocking means 711 to the passing side and the second to nth signal blocking means 712 to 71n to the blocking side (step S1005).

  The feature of the third embodiment is that the phase of the received signal whose phase is controlled by the second to n-th variable phase shifters 42 to 4n based on the signal strength of the received signal detected by the signal strength detecting means 7. The phase of the received signal whose phase is controlled by the first variable phase shifter 41 is opposite to the phase of the received signal whose phase is controlled by the variable phase shifters 2 to n (1042 to 104n). Thus, the amount of phase shift is controlled. The phase shift amounts set in the variable phase shifters 2 to n (1042 to 104n) are calculated by the phase shift amount control means 1003 one by one. Here, a method of setting the phase shift amount of the variable phase shifter 2 (1042) will be described.

  The signal selecting means 75 sets the second signal blocking means 712 to the passing side, and notifies the phase shift amount calculating means 331 that it has been set to the passing side in this way (step S1006). In this state, the received signal strength P detected by the signal strength detection means 7 is input to the phase shift amount calculation means 331 (step S1007). Based on this, the phase shift amount calculation means 331 calculates the phase shift amount Φ2 that minimizes the strength P (step S1008).

  As a method of minimizing the signal strength P, for example, the method described with reference to FIG. 3 or the method of sequentially setting the phase shift amount and determining the phase shift amount that minimizes the signal strength P can be considered. FIG. 9 shows the change in intensity P in dB when the phase shift amount is sequentially set. As shown in FIG. 9, since the minimum point of the received intensity has a sharp characteristic, the phase shift amount can be determined with high accuracy.

  Subsequently, based on the notification from the signal selection unit 75, the phase shift amount Φ 2 calculated by the phase shift amount calculation unit 331 is input to the phase shift amount setting unit 372. This phase shift amount Φ2 is set in the second variable phase shifter 42 by the phase shift amount setting means 372 (step S1009). Subsequently, the second signal blocking means 712 is set to the blocking side by the signal selection means 75 (step S1010). Subsequently, the same procedure is used for setting the phase shift amount of the third to n-th variable phase shifters 43 to 4n.

  Through the above processing, the phase of the reception signal phase-controlled by each of the second to n-th variable phase shifters 42 to 4n is opposite to the phase of the reception signal phase-controlled by the first variable phase shifter 41. It becomes a phase relationship. Subsequently, the signal selection unit 75 sets the first signal blocking unit 711 to the blocking side and the second to nth signal blocking units 712 to 71n to the passing side (step S1011).

  Through the above processing, the phases of the received signals whose phases are controlled by the variable phase shifters 2 to n (1042 to 104n) become the same, and the signal transmitted from the terminal can be in-phase combined by the combiner 5. For example, if the calculated amount of phase shift is stored, it can be used when a call is resumed after a call is terminated once. The effects of the third embodiment of the present invention described above are summarized as follows.

  Based on the signal strength of the received signal detected by the signal strength detection means 7, the phase shift amount for receiving the signal transmitted from the terminal station by in-phase synthesis can be obtained by simple processing. Therefore, there is an advantage that it can be realized with a simple circuit configuration and the processing time can be shortened. This is particularly effective when real-time processing is required in a high-speed transmission wireless communication system.

  Even if there is a deviation of the device connected to each antenna element, a deviation of the antenna element, or a phase deviation due to multipath propagation, etc. Unlike the conventional beam steering method, it is not necessary to set the amount of phase shift so as to compensate for the phase deviation, and the compensation by measuring the deviation can be omitted or simplified.

  The optimal amount of phase shift once stored, especially when the base station and terminal station are spatially fixed as in the WLL (Wireless Local Loop) system, the radio wave propagation environment is substantially fixed in time. Therefore, it can be used again, and the control during communication can be simplified.

(Fourth embodiment)
Next, an adaptive array antenna according to a fourth embodiment of the present invention will be described. Since the configuration of the adaptive array antenna according to the fourth embodiment of the present invention is the same as that of the third embodiment, the hardware configuration will be described according to the configuration of FIG.

  The difference from the third embodiment is that, after step S1011 in FIG. 8 showing the processing operation of the third embodiment, a new phase shift amount is set in the first variable phase shifter 41 and the optimum value to be set is set. The received signal received by the first antenna element 11 is also used when determining the amount of phase shift and in-phase combining the signals transmitted by the terminal station.

  The operation of the fourth embodiment will be described in more detail. FIG. 10 is a flowchart showing the operation of the adaptive array antenna.

  Steps S1001 to S1011 shown in FIG. 8 are performed in the same procedure as in the third embodiment. Subsequently, the first variable phase shifter 41 is set by the first phase shift amount setting means 371 by changing the phase shift amount Φ1 currently set in the first variable phase shifter 41 by 180 degrees. (Step S1101). Subsequently, the signal selection means 75 sets the first signal blocking means 711 to the passing side (step S1102).

  Through the above processing, the phases of the received signals whose phases are controlled by the second to n-th variable phase shifters 42 to 4n become the same, and the signal transmitted from the terminal station can be in-phase combined by the combiner 5.

  As described above, according to the fourth embodiment of the present invention, the received signal received by the first antenna element 11 is also used when the signals transmitted from the terminal station are subjected to in-phase synthesis, thereby directing the terminal station. The sex gain can be increased.

(Fifth embodiment)
Next, a fifth embodiment of the present invention will be described. FIG. 11 is a configuration diagram of an adaptive array antenna according to the fifth embodiment of the present invention.

  The fifth embodiment is different from the third embodiment in the configuration using a variable gain circuit and gain control means. In FIG. 11, 1101 to 110n amplify the reception signals whose phases are controlled by the variable phase shifters 41 to 4n according to the control signals input from the outside, and input the amplified reception signals to the synthesizer 5. The first to n-th variable gain circuits 110 are configured to receive the received signals amplified by the first to n-th variable gain circuits 1101 to 110n based on the strength of the received signals detected by the signal strength detecting means 7, respectively. This is gain control means for setting the gains of the variable gain circuits 1101 to 110n so that the intensities are equal. Since the other configuration is the same as that of FIG. 7 showing the configuration of the third embodiment, the same reference numerals are assigned and redundant description is omitted.

  The operation of the adaptive array antenna configured as described above will be described in more detail. FIG. 12 is a flowchart showing the operation of the adaptive array antenna.

  First, the operations in steps S1001 to S1004 shown in FIG. 8 are performed in the same procedure as in the third embodiment. Subsequently, the first to nth signal blocking means 711 to 71n are set to the blocking side by the signal selection means 75 (step S1201).

  The feature of the fifth embodiment is that the received signals amplified by the first to nth variable gain circuits 1101 to 110n have the same intensity based on the signal strength of the received signal detected by the signal strength detecting means 7. Thus, the gain control of the variable gain circuits 1101 to 110n is performed. The gains set in the first to nth variable gain circuits 1101 to 110n are set by the gain control means 110 one by one. Here, a method for setting the gain of the first variable gain circuit 1101 will be described.

  The signal selection means 75 sets the first signal blocking means 711 to the passing side, and notifies the gain control means 110 of this (step S1202). In this state, the strength Q of the received signal detected by the signal strength detection unit 1007 is input to the gain control unit 110 (step S1203). Based on this, the gain of the first variable gain circuit 1101 is set by the gain control means 110 so that the intensity of the received signal amplified by the first variable gain circuit 1101 becomes a specified value (step S1204). Subsequently, the signal selection means 75 sets the first signal cutoff means 711 to the cutoff side (step S1205). Subsequently, the gains of the second to nth variable gain circuits 1102 to 110n are set in the same procedure.

  Subsequently, steps S1005 to S1011 shown in FIG. 8 are performed in the same procedure as in the third embodiment.

  In the third embodiment, the signal strength of the received signal received by each antenna element is described as being the same. However, the signal strength of the received signal received by each antenna element may be different due to the influence of the reflection of the signal transmitted from the terminal station or the deviation of the amplifier connected to each antenna element. In this case, as shown in FIG. 13, the signal strength of the received signal shown in FIG. 9 does not have a sharp characteristic at the minimum point, and phase alignment with high accuracy cannot be performed between antenna elements.

  On the other hand, in the fifth embodiment, the first to nth variable gains are determined before the operation of determining the optimum phase shift amount even if the signal strengths of the received signals received by the respective antenna elements are different. Since the gain control of the variable gain circuits 1101 to 110n is performed so that the intensity of the reception signals amplified by the circuits 1101 to 110n becomes equal, the minimum point of the signal intensity of the reception signals again has a sharp characteristic as shown in FIG. As a result, it is possible to perform phase alignment with high accuracy between the antenna elements.

  A method of measuring signal strengths respectively amplified by the variable gain circuits 1101 to 110n by providing signal strength measuring means after the variable gain circuits 1101 to 110n is also conceivable.

(Sixth embodiment)
Next, a sixth embodiment of the present invention will be described. FIG. 14 is a configuration diagram of an adaptive array antenna according to the sixth embodiment of the present invention.

  The sixth embodiment is different from the third embodiment in that the first signal strength storage unit, the second signal strength storage unit, and the phase shift amount calculation unit are used. In FIG. 14, the phase shift amount control means 3 is a first signal strength storage means 141 that stores the first strength P1 of the received signal detected by the signal strength detection means 7 in the state where the desired wave and the interference wave exist. Any one of the second signal strength storage means 142 that stores the second strength P2 of the received signal detected by the signal strength detection means 7 in the presence of only the interference wave, and the signal blocking means 711 to 71n. With one set on the passing side and the rest set on the blocking side, the phase shift amount that minimizes the difference “P1−P2” is calculated based on the first intensity P1 and the second intensity P2. And a phase shift amount calculation means 331. Since other configurations are the same as those in FIG. 7, the same reference numerals are given and redundant description is omitted.

  The operation of the adaptive array antenna configured as described above will be described in more detail. FIG. 15 is a flowchart showing the operation of the adaptive array antenna. A method for setting the phase shift amount of the second variable phase shifter 42 will be described with reference to FIG. First, steps S1001 to S1006 shown in FIG. 8 are performed in the same procedure as in the third embodiment. Next, the first strength P1 of the received signal detected by the signal strength detection means 7 is input to the first signal strength storage means 141 (step S1301). Subsequently, the base station instructs a desired terminal station to suspend transmission for a certain period, and the terminal station suspends transmission for a certain period according to the instruction (steps S1302 to 1303). In this state, the received signal strength P2 detected by the signal strength detection means 7 is input to the second signal strength storage means 142 (step S1304). Based on this, the phase shift amount calculation means 331 calculates the phase shift amount Φ2 that minimizes the difference between the first intensity and the second intensity, that is, “P1−P2” (step S1305). Subsequently, steps S1009 to S1011 shown in FIG. 8 are performed in the same procedure as in the third embodiment.

  In the third embodiment, when calculating the amount of phase shift, it is assumed that only the reception intensity of a signal transmitted from a desired terminal station is detected by the signal intensity detection means 7. Therefore, when other terminal stations are also transmitting simultaneously, the signal strength of the received signal detected by the signal strength detecting means 7 is the signal transmitted from the other terminal station to the received strength of the signal transmitted from the desired terminal station. The received strength is added. In that case, highly accurate phase alignment cannot be performed between the antenna elements.

  On the other hand, in the sixth embodiment, even when there is a signal transmitted by another terminal station, when calculating the amount of phase shift, the reception intensity of the signal transmitted by the other terminal station is detected, Since the influence is removed, highly accurate phase matching can be performed between the antenna elements.

(Seventh embodiment)
FIG. 16 is a configuration diagram of an adaptive array antenna according to the seventh embodiment of the present invention used for transmission. In FIG. 16, the antenna system is set by a modulator 161, a distributor 162 that distributes transmission signals transmitted by the modulator 161, and a phase shift amount control means 3 that will be described later. The variable phase shifters 41 to 4n that perform phase control according to the amount of phase shift, the amplifiers 21 to 2n that amplify the phase-controlled transmission signals, and the signal selection means 75 that will describe these amplified transmission signals later. Signal blocking means 711 to 71n that pass or block to subsequent circuits in accordance with each input control signal, antenna elements 11 to 1n that transmit transmission signals that have passed through these signal blocking means, and terminal stations that communicate with each other The signal strength detection means 7 for detecting the signal strength of the received signal received at the terminal station by the notification of the signal, and the phase shift based on the detected strength of the received signal The phase shift amount control means 3 to be set in each first through variable phase shifters 41~4n of the n the calculated calculated phase shift these, and is composed of.

  The signal strength detected by the signal strength detection means 7 can be obtained, for example, by receiving notification of signal strength information from the terminal station by the receiver 163 and inputting the signal strength information to the signal strength detection means 7. it can. The phase shift amount control means 3 in the seventh embodiment sets any two of the signal blocking means 711 to 71n on the passing side and sets the rest on the blocking side, and the signal blocking means 711 to 71n. The phase shift amount that minimizes the intensity P based on the intensity P of the received signal detected by the signal intensity detection means 7 with any two of these being set to the passing side and the rest set to the blocking side The phase shift amount calculating means 331 for calculating the signal and the signal cutoff means i (1 ≦ i ≦ n) set by the signal selection means 75 among the variable phase shifters 41 to 4n for the calculated phase shift amount. And phase shift amount setting means 371 to 37n for setting to the variable phase shifter i connected to.

  The operation of the adaptive array antenna according to the seventh embodiment configured as described above will be described. FIG. 17 is a flowchart showing the operation of the adaptive array antenna. When a new terminal station starts operation or when an existing terminal station resumes operation after changing its position, the terminal station transmits a first control signal to the base station, and the communication channel If it is free, the base station uses the second control signal to designate one or more communication channels for subsequent transmission / reception (steps S3001 to S3003). Subsequently, the signal selection means 75 sets the first signal blocking means 711 to the passing side and the second to nth signal blocking means 712 to 71n to the blocking side (step S3004).

  The feature of the seventh embodiment is that the phase of the received signal whose phase is controlled by the second to n-th variable phase shifters 712 to 71n based on the signal strength of the received signal detected by the signal strength detecting means 7. In the terminal station, the phase of the transmission signal phase-controlled by the first variable phase shifter 41 is opposite to that of the transmission signal, that is, the phase is controlled by the second to n-th variable phase shifters 42 to 4n. The phase shift amount control is performed so that the phases of the transmission signals are the same at the terminal station. The phase shift amounts set in the second to nth variable phase shifters 42 to 4n are calculated by the phase shift amount control means 3 one by one. Here, a method for setting the phase shift amount of the first variable phase shifter 42 will be described.

  The signal selecting means 75 sets the second signal blocking means 712 to the passing side, and notifies this to the phase shift amount calculating means 331 (step S3005). Subsequently, the base station performs transmission with a constant transmission power on the designated communication channel (step S3006). In this state, the received signal strength P detected by the signal strength detection means 7 is input to the phase shift amount calculation means 331 (steps S3007 to S3008). Based on this, the phase shift amount calculation means 331 calculates the phase shift amount Φ2 that minimizes P (step S3009).

  Subsequently, based on the notification from the signal selection means 75, the phase shift amount Φ 2 calculated by the phase shift amount calculation means 331 is input to the second phase shift amount setting means 372. This phase shift amount Φ2 is set in the second variable phase shifter 42 by the phase shift amount setting means 372 (step S3010). Subsequently, the signal selection means 3032 sets the second signal cutoff means 712 to the cutoff side (step S3010). Subsequently, the same procedure is performed for setting the amount of phase shift of the third to n-th variable phase shifters 43 to 4n.

  Through the above processing, the phase of the transmission signal whose phase is controlled by each of the second to n-th variable phase shifters 42 to 4n is the transmission signal whose phase is controlled by the first variable phase shifter 41 in the terminal station. The relationship between the phase and the opposite phase. Subsequently, the first signal blocking unit 711 is set to the blocking side and the second to nth signal blocking units 712 to 71n are set to the passing side by the signal selection unit 75 (step S3011).

  With the above processing, the phase of the received signal whose phase is controlled by the second to n-th variable phase shifters 42 to 4n becomes the same at the terminal station, and the signal transmitted from the base station can be received in phase at the terminal station. it can. For example, if the calculated amount of phase shift is stored, it can be used when a call is resumed after a call is terminated once.

(Eighth embodiment)
Next, an adaptive array antenna according to an eighth embodiment of the present invention will be described. The configuration diagram of the adaptive array antenna according to the eighth embodiment of the present invention is the same as the configuration of FIG. 16 in the seventh embodiment.

  The eighth embodiment is different from the seventh embodiment in that an optimal phase shift is set by setting a new phase shift amount in the first variable phase shifter 41 after step S3012 of the seventh embodiment. When the amount is determined and the base station transmits, the transmission signal transmitted by the first antenna element 11 is also used.

  The operation of the eighth embodiment will be described in more detail. FIG. 18 is a flowchart showing the operation of the adaptive array antenna.

  Next, steps S3001 to S3012 are performed in the same procedure as in the seventh embodiment. Subsequently, a phase shift amount obtained by increasing the phase shift amount Φ1 currently set in the first variable phase shifter 41 by 180 degrees is transferred to the first variable phase shifter 41 by the first phase shift amount setting means 371. Setting is performed (step S3101). Subsequently, the signal selection means 75 sets the first signal blocking means 711 to the passing side (step S3102).

  With the above processing, the phases of the transmission signals whose phases are controlled by the second to n-th variable phase shifters 42 to 4n are the same in the terminal station, and the directivity gain with respect to the base station can be increased.

  As described above, according to the eighth embodiment of the present invention, when the base station transmits, the directivity gain with respect to the terminal station is increased by using the transmission signal transmitted by the first antenna element 11 as well. be able to.

(Ninth embodiment)
Next, an adaptive array antenna according to a ninth embodiment of the present invention will be described. FIG. 19 is a configuration diagram of an adaptive array antenna according to the ninth embodiment of the present invention.

  The ninth embodiment differs from the seventh embodiment in the configuration using a variable gain circuit and gain control means. In FIG. 19, the adaptive array antenna amplifies the transmission signal distributed by the distributor 162 according to the control signal inputted from the outside, and converts the amplified transmission signal to the variable phase shifters 41 to 4n. The gains of the transmission signals amplified by the variable gain circuits 81 to 8n based on the strength of the received signals detected by the signal strength detection means 7 are made equal at the terminal station. And gain control means 85 for setting the gains of the variable gain circuits 81 to 8n. Since other configurations are the same as those in FIG. 16 showing the seventh embodiment, the same or corresponding components are denoted by the same reference numerals, and redundant description is omitted.

  The operation of the adaptive array antenna configured as described above will be described in more detail. FIG. 20 is a flowchart showing the operation of the adaptive array antenna according to the ninth embodiment. Steps S3001 to S3003 are performed by the same procedure as in the seventh embodiment. Next, the first to nth signal blocking means 711 to 71n are set to the blocking side by the signal selection means 75 (step S3201).

  The feature of the ninth embodiment is that, based on the signal strength of the received signal detected by the signal strength detecting means 7, the strength of the transmission signal amplified by the variable gain circuits 81 to 8n is equalized in the terminal station. The gain control of the variable gain circuits 81 to 8n is performed. The gains set in the first to nth variable gain circuits 81 to 8n are set by the gain control means 85 one by one. Here, a method for setting the gain of the first variable gain circuit 81 will be described.

  The signal selection means 75 sets the first signal blocking means 711 to the passing side, and notifies the gain control means 85 of this (step S3202). Subsequently, the base station performs transmission with a constant transmission power on the designated communication channel (step S3203). In this state, the received signal strength G detected by the signal strength detection means 7 is input to the gain control means 3009 (steps S3204 to S3205). Based on this, the gain of the first variable gain circuit 81 is set so that the intensity of the transmission signal amplified by the first variable gain circuit 81 becomes a specified value by the gain control means 85 (step S3206). Subsequently, the signal selection means 75 sets the first signal cutoff means 711 to the cutoff side (step S3207). Subsequently, the gains of the second to nth variable gain circuits 82 to 8n are set in the same procedure. Finally, steps S3004 to S1012 are performed in the same procedure as in the seventh embodiment.

  In the seventh embodiment, the signal strength of the transmission signal transmitted by each antenna element is assumed to be the same at the terminal station. However, it is also assumed that the signal strength of the transmission signal transmitted from each antenna element differs at the terminal station due to the reflection of the signal transmitted by the base station and the deviation of the amplifier connected to each antenna element. . In that case, highly accurate phase alignment cannot be performed between the antenna elements for the same reason as described in the fifth embodiment.

  On the other hand, in the ninth embodiment, even if the signal strength of the transmission signal transmitted by each antenna element is different, the first to nth variable gain circuits are arranged before the operation of determining the optimum phase shift amount. Since the gain control of the variable gain circuits 81 to 8n is performed so that the intensity of the transmission signals respectively amplified by 81 to 8n is equal in the terminal station, phase alignment with high accuracy can be performed between the antenna elements.

(10th Embodiment)
Next, an adaptive array antenna according to a tenth embodiment of the present invention will be described. FIG. 21 is a configuration diagram of an adaptive array antenna according to the tenth embodiment of the present invention.

  The tenth embodiment differs from the seventh embodiment in that the sixth embodiment shown in FIG. 14 on the receiving side has the same configuration as the fifth embodiment shown in FIG. A signal intensity storage unit 141 and a second signal intensity storage unit 142 are provided, and a phase shift amount calculation unit 331 that calculates a phase shift amount based on the first and second phase shift amount storage units 141 and 142. It is in the composition using. In FIG. 21, the adaptive array antenna includes a first signal strength storage unit 141 that stores the strength P1 of the received signal detected by the signal strength detection unit 7 while the base station is transmitting, and the base station transmits the signal. Any one of the second signal strength storage means 142 for storing the strength P2 of the received signal detected by the signal strength detection means 7 and the first to n-th signal blocking means 711 to 71n are passed. A phase shift amount calculation means 331 for calculating a phase shift amount that minimizes the difference “P1−P2” based on P1 and P2 while the other is set to the shut-off side. ing. Since other configurations are the same as those in FIG. 16, the same or corresponding components are denoted by the same reference numerals, and redundant description is omitted.

  The operation of the adaptive array antenna configured as described above will be described in more detail. FIG. 22 is a flowchart showing the operation of the adaptive array antenna. A method for setting the phase shift amount of the second variable phase shifter 42 will be described with reference to FIG. First, the processing in steps S3001 to S3007 shown in FIG. 17 is performed according to the same procedure as in the seventh embodiment. Subsequently, the received signal strength P1 detected by the signal strength detection means 7 is input to the first signal strength storage means 141 (step S3301). Next, the base station notifies the desired terminal station that the transmission is interrupted for a certain period, and the transmission is interrupted for a certain period (step S3302). In this state, the received signal strength P2 detected by the signal strength detection means 7 is input to the second signal strength storage means 142 (steps S3303 to S3304). Based on this, the phase shift amount calculating means 331 calculates the phase shift amount Φ2 that minimizes the difference “P1−P2” between the strengths P1 and P2 (step S3305). Subsequently, the processing in steps S3010 to S3012 shown in FIG. 17 is performed in the same procedure as in the seventh embodiment.

  In the adaptive array antenna according to the seventh embodiment described above, when calculating the amount of phase shift, it is assumed that only the transmission signal transmitted from the base station is received by the terminal station. Therefore, when other interfering stations are also transmitting at the same time, the signal strength of the received signal detected by the signal strength detecting means 3007 is the received strength of the signal transmitted by the interfering station to the received strength of the signal transmitted by the base station. Will be added. In this case, highly accurate phase alignment cannot be performed between the antenna elements.

  On the other hand, in the adaptive array antenna according to the tenth embodiment, even when there is a signal transmitted by the interfering station, the reception intensity at the terminal station of the signal transmitted by the interfering station when calculating the phase shift amount. Is detected and its influence is removed, so that highly accurate phase alignment can be performed between the antenna elements.

(Eleventh embodiment)
Next, an eleventh embodiment of the present invention will be described with reference to FIG. FIG. 23 is a diagram showing an adaptive array antenna according to the eleventh embodiment.

  Considering a time zone in which the radio base station 2301 and the terminal station 2302 communicate, a constraint condition that directs null is added to another radio base station 2303 that is in the same direction as the terminal station 2302 from the radio base station 2301. Of the other radio base stations, those that are relatively close to the base station 2301 and within the angular range of variable directivity of the adaptive array antenna installed in the base station 2301 2304, 2305, 2306, 2307, 2308, 2309, 2310 Is characterized in that an algorithm for controlling the beam is applied by adding a constraint condition in which the null is directed.

  In particular, in the case of a subscriber radio access system, an interference signal from a terminal that communicates with another base station is generated in bursts at unpredictable random timing, and in many cases, the number of transmission symbols is several tens of symbols. From a few hundred symbols to a few hundreds of microseconds to a few tens of microseconds. As in the conventional control method, the interference signal from the terminal in another cell and its arrival direction are sequentially detected by the own base station, and digital signal processing or the like is used to direct null toward the terminal direction. To perform the control, a very high signal processing speed is required. On the other hand, in the case of the adaptive array antenna according to the eleventh embodiment, the direction in which the interference wave arrives is obtained by acquiring the position information of other base stations in advance and the terminal using the directional antenna. The direction of the terminal station that communicates with the base station is detected at the initial call stage, or the position information of other base stations is cited from a pre-registered database. By doing so, the restraining direction of the null can be determined promptly. Thereby, the advantage that the control processing during communication can be reduced is obtained. In addition, during the communication with the terminal, there is no particular need to change the beam control for the slot allocated to the terminal, so that the calculation process for the control during the communication is compared with the method of sequentially detecting the interference wave. It also has the advantage that the amount is very small.

  In general, in the case of a cellular radio communication system using TDD (Time Division Duplex), when TDMA (Time Division Multiple Access) synchronization between base stations is not taken, transmission from other base stations at the same frequency Since a wave causes interference, a method of detecting the arrival direction of the interference wave from the base station according to the level of the interference wave and adaptively suppressing it is conceivable. In contrast to such a scheme, the adaptive array antenna according to the eleventh embodiment can be applied to a case where FDD (Frequency Division Duplex) is used as a duplex scheme, and has a specific effect that simple control is possible. is doing. It should be noted that in the case of a wireless communication system using FDD as a duplexing method, the frequency transmitted from the base station is a cause of interference in reception of the base station even if time division multiplexing is not synchronized between the base stations. Therefore, in the conventional algorithm for preventing interference, there is no additional constraint on the direction of other base stations. Even in a system using FDD, when a directional antenna is used on the terminal side, signals from individual interfering terminals can be obtained by using constraint conditions in the direction of other base stations as in the control method of the eleventh embodiment. Therefore, it is possible to control at a very high speed.

  As is clear from FIG. 23, the base stations 2304 and 2305, 2306 and 2307, 2309 and 2310 are located in directions close to each other when viewed from the base station 2301. In such a case, it is estimated that among other base stations, the level of the interference wave is the highest including the gain, distance of the adaptive array antenna, propagation conditions such as the line-of-sight status to the corresponding base station, etc. Only the direction of possible base stations is added to the constraint condition, or the above-mentioned conditions of multiple base stations are weighted and averaged as the constraint condition, or approximately the center of both ends of the multiple base station directions The constraint condition can be reduced by using a method such as the above.

  Note that there is a low probability that a terminal communicating with a distant base station will cause interference. In general, the number of nulls that can be formed by an array antenna having the number N_el of antenna elements is limited to N_el. Therefore, the direction in which the constraint condition is set is N_el or less, and it can be estimated that the level of the interference wave increases including the propagation condition such as the gain of the adaptive antenna, the distance, the line-of-sight condition to the corresponding base station, if necessary. It is appropriate to set a constraint condition preferentially from the base station. Therefore, in the case of the eleventh embodiment, no constraint condition is provided for 2311, 2312, 2313, and 2314 among the other base stations.

  In the eleventh embodiment, a null is not directed toward another base station 2303 located in a direction close to the direction of the terminal 2302 that is communicating as viewed from the base station 2301. On the other hand, since control information is generally not exchanged between base stations, the relationship between the position of a terminal communicating with the base station 2301 and the position of a terminal communicating with the base station 2303 is random. For example, as shown in FIG. 24, while the terminal 1402 is communicating, the antenna directivity of the value terminal 5216 is not suitable for the base station 2401 while the base station 2403 and the terminal 2416 are communicating. Interference waves are not a problem. Also, as shown in FIG. 25, while the terminal 2502 is communicating, while the base station 2503 and the terminal 2516 happen to be in communication, the antenna directivity of the terminal 2516 is suitable for the base station 2501. The transmission signal of terminal 2516 is an interference wave. However, when the sector antenna is used as shown in FIG. 38 or FIG. 39 in the related art, the communication is directed while communicating with other base stations (for example, 3504, 3505, 3506, 3507, 3508, 3509, 3510). In the case of the eleventh embodiment, the terminal station transmitting by the directional antenna receives interference from all terminals in the position range 3515 that causes interference with the base station 3501. It has the advantage of not receiving interference from a terminal communicating with a station.

As for the method of knowing the direction of other radio base stations, it is conceivable to register the positional relationship with other existing radio base stations or the direction of other radio base stations in advance when setting the radio base station. In addition, when a new radio base station is installed, the position information of the new radio base station is notified to each radio base station as control information from the control station that supervises a plurality of radio base stations. It is conceivable that the positional relationship with the own radio base station is calculated from the position information as necessary and added to the existing registration. In addition, when installing a new radio base station, use a radio station that can transmit a control burst for registering a new base station at the reception frequency of the base station, such as a modified radio station for a terminal, for an existing base station. When a control burst for new base station registration is transmitted and the existing known station recognizes the control burst as new base station registration, the direction and propagation conditions of the new base station are determined from the transmitted signal and its signal strength. It is conceivable to detect and register a new base station, and calculate and register the priority order and the direction when providing a null constraint condition. As a method for determining whether or not the difference between the direction of a certain base station and the direction of a terminal that communicates (here, δθ) is small, for example, the following various methods are conceivable. For example, if the directional beam width of the terminal is θ_t, as shown in FIG. 26, the range of the position of the terminal station that communicates with another base station 2603 that interferes with its own base station 2601 is This is a range 2615 included in an angle θ_t centered on a line opposite to the base station 2601 from the base station 2603 in the straight line within the radio zone of the station 2603 and passing through the base stations 2601 and 2603. The angle θ_i for viewing this range 2615 from the base station 2601 is obtained by using the distance d_BB between the base station 2601 and the base station 2603 and the radius r_z of the radio zone of the base station 2603,
θ_i = 2 × arctan {((r_z) × tan ((θ_t) / 2)) / ((r_z) + (d_BB)))}
As required. Therefore,
δθ <θ_iθ × 0.5
Is used as a criterion for determining whether or not the difference δθ between the direction of a certain base station and the direction of a terminal that performs communication is small, it is possible to determine whether or not the direction of the terminal that performs communication is within the interference range .

In addition, as a method of obtaining an approximation of the above θ_i, as shown in FIG. 26, when base stations are arranged almost regularly, using the radio zone radius r_g of the average target system, By approximating r_z = r_g, d_BB = 3 × r_g,
θ_i ′ = 2 × arctan {tan ((θ_t) / 2)) / 4}
Can be used as an approximate value of θ_i. There is no need to consider the distance between base stations, and there is an advantage that interference waves can be removed.

From FIG. 26, clearly
θ_t> θ_i
Therefore, as a simpler method than the above method, if the directional beam width θ_t of the terminal is used as the threshold value, the angle tends to be slightly widened, but the distance between the base stations and the base station There is no need to consider the size of the wireless zone, and there is an advantage that interference waves can be removed.

  As already described, when the number of elements of the adaptive array antenna is limited, the number of nulls that can be formed is limited. In general, the number of nulls that can be formed by an array antenna having N_el elements is at most N_el. In this case, using a standard such as one that is close to the base station, the direction of the base station to which more terminal stations are connected, or one in which the angular directions are separated from each other, It is conceivable that at most N_el directions are selected and a constraint condition for directing null is used.

  In addition, when the directional beam width θ_t of the antenna element is relatively narrow, the angular width at which the beam as the broadside array antenna can be shaken is approximately θ_t. Therefore, it is desirable to exclude the direction to the base station in the direction outward from this angle from the direction of the base station group of the eleventh embodiment.

  In the eleventh embodiment, for example, considering the frame configuration as shown in FIG. 27, the case where the base station adaptive array antenna is used for transmission / reception of data packets communicated in the up payload window has been described. The method may be applied to transmission / reception of control packets in the rising control window. In other words, when applying to the rising control window, for example, when there are n directions where null constraint conditions should be provided due to other base station direction relationships, a plurality of radiation patterns created by removing some of them are prepared. To do. At this time, when a certain direction is picked up, at least one of the plurality of patterns is set in such a combination that the null does not face in that direction. Then, by appropriately switching the plurality of patterns for each slot in the rising control window in which the control channel can be transmitted, it is possible to receive all the control signals from the terminals in the own cell while reducing interference. It becomes possible. In particular, when there is a lot of traffic in a specific neighboring cell, in order to avoid interference from the terminal of this neighboring cell, the number of slots for directing a null to the base station of this neighboring cell is slightly increased, and this time zone interference There is an advantage that a control signal from a terminal existing in this direction can also be received by increasing the throughput by increasing the level and providing a slot in which the null is not directed to the base station of this adjacent cell.

(Twelfth embodiment)
Next, an adaptive array antenna according to a twelfth embodiment of the present invention will be described with reference to FIG. FIG. 28 shows the configuration of the twelfth embodiment. As shown in FIG. 28, the adaptive array antenna according to the twelfth embodiment includes a plurality of antenna elements and a high frequency circuit connected to each antenna element, and the phase of a local signal applied to the frequency conversion circuit in the high frequency circuit is determined. In the adaptive array antenna, an orthogonal modulator 2812 having a local frequency signal and a control signal as inputs is used as a part of the local signal phase shift circuit 2811 that changes for each high frequency circuit for each antenna element. The circuit includes a coupler 2801 that branches a part of a signal from each antenna element, and a quadrature demodulator 2802 for individual elements to which the signal from the coupler 5601 is input.

  Further, a phase control signal output circuit that outputs a control signal to the quadrature modulator 2812 of the local signal phase shift circuit 2811 and a demodulated signal from the quadrature demodulator 2802 for individual elements are input, and the phase of the input signal to the individual element is input. A plurality of individual element signal sensors for detecting amplitude, a comparison circuit for comparing signals from the plurality of individual element signal sensors and detecting the difference, and the detected difference and antenna supply based on the comparison result. Compensation control means for controlling the output signal of the phase control signal output circuit so as to compensate for a phase difference or the like due to a difference in the wiring length or other wiring length is provided in the phase shift amount / amplitude weight calculation circuit 2813. It is also a feature.

  Further, among the second IF signals from the plurality of individual elements, a first RSSI circuit for monitoring one signal level (coupler 2820 for extracting a certain percentage of signal power of the signal, Including an RSSI output circuit 2821 composed of a logarithmic amplifier to be amplified and an ADC that converts the output into a digital value), and a second RSSI circuit (after synthesis) that monitors the signal level of the second IF signal after synthesis. A RSSI output circuit 2823 including a coupler 2822 for extracting a certain ratio of signal power of the signal of, a logarithmic amplifier for amplifying the extracted signal and an ADC for converting the output to a digital value), and N first IF variable gain amplifiers 2816 and N second IF variable gains that make the relative levels of all IF signals of the individual elements variable. Based on the RSSI signals from the amplifier 2815, the combined variable gain amplifier 2825 that changes the signal level of the second IF signal after combining the signals from the individual elements, and the RSSI signals from the first RSSI circuit and the second RSSI circuit. The first IF variable gain amplifier 2816 and the second IF variable gain amplifier 2815 are combined so that the output signal level of the first IF variable gain amplifier 2816 is controlled to a certain width and the high frequency circuit elements for the individual elements are not saturated. It also has an AGC control circuit 2824 for controlling the post-variable gain amplifier 2825. The RSSI is an abbreviation for Receive Signal Strength Indication and is a numerical value of the strength of the received radio signal.

  Further, in order to reduce a clock recovery circuit that is generally complicated and requires a high-speed circuit such as oversampling with respect to the baud rate, the output of the clock recovery circuit 2828 mounted on the receiver 2819 is changed as necessary. A clock timing adjustment circuit 2827 that compensates for internal delays of the receiver 2819, the combined output demodulation circuit 2829, and the weight determination individual element demodulation circuit 2803, and adjusts the timing to supply the eye with the highest aperture ratio. Is also supplied to the ADC 2826 of the combined output demodulation circuit 2829 and the plurality of ADCs 2809 of the weight determination individual element demodulation circuit 2803.

  As a result, it is not necessary to apply oversampling to the post-combination output demodulation circuit 2829 and the weight determination individual element demodulation circuit 2803, and the ADC sampling rate can be lowered, so that the power consumption can be reduced. is there.

  In general, the output frequency of the clock recovery circuit is approximately equal to the baud rate. However, depending on the modulation method and the like, it may be preferable to perform oversampling of a relatively small multiple on the ADC 2826 and the plurality of ADCs 2809. In this case, a frequency that is a multiple of the baud rate may be output from the clock recovery circuit 2828. Instead of being provided in the clock recovery circuit and receiver 2819, it may be provided in the post-combination output demodulation circuit 2829 or in the weight determination individual element demodulation circuit 2803.

  With these configurations, in the case of a DBF (Digital Beam Forming) type adaptive antenna, if the transmission rate becomes fast, such as 1 Mbaud or more, which is being studied in the PTMP system, very fast digital signal processing is required for real-time reception. Whereas the adaptive array antenna according to the twelfth embodiment has a problem that it is necessary, the actual signal weighting and synthesis are performed by the local signal phase circuit 2811, the amplitude weight weighting circuit 2817, and the high frequency adder 2818. Therefore, even if a very high transmission rate is used, real-time reception can be performed by an ordinary receiver 2819.

  In addition, a high-frequency circuit constituting the array antenna, for example, a special additional circuit (for example, a phase difference due to a difference in phase distortion of an amplifier or a mixer, a routing length of an antenna feeding line or other wiring length) There is no need to provide a high-frequency phase shifter), it is only necessary to correct the digital input value, and the cost can be reduced. In addition, deviations of individual element circuits may occur with respect to a local phase shift circuit using a quadrature modulator. In this embodiment, calibration including the local phase shift circuit can also be performed.

  FIG. 30 shows a configuration example for compensating for the phase difference and amplitude difference in the adaptive array antenna according to the twelfth embodiment described above. A demodulated signal from the weight determination individual element demodulation circuit 2803 is input, and a phase / amplitude comparison circuit 3202 that compares the phase and amplitude of each input signal to detect a difference between them is detected based on the comparison result. In addition, phase control is performed so as to compensate for the phase deviation due to the above-mentioned phase deviation, the difference in the length of the antenna feed line and other wiring lengths, the difference in the passing phase characteristics of the amplitude weight weighting variable gain amplifier 3208 and the combiner 2818, etc. The phase deviation compensation control means 3203 for controlling the output signal of the signal output circuit, and the phase deviation compensation output from the phase deviation compensation control means 3203 and the phase shift amount / amplitude weight calculation circuit 3205 are output from the local signal phase shift circuit. Based on the comparison result of the phase shift control signal output circuit 3204 for outputting the control signal to the quadrature modulator and the phase shift / amplitude comparison circuit 3202, the detection is performed. AGC / amplitude deviation compensation circuit so as to compensate for amplitude deviation due to differences in amplitude deviation, antenna feed line routing length, other wiring length, amplitude weight weighting variable gain amplifier 3208 and pass amplitude characteristics of combiner 2818, etc. And amplitude deviation compensation control means 3206 for controlling an output signal from 3201 to the second IF / AGC control and amplitude deviation compensation circuit 2814.

  In general, components constituting an RF / IF circuit, a local phase shift circuit, and the like for each antenna element of an adaptive array antenna have variations in gain, loss, phase characteristics accompanying signal passage, and the like. Deviations in the amplitude and phase of each antenna element system due to this variation cause an error in the radiation pattern characteristics by controlling the amount of phase shift and amplitude weight.

  If the deviation of the amplitude and phase of each antenna element system is measured at the time of manufacturing the antenna and every certain period of time during operation, and if the deviation can be compensated, the error of the radiation pattern can be suppressed. .

  For example, at the time of manufacturing, each antenna element system is configured by inputting a signal having the same phase and amplitude to each antenna input by a distributor or the like, or transmitting a radio wave from a sufficiently distant position in the boresight direction in an anechoic chamber or the like. The phase / amplitude comparison circuit 3202 detects the phase deviation and amplitude deviation of the input from. The comparison result is input to the phase deviation compensation control means 3203 and the amplitude compensation control means 3206, and these means obtain the phase deviation and the phase shift amount and the amplitude adjustment amount for compensating the amplitude deviation. The phase shift amount for phase deviation compensation and the phase shift amount for controlling the radiation pattern of the antenna output from the phase shift amount / amplitude weight calculation circuit 3205 are added by the phase control signal output circuit 3204. The signal is converted into a control signal to be output to the quadrature modulator of the local signal phase shift circuit. The obtained amplitude adjustment amount for compensating for the amplitude deviation and the amplitude adjustment amount for performing the AGC are added by the AGC / amplitude deviation compensation control circuit 3201, and the second IF / AGC control and amplitude deviation compensation circuit 2814 is added. It is converted into a digital signal for variable gain and output. By these control methods, errors in the radiation pattern can be suppressed.

  In addition, during operation, each antenna element that receives a signal from a specific transmission station whose position is known in advance at a timing when a signal from another transmission station does not arrive as much as possible and is predicted from the direction of the specific transmission station By detecting the deviation from the phase difference of the input from the system and the amplitude deviation of the input by the phase / amplitude comparison circuit 3202, compensation can be performed by the same method as described above.

  Depending on the format of the IF frequency converter 3207, the output level of the conversion number of the IF frequency converter 3207 may be changed depending on the output level of the local signal phase shift circuit 2811. In this case, the phase deviation and amplitude deviation are fetched from the phase / amplitude comparison circuit 3202 into the phase / amplitude deviation compensation control means provided in a place corresponding to the phase deviation compensation control means 3203 without using the amplitude compensation control means 3206, and transferred. The phase amount and the amplitude adjustment amount are obtained, and the radiation of the antenna output from the phase shift amount / amplitude weight calculation circuit 3205 by the phase shift / amplitude control signal output circuit provided at the place corresponding to the phase shift control signal output circuit 3204 is obtained. The phase shift amount for controlling the pattern and the phase shift amount for deviation compensation obtained as described above are added, and I and Q to each of the N quadrature modulators are added according to the amplitude adjustment amount. It is also conceivable to compensate for amplitude deviation and phase deviation by adjusting the input. In this example, it is also conceivable that the amplitude compensation control means 3206 is used in combination and the compensation amount of the amplitude deviation is distributed and controlled by the phase / amplitude deviation compensation means and the amplitude compensation control means 3206.

  FIG. 31 shows another configuration example for compensating for the above phase difference and amplitude difference. 31 differs from FIG. 30 in that the output of the amplitude compensation control means 3206 is input to the amplitude control signal output circuit 3303 together with the amplitude weight from the phase shift amount / amplitude weight calculation circuit 3205 and added here, and the amplitude The weight weighting and amplitude deviation compensation circuit 3302 is configured to be converted into a digital signal for variable gain and output, and performs phase and amplitude compensation by the same control as the example described in the operation description of FIG. be able to.

  The adaptive array antenna having the configuration shown in FIG. 28 is different from a normal wireless communication device in that it is necessary to monitor both the signal level after combining and the signal level before combining. For example, when the signal from other than the desired terminal is stopped in the cell and the phase shift amount is continuously changed by the phase shifter to search for the null point, the dynamic range of the combined signal level becomes considerably large. On the other hand, it is predicted that the intensity of the signals from the respective antennas before synthesis will be at a substantially constant level. In this case, saturation occurs if the gain of the variable gain amplifier up to the synthesizer is increased just because the level of the received signal after the synthesis is lowered. Therefore, the level of the received signal before synthesis is also monitored, the gain is increased to the extent that saturation does not occur before reaching the combiner, and the remaining shortage is compensated by the gain increase of the variable gain amplifier after synthesis.

  On the other hand, when the synthesis is performed such that the beam direction is directed after the terminal direction can be identified or converged to the optimum weighting factor, the signal strength after synthesis is stable. Fluctuation is reduced. On the other hand, the level of the signal strength from each antenna before combining may decrease due to signal interference from a plurality of terminal stations.

  However, since the transmission signal of wireless communication is generally scrambled so that the line spectrum does not stand, it can be assumed that the phase of the information signal follows a uniform distribution over a certain period of time. In the case of the PTMP system of the subscriber radio access system, the position of each terminal station does not move in principle. Accordingly, if averaging is performed in a time sufficiently longer than the symbol duration (reciprocal of the transmission symbol rate Ts [Hz]) in the RSSI circuit, the phase difference between the plurality of transmission signals becomes a random uniform distribution, and the fluctuation of the RSSI output due to interference Is considered to have no effect. In addition, this property is considered to be irrelevant regardless of the output of any of the plurality of antennas. Therefore, it is not always necessary to monitor all input power from a plurality of elements. As shown in FIG. 28, if a coupler 2820 and an RSSI circuit 2821 for monitoring at least one of the inputs are used, each antenna is monitored. Can be estimated.

  The above two RSSI circuits are used in combination, and the gains of the three sets of variable gain amplifiers 2816, 2815, and 2825 are adjusted based on the two monitoring results. That is, the AGC control circuit 2824 prepares a table for obtaining three gain adjustment voltage outputs for two inputs.

  FIG. 29 shows an example of an AGC voltage control method for a certain terminal in the case of using the adaptive array antenna of the twelfth embodiment. Note that the gain increase and decrease ranges in FIG. 28 are generally set to be almost the same as the difference between the desired lower limit value and the desired upper limit value, but in order to simplify the control although the convergence is slow, A method of stepwise control with a predetermined constant value that is smaller than a desired value range is also conceivable. By performing the control as described above, it is possible to control the combined output signal level to be a constant width, and to control so that the high-frequency circuit element for each individual element is not saturated. can get.

  In general, the combined receiver 2819 is provided with an input fluctuation margin of about ± 2 dB. Therefore, it is conceivable to provide hysteresis so that the gain adjustment function reacts sensitively with fluctuations much smaller than this and the gain is not changed too often. Specifically, a certain number of past output values of the RSSI circuit is stored, and only when the deviation from the certain value exceeds a certain value, the AGC control circuit 2824 and the first IF variable gain amplifier 2816 When a limitation is made to output a gain change command to the IF variable gain amplifier 2815 and the synthesized variable gain amplifier 2825, slight fluctuations in signal level due to noise components of the RSSI circuit and minute fading of the input RF signal Therefore, the AGC control circuit 2824 reacts excessively, and since it is originally within the allowable reception power range of the receiver 2819, unnecessary control can be prevented.

  Also, in the case where the phase shift amount is continuously changed by the phase shifter and the properties of the received signal after the synthesis are measured at that time, the speed of change of the phase shift amount is sufficiently higher than the RSSI time constant. It is desirable to slow down. If the RSSI time constant is set to a certain value, the measurement speed may be reduced. In that case, a mode for changing the RSSI time constant may be provided.

(13th Embodiment)
Next, an adaptive array antenna according to a thirteenth embodiment of the present invention will be described in detail with reference to FIG.

  The adaptive array antenna of the thirteenth embodiment includes a plurality of antenna elements 11 to 1n, a high-frequency circuit 30 connected to each antenna element, and a high-frequency distribution circuit 162 that distributes output to the plurality of high-frequency circuits. The high-frequency circuit 30 includes an amplitude weighting circuit 31 that performs amplitude weighting for each antenna element, and a local signal phase shift circuit 32 that performs phase weighting. The second IF signal before distribution to individual elements is provided. A pre-distribution variable gain amplifier 33 that makes the signal level variable, N second IF variable gain amplifiers 34 that can change the relative levels of the second IF signals of the N individual elements, and the amplitude weight weighting circuit. The effective radiated power in consideration of the directivity gain from the adaptive array antenna estimated from the output of 31 does not exceed a predetermined value. A gain control circuit 35 for controlling the pre-distribution variable gain amplifier 33 and the N second IF variable gain amplifiers 34 so that the high frequency circuit elements for the individual elements are not saturated. It is characterized by having.

  FIG. 33 shows an example of an AGC voltage control method for a certain terminal in the case of using the adaptive array antenna of the thirteenth embodiment. It is also conceivable to use the N second IF variable gain amplifiers 34 after distribution in FIG. 32 as a circuit that performs amplitude weighting of each antenna element. In this case, the gain control voltage written in the gain setting value table of the pre-distribution variable gain amplifier and the N second IF variable gain amplifiers corresponding to the desired ERP value in FIG. Even when the upper and lower limits of the variable range are taken into account, the control voltage must be such that the gain is such that distortion due to NF deficiency or saturation does not occur. If this condition cannot be satisfied at the same time, in addition to the gain setting value table, the upper and lower limits of the gain variable range as the allowable amplitude weight are prepared as a table for the desired ERP value. If it is important to prevent distortion due to shortage or saturation, it may be possible to refer to this table when determining the amplitude weight and change the amplitude weight so that it falls between the upper and lower limits.

  By the method described above, it is possible to obtain an effect that it is possible to simultaneously realize an effective radiated power value of a predetermined value or less and a low distortion of the high frequency circuit for each individual element. In addition, when it is necessary to greatly increase the control range of transmission power, a large control range is required with only one variable gain amplifier, so it is difficult to achieve input / output isolation for increasing the gain. Or the structure may be complicated because the variable gain amplifier has an attenuation function. Such a problem also has an advantage that it can be avoided by dividing the variable gain element before and after the distribution as in this embodiment.

  In the thirteenth embodiment, the amplitude weight weighting circuit 31 and the N second IF variable gain amplifiers 34 are separately provided. However, it is conceivable that the two are realized by a single circuit. . In this case, there is an advantage that the circuit scale for taking the necessary transmission power control width can be further reduced, and the above-described problems such as isolation and attenuation functions can be solved.

(14th Embodiment)
Next, an adaptive array antenna according to a fourteenth embodiment of the present invention will be described in detail with reference to FIGS. In addition, since this invention has demonstrated about the detailed content of invention using many embodiment, when the code | symbol in drawing used for 14th Embodiment overlaps the code | symbol used in drawing of other embodiment However, the reference numerals used in FIGS. 34 to 36 are limited to those used in the fourteenth embodiment.

  34, reference numerals 11 to 1n denote antenna elements, and 21 to 2n denote a plurality of real number weighting means for weighting received signals received by the antenna elements 11 to 1n with real number weights set by real number weight control means 7 described later. Reference numerals 31 to 3n denote a plurality of individual element signal strength detecting means for detecting the weighted received signal strengths as individual element signal strengths. Reference numeral 4 denotes a synthesizer that synthesizes the reception signals weighted by the real number weighting means 21 to 2n, reference numeral 5 denotes a demodulator that demodulates the reception signal synthesized by the synthesizer 4, and reference numeral 6 denotes This is signal strength detection means for detecting the strength of the received signal synthesized by the synthesizer 5 as the synthesized signal strength.

  Reference numeral 7 calculates a real number weight to be newly set based on the individual element signal intensity detected by the individual element signal intensity detection units 31 to 3n and the combined signal intensity detected by the combined signal intensity detection unit 6, respectively. The real number weight control means repeats the process of setting the calculated real number weights in the weighting means 21 to 2n for a plurality of cycles.

The real number weight control means 7 stores a plurality of initial value memories for storing initial values W_1 (0) to W_n (0) (n is the number of antenna elements) of real number weights set in the plurality of real number weighting means 21 to 2n. When the means 711 to 71n and the real weight control means 7 are operated for the first time, the real number weights W_1 (k) to be set in the respective real number weighting means 21 to 2n with these W_1 (0) to W_n (0). ~ W_n (k) (k is the number of times of updating the real number weight) and a plurality of real number weight storage means 721 to 72n, and W_1 (k) to W_n () stored in the plurality of real number weight storage means 721 to 72n. k), one of W_i (k) and −W_i (k) (1 ≦ i ≦ n) is used as the real number weight of the plurality of real number weighting units 21 to 2n. A plurality of real number weight setting units 731 to 73n to be set and a plurality of real number weighting units 21 to 2n are respectively detected by the combined signal intensity detection unit 6 in a state where W_1 (k) to W_n (k) are set. The combined signal strength Py (k) is input, and similarly, the plurality of individual element signal strength detection means in a state where W_1 (k) to W_n (k) are set by the plurality of real number weighting means 21 to 2n, respectively. The individual element signal strengths Px_1 (k) to Pxn (k) detected by 31 to 3n are respectively input, and W_1 (k), W_2 (k),. .., W_i-1 (k), W_i (k), W_i + 1 (k),..., W_n (k) (1 ≦ i ≦ n) are detected by the combined signal intensity detection means 6 respectively. The combined signal strength Py_i (k) (1 ≦ i ≦ n) is at each entered a new real weight ^{W_i (k + 1) = W_i} (k) + a * [Px_i (k) + {Py (k) −Py_i (k)} / 4] / W_i (k) (a is a constant) and (1 ≦ i ≦ n) are calculated, and W_1 (k) to W_n (in the plurality of real weight storage means 721 to 72n). k) is further provided with real number weight calculating means 741 to 74n.

  In FIG. 34, the real number weight control means 7 includes an update stop means 75 for stopping the operation based on a predetermined condition.

  The real number weighting means 21 to 2n are configured, for example, as shown in FIG. In FIG. 35, the real number weighting means 21 (2n) includes an absolute value detection means 211 for calculating the absolute value of the real number weight W_i (k), a code detection means 212 for calculating the sign of W_i (k), and an absolute value detection. A variable gain amplifier 213 that amplifies the received signal X_i (t) based on the absolute value calculated by the means 211, and a code for controlling the code of the amplified received signal based on the code calculated by the code detecting means 212 1 A bit phase shifter 214.

  As described above, the weighting of the real number weight can be realized with a simple circuit configuration because a multi-bit phase shifter necessary for the weighting of the amplitude and the phase weight is not used. However, the present invention can also be applied to a circuit configuration that weights amplitude and phase weights.

  The operation of the adaptive array antenna configured as described above will be described with reference to FIG. FIG. 36 is a flowchart for explaining the operation of the adaptive array antenna.

  First, the real number weight W_1 (0) stored in the initial value storage unit 711 is input to the real number weight storage unit 721. Based on this, W_1 (0) is stored in W_1 (0) by the real weight storage means 721 as in the following equation.

W ₁ (k) = W ₁ (0)
Subsequently, the real weight initial values W_2 (0) to W_n (0) stored in the initial value storage means 712 to 71n are similarly stored in the real weight storage means 722 to 72n (steps S1 to S4). .

  Subsequently, the initial value W_1 (k) of the real number weight stored by the real number weight storage unit 721 is input to the real number weight setting unit 731. The real number weight W_1 (k) is set in the real number weighting means 21 by the real number weight setting means 731.

  Subsequently, the real weight initial values W_2 (k) to W_n (k) stored in the real weight storage means 722 to 72n are similarly input to the real weight setting means 732 to 73n, and are sent to the real weight weighting means 22 to 2n. It is set (step S5).

  The real weight initial values W_1 (0) to W_n (0) may be set to maximize the directivity gain in the desired wave direction, for example.

と表される。但し、ｉ：１＜＝ｉ＜＝ｎ，Ｅ［・］：期待値演算である。 At time t, reception signals received by the antenna elements 11 to 1n are X_1 (t) to X_n (t). These signals are weighted by the real number weighting means 21 to 2n. These weighted reception signals are input to the individual element signal strength detection means 31 to 3n. Assuming that the real weights set in the real number weighting means 21 to 2n are W_1 (k) to W_n (k), the individual element signal strengths Px_1 (k) to Px_n detected by the individual element signal strength detection means 31 to 3n, respectively. (K)

It is expressed. However, i: 1 <= i <= n, E [•]: Expected value calculation.

と表される。但し、^＊：複数共役である。 Subsequently, the received signal weighted by the real number weighting means 21 to 2n is synthesized by the synthesizer 4. This combined received signal is input to the combined signal strength detecting means 6. Based on this, the combined signal strength Py (k) detected by the combined signal strength detecting means 6 is

It is expressed. However, ^* : Plural conjugate.

  The feature of the fourteenth embodiment is that the individual element signal intensity detecting means 31 calculates the derivative of the combined signal intensity detected by the combined signal intensity detecting means 6 with respect to the real number weights set in the real number weighting means 21 to 2n. It is a point which can be calculated | required using the separate signal intensity | strength detected by ~ 3n, and the synthetic | combination signal strength detected by the synthetic | combination signal strength detection means 6. Using this differential coefficient, real number weight control based on the steepest descent method is performed.

Hereinafter, the procedure of weight control will be described.
First, the number of real weight updates is set to k = 1 by the update stopping means 75 (step S6).

  Subsequently, the combined signal strength Py (k) detected by the combined signal strength detection unit 6 in a state where W_ (k) to W_n (k) are set in the real number weighting units 21 to 2n, respectively, and the real number weight calculation units 741 to 74n. (Step S7).

  Subsequently, the individual element signal strength Px_1 (k) detected by the individual element signal strength detecting means 31 in a state where W_1 (k) to W_n (k) are set in the real number weighting means 21 to 2n, respectively, is a real number weight calculating means 741. Is input.

  Subsequently, the individual element signal strengths Px_2 (k) to Px_n (k) detected by the individual element signal strength detection units 32 to 3n in a state where W_1 (k) is set in the real number weighting units 21 to 2n, respectively. The real number weight calculating means 741 to 74n are inputted (steps S8 to S11).

Subsequently, -W_1 (k), W_2 (k),..., W_n (k) are assigned to the real weighting means 21 to 2n by the real number weight setting means 731 to 73n, respectively.
The combined signal strength Py_1 (k) detected by the combined signal strength detection means 6 in the state where is set is input to the real number weight calculation means 741.

Subsequently, W_1 (k), −W_2 (k),..., W_n (k) are assigned to the real weighting means 21 to 2n by the real number weight setting means 731 to 73n, respectively.
The combined signal strength Py_2 (k) detected by the combined signal strength detection means 6 in a state where is set is input to the real number weight calculation means 742.

  Subsequently, the combined signal strengths Py_3 (k) to Py_n (k) are similarly input to the real number weight calculation means 743 to 74n (steps S12 to S16).

  Based on these inputs, new real number weights W_1 (k + 1) to W_n (k + 1) respectively set for the real number weighting means 21 to 2n are calculated by the real number weight calculating means 741 to 74n.

First, based on the combined signal strength Py (k), the individual element signal strength Px_1 (k), and the combined signal strength Py_1 (k), a new real weight W_1 (k + 1) to be set in the real number weighting means 21 is calculated as a real number weight. Calculated by means 741 as follows.
W ₁ (k + 1) = W ₁ (k) + a {P _X1 (k) + (P _Y (k) −P _Y1 (k)) / 4} / W ₁ (k)
Where a: real number.
Subsequently, the real weight calculation means 742 to 74n are similarly applied to the combined signal strength Py (k), the individual element signal strengths Px_2 (k) to Px_n (k), and the combined signal strengths Py_2 (k) to Py_n (k). (Steps S17 to S20).

  Subsequently, a new real number weight W — 1 (k + 1) calculated by the real number weight calculation unit 741 is input to the real number weight storage unit 721. Based on this, W_1 (k + 1) is stored as W_1 (k) by the real weight storage means 721 as shown in the following equation.

W ₁ (k) = W ₁ (k + 1)
Subsequently, the new real number weights W_2 (k + 1) to W_n (k + 1) calculated by the real number weight calculation units 742 to 74n are similarly stored in the real number weight storage units 722 to 72n (steps S21 to S24).

  Subsequently, a new real number weight W_1 (k) stored in the real number weight storage unit 721 is input to the real number weight setting unit 731. The real number weight W_1 (k) is set in the real number weighting means 21 by the real number weight setting means 731.

  Subsequently, the new real weights W_2 (k) to W_n (k) stored in the real number weight storage means 722 to 72n are similarly input to the real number weight setting means 732 to 73n and set in the real number weighting means 22 to 2n. (Step S25).

  Next, it is determined by the update stopping means 75 whether the number k of real weight updates is smaller than K. If k is smaller than K, k is incremented by 1, and the processing of steps S7 to S25 is repeated. If there is, the process is terminated (steps S26 to S27).

  By providing the update stop means 75, it is possible to avoid the real weight control means 7 from continuing to operate.

と表される。但し、ｉ：１＜＝ｉ＜＝ｎを満たす整数であり、Ｒｅ｛・｝：実部である。 Here, the processing is terminated by counting the number of repetitions of the real number weight update, but in this case, the operation of the real number weight control means 7 can be terminated within a predetermined time. In addition, a method of ending the processing when W_i (k + 1) −W_i (k) (1 <= i <= n) is equal to or less than a predetermined value may be considered. In this case, the operation of the real number weight control means 7 can be finished in a state where the so-called adaptive algorithm has converged.
(Px_i (k) + (Py (k) −Py_i (k)) / 4) / W_i (k) is

It is expressed. However, i: 1 <= i <= n which satisfies n, and Re {·}: real part.

と表される。 On the other hand, the derivative δPy (k) / δW_i (k) related to the real weight W_i (k) of the combined signal strength Py (k) is

It is expressed.

と等価の処理を行なっていることになる。 From the above, δPy (k) / δW_i (k) = 2 (Px_i (k) + (Py (k) −Py_i (k)) / 4) W_i (k) holds. Therefore, the process of step S18 is

Is equivalent to the process.

  When the real number a is a negative value, the real number weights of the real number weighting units 21 to 2n are updated so as to reduce the combined signal strength of the adaptive array antenna, and finally δPy (k) / δW_i (k) = Since a real number weight that satisfies 0 (1 <= i <= n) is set, if there is an interference wave, it can be suppressed. However, in order to avoid that all real weights become 0, it is necessary to limit the amount of change from the initial value of one or more real weights.

  For example, when applying such real number weight control to a receiving adaptive array antenna of a base station, before giving a communication channel to a terminal station that has requested communication, control the real number weight of the real number weighting means, Real number weights for suppressing co-channel interference are calculated, then the communication channel is given to the terminal station, and the real number weights for suppressing the co-channel interference are set in the real number weighting means 21 to 2n and transmitted by the terminal station A method of receiving a signal is conceivable.

  When the arrival direction of the desired wave is known in advance, a directional antenna or array antenna in the desired wave direction may be used. In the case of a directional antenna, the signal received by each element can be limited by the direction of arrival. In the case of an array antenna, appropriate directivity can be provided, for example, as an orthogonal beam.

  As described above, according to the fourteenth embodiment of the present invention, the plurality of individual element signal intensities detected by the individual element signal intensity detecting units 31 to 3n and the combined signal intensity detected by the combined signal intensity detecting unit 6 are obtained. Since the real weight control based on the steepest descent method can be performed by calculating the derivative with respect to the real weight of the evaluation function, compared to the case of using the demodulated signal of each antenna element as in the prior art, It can be realized with a simple circuit configuration.

It is a block diagram which shows the whole structure of the adaptive array antenna as a basic concept of this invention. It is a block diagram which shows the structure of the adaptive array antenna of 1st Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 1st Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 2nd Embodiment of this invention. It is a block diagram which shows the structure of the error detection means in the adaptive array antenna which concerns on 2nd Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 2nd Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 3rd Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 3rd Embodiment of this invention. It is a characteristic view which shows the change of the receiving strength with respect to the amount of phase shifts in the adaptive array antenna which concerns on 3rd Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna of 4th Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 5th Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 5th Embodiment of this invention. It is a characteristic view which shows the change of the receiving strength with respect to the amount of phase shifts in the adaptive array antenna which concerns on 5th Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 6th Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 6th Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 7th Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 7th Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 8th Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 9th Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 9th Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 10th Embodiment of this invention. It is a flowchart which shows operation | movement of the adaptive array antenna which concerns on 10th Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 11th Embodiment of this invention. In 11th Embodiment, it is a figure which shows the case where the antenna directivity of the terminal which communicates with another base station does not face its own base station, and there is no interference. In 11th Embodiment, it is a figure which shows the case where the antenna directivity of the terminal which communicates with another base station faces the self base station, and interference generate | occur | produces. It is a figure which shows the relationship between the antenna beam width and the threshold value of a difference in direction in the eleventh embodiment. It is a figure which shows the example of a frame structure of a PTMP system. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 12th Embodiment of this invention. It is a figure which shows an example of the control method in the case of using the adaptive array antenna which concerns on 12th Embodiment of this invention. It is a block diagram which shows the structure for compensating the phase difference and amplitude difference in 12th Embodiment. It is a figure which shows the structure different from FIG. 30 in the adaptive array antenna which concerns on 12th Embodiment. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 13th Embodiment of this invention. It is a figure which shows an example of the control method in the case of using the adaptive array antenna which concerns on 13th Embodiment of this invention. It is a block diagram which shows the structure of the adaptive array antenna which concerns on 14th Embodiment of this invention. It is a block diagram which shows the real number weighting means in 14th Embodiment of this invention. It is a flowchart which shows the operation | movement of the adaptive array antenna which concerns on 14th Embodiment of this invention. It is explanatory drawing of WLL of a general PTMP form. It is a figure which shows the interference wave arrival state at the time of using a sector antenna with a half value angle of 120 degree | times. It is a figure which shows the arrival condition of the interference wave in the case of the conventional 4 cell frequency repetition. It is a figure which shows the DBF type adaptive antenna by a conventional example. It is a figure which shows the adaptive antenna by a conventional example which inserts the variable gain amplifier for AGC in the output after a synthesis | combination. It is a figure which shows the adaptive antenna for transmission by a conventional example which inserts a variable gain amplifier before distribution. It is a figure which shows the adaptive antenna for transmission by a conventional example which inserts several variable gain amplifier after distribution.

Explanation of symbols

11 to 1n Antenna element 3 Phase shift amount control means 311 First signal strength storage means 321 Second signal strength storage means 331 Phase shift amount calculation means 341 to 34n First phase shift amount storage means 351 to 35n Second Phase shift amount storage means 361 to 36n Third phase shift amount storage means 371 to 37n Phase shift amount setting means 381 to 38n Initial value storage means 41 to 4n Variable phase shifter 5 Synthesizer 71 Signal strength detection means 8 Update stop means 91 Reference signal generation means 92 Error detection means 7 Real number weight control means 711 to 71n Initial value storage means 721 to 72n Real number weight storage means 731 to 73n Real number weight setting means 741 to 74n Real number weight calculation means 75 Update stop means

Claims (10)

A plurality of antenna elements for receiving a reception signal including a control signal input from the outside and transmitting a transmission signal to the outside, and a circuit in the subsequent stage for each of the reception signal and the transmission signal in accordance with the control signal input from the outside A plurality of signal blocking means provided corresponding to the antenna elements to pass or block to the antenna, and phase control of the received signals that have passed through the plurality of signal blocking means according to a set phase shift amount In order to control the phase of the transmission signal according to the set phase shift amount, a plurality of phase shift means provided corresponding to the antenna element and the reception signal phase-controlled by the plurality of phase shift means are combined. And a signal combining / distributing means for distributing the transmission signal, and the received signal or the transmission based on the strength of the received signal or information inputted with respect to the transmission signal. Information including the phase shift amount control means for calculating the phase shift amount of the signal and setting the calculated phase shift amount in the phase shift means, and the received signal synthesized by the synthesis means or the notification from the communication partner station In an adaptive array antenna comprising: signal strength detection means for detecting the signal strength of the received signal received at the counterpart station by
The phase shift amount control means includes:
A signal selecting means for selectively switching the plurality of signal blocking means so as to set any two of the signal blocking means on the passing side and the rest on the blocking side;
With any two of the plurality of signal blocking means set on the passing side and the rest set on the blocking side, this strength (P) is determined based on the received signal strength (P) detected by the signal strength detecting means. A phase shift amount calculating means for calculating a phase shift amount that minimizes P);
A phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculation means to one connected to the signal blocking means set on the passing side by the signal selection means among the plurality of phase shift means. When,
An adaptive array antenna comprising:   The plurality of antenna elements and the plurality of antenna elements provided corresponding to the antenna elements to pass or block received signals respectively received by the antenna elements to a subsequent circuit according to a control signal input from the outside. And a plurality of phase shift means provided corresponding to the antenna elements to control the phase of the received signal that has passed through the signal cut-off means in accordance with a set phase shift amount. Combining means as the combining / distributing means for combining the reception signals phase-controlled by the phase means, the signal intensity detecting means for detecting the intensity of the combined received signal, and the reception detected by the signal intensity detecting means Phase shift amount control means for calculating the phase shift amount based on the signal intensity and setting the calculated phase shift amount in the phase shift means, respectively. Adaptive array antenna according to claim 1.   Distributing means as the combining and distributing means for distributing the transmission signal, the plurality of phase shifting means for controlling the phase of the transmission signal distributed by the distributing means in accordance with the set phase shift amount, and the phase shifting means A plurality of signal blocking means for passing or blocking a transmission signal phase-controlled by each to a subsequent circuit according to a control signal input from the outside, and for transmitting each of the transmission signals that have passed through these signal blocking means An antenna element provided corresponding to the signal blocking means, the phase shift amount control means for calculating the phase shift amount based on the input information and setting the calculated phase shift amount in the phase shift means, 2. The adaptor according to claim 1, further comprising: the signal strength detection unit configured to detect a signal strength of a received signal received at the partner station based on information including a notification from the partner station of communication. Blanking array antenna. A plurality of antenna elements for receiving a reception signal including a control signal input from the outside and transmitting a transmission signal to the outside, and a circuit in the subsequent stage for each of the reception signal and the transmission signal in accordance with the control signal input from the outside A plurality of signal blocking means provided corresponding to the antenna elements to pass or block to the antenna, and phase control of the received signals that have passed through the plurality of signal blocking means according to a set phase shift amount In order to control the phase of the transmission signal according to the set phase shift amount, a plurality of phase shift means provided corresponding to the antenna element and the reception signal phase-controlled by the plurality of phase shift means are combined. And a signal combining / distributing means for distributing the transmission signal, and the received signal or the transmission based on the strength of the received signal or information inputted with respect to the transmission signal. Information including the phase shift amount control means for calculating the phase shift amount of the signal and setting the calculated phase shift amount in the phase shift means, and the received signal synthesized by the synthesis means or the notification from the communication partner station In an adaptive array antenna comprising: signal strength detection means for detecting the signal strength of the received signal received at the counterpart station by
The phase shift amount control means includes:
First signal strength storage means for storing a first strength (P1) of the received signal detected by the signal strength detection means in a state in which a transmission signal is transmitted by the antenna element;
Second signal strength storage means for storing the second strength (P2) of the received signal detected by the signal strength detection means in a state where no transmission signal is transmitted by the antenna element;
Signal selection means for setting any two of the plurality of signal blocking means to the passing side and the rest to the blocking side;
With any two of the plurality of signal blocking means set to the passing side and the rest set to the blocking side, the difference between them based on the first intensity (P1) and the second intensity (P2) A phase shift amount calculating means for calculating a phase shift amount that minimizes (P1-P2);
A phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculation means to one connected to the signal blocking means set on the passing side by the signal selection means among the plurality of phase shift means. When,
An adaptive array antenna comprising:   The plurality of antenna elements and the plurality of antenna elements provided corresponding to the antenna elements to pass or block received signals respectively received by the antenna elements to a subsequent circuit according to a control signal input from the outside. And a plurality of phase shift means provided corresponding to the antenna elements to control the phase of the received signal that has passed through the signal cut-off means in accordance with a set phase shift amount. Combining means as the combining / distributing means for combining the reception signals phase-controlled by the phase means, the signal intensity detecting means for detecting the intensity of the combined received signal, and the reception detected by the signal intensity detecting means Phase shift amount control means for calculating the phase shift amount based on the signal intensity and setting the calculated phase shift amount in the phase shift means, respectively. Adaptive array antenna according to claim 4.   Distributing means as the combining and distributing means for distributing the transmission signal, the plurality of phase shifting means for controlling the phase of the transmission signal distributed by the distributing means in accordance with the set phase shift amount, and the phase shifting means A plurality of signal blocking means for passing or blocking a transmission signal phase-controlled by each to a subsequent circuit according to a control signal input from the outside, and for transmitting each of the transmission signals that have passed through these signal blocking means An antenna element provided corresponding to the signal blocking means, the phase shift amount control means for calculating the phase shift amount based on the input information and setting the calculated phase shift amount in the phase shift means, The adapter according to claim 4, further comprising: the signal strength detection unit configured to detect a signal strength of a received signal received by the partner station based on information including a notification from the partner station of communication. Blanking array antenna. A plurality of antenna elements and a plurality of signals provided in correspondence with the antenna elements for passing or blocking received signals respectively received by these antenna elements to a subsequent circuit according to a control signal inputted from the outside. A blocking means, a plurality of phase shifting means provided corresponding to the antenna elements to control the phase of the received signal that has passed through the signal blocking means according to a set phase shift amount, and the phase shifting means A synthesizing unit for synthesizing the phase-controlled received signal, a signal intensity detecting unit for detecting the intensity of the synthesized received signal, and a phase shift amount based on the intensity of the received signal detected by the signal intensity detecting unit. An adaptive array antenna comprising: a phase shift amount control unit that calculates and sets the calculated phase shift amount in each of the phase shift units,
The phase shift amount control means includes:
A signal selecting means for selectively switching the plurality of signal blocking means so as to set any two of the signal blocking means on the passing side and the rest on the blocking side;
With any two of the plurality of signal blocking means set on the passing side and the rest set on the blocking side, this strength (P) is determined based on the received signal strength (P) detected by the signal strength detecting means. A phase shift amount calculating means for calculating a phase shift amount that minimizes P);
A phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculation means to one connected to the signal blocking means set on the passing side by the signal selection means among the plurality of phase shift means. When,
An adaptive array antenna comprising: A plurality of antenna elements and a plurality of signals provided in correspondence with the antenna elements for passing or blocking received signals respectively received by these antenna elements to a subsequent circuit according to a control signal inputted from the outside. A blocking means, a plurality of phase shifting means provided corresponding to the antenna elements to control the phase of the received signal that has passed through the signal blocking means according to a set phase shift amount, and the phase shifting means A synthesizing unit for synthesizing the phase-controlled received signal, a signal intensity detecting unit for detecting the intensity of the synthesized received signal, and a phase shift amount based on the intensity of the received signal detected by the signal intensity detecting unit. In an adaptive array antenna comprising: a phase shift amount control unit that calculates and sets the calculated phase shift amount in each of the phase shift units,
The phase shift amount control means includes:
First signal intensity storage means for storing a first intensity (P1) of the received signal detected by the signal intensity detection means in the presence of a desired wave and an interference wave;
Second signal strength storage means for storing a second strength (P2) of the received signal detected by the signal strength detection means in the presence of an interference wave;
Signal selection means for setting any two of the signal blocking means to the passing side and the rest to the blocking side;
In a state where any two of the signal blocking means are set to the passing side and the rest are set to the blocking side, the difference (P1−) based on the first intensity (P1) and the second intensity (P2). A phase shift amount calculating means for calculating a phase shift amount that minimizes P2);
A phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculation means to one connected to the signal blocking means set on the passing side by the signal selection means among the plurality of phase shift means. When,
An adaptive array antenna comprising: Distributing means for distributing a transmission signal, a plurality of phase shifting means for controlling the phase of the transmission signal distributed by the distributing means in accordance with a set phase shift amount, and a transmission signal phase-controlled by these phase shifting means A plurality of signal blocking means for passing or blocking each of the signals to the subsequent circuit according to a control signal input from the outside, and a transmission signal that passes through these signal blocking means is provided in correspondence with the signal blocking means. In an adaptive array antenna comprising: the antenna element provided; and a phase shift amount control unit that calculates a phase shift amount based on input information and sets the calculated phase shift amount in each of the phase shift units,
With signal strength detection means for detecting the signal strength of the received signal received at the partner station by information including notification from the partner station of communication,
The phase shift amount control means includes:
Signal selection means for setting any two of the signal blocking means to the passing side and the rest to the blocking side;
In a state where any two of the plurality of signal blocking means are set on the passing side and the rest are set on the blocking side, the strength (P) of the received signal is detected based on the received signal strength (P). A phase shift amount calculating means for calculating a phase shift amount that minimizes P);
A phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculation means to one connected to the signal blocking means set on the passing side by the signal selection means among the plurality of phase shift means. When,
An adaptive array antenna comprising: Distributing means for distributing a transmission signal, a plurality of phase shifting means for controlling the phase of the transmission signal distributed by the distributing means in accordance with a set phase shift amount, and a transmission signal phase-controlled by these phase shifting means A plurality of signal blocking means for passing or blocking each of the signals to the subsequent circuit according to a control signal input from the outside, and a transmission signal that passes through these signal blocking means is provided in correspondence with the signal blocking means. In an adaptive array antenna comprising: the antenna element provided; and a phase shift amount control unit that calculates a phase shift amount based on input information and sets the calculated phase shift amount in each of the phase shift units,
With signal strength detection means for detecting the signal strength of the received signal received at the partner station by information including notification from the partner station of communication,
The phase shift amount control means includes:
First signal strength storage means for storing a first strength (P1) of the received signal detected by the signal strength detection means in a state in which a transmission signal is transmitted by the antenna element;
Second signal strength storage means for storing the second strength (P2) of the received signal detected by the signal strength detection means in a state where no transmission signal is transmitted by the antenna element;
Signal selection means for setting any two of the plurality of signal blocking means to the passing side and the rest to the blocking side;
With any two of the plurality of signal blocking means set to the passing side and the rest set to the blocking side, the difference between them based on the first intensity (P1) and the second intensity (P2) A phase shift amount calculating means for calculating a phase shift amount that minimizes (P1-P2);
A phase shift amount setting means for setting the phase shift amount calculated by the phase shift amount calculation means to one connected to the signal blocking means set on the passing side by the signal selection means among the plurality of phase shift means. When,
An adaptive array antenna comprising:

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