JP4460746B2

JP4460746B2 - Code division multiplexing communication method and apparatus

Info

Publication number: JP4460746B2
Application number: JP2000307645A
Authority: JP
Inventors: 正和高橋
Original assignee: Kenwood KK
Current assignee: Kenwood KK
Priority date: 2000-10-06
Filing date: 2000-10-06
Publication date: 2010-05-12
Anticipated expiration: 2020-10-06
Also published as: JP2002118536A

Description

【０００１】
【発明の属する技術分野】
本発明は、完全相補系列パイロット支援形符号分割多重通信方法及び装置に関し、特に、送信データを復調する受信装置側において該復調のための回路構成を簡略にできる完全相補系列パイロット支援形符号分割多重通信方法及び装置に関する。
【０００２】
【従来の技術】
移動体通信の通信方式として、符号分割多重（ＣＤＭＡ）通信方式が広く用いられている。符号分割多重通信方式は、周波数分割多重通信（ＦＤＭＡ）や時分割多重通信（ＴＤＭＡ）に比して、同一チャンネル内で多重できる信号の数を極めて多くできる利点があることから、今後も更なる普及が期待されている。
【０００３】
符号分割多重通信においては、完全相補系列を用いた櫛の歯状スペクトル通信方式が広く採用されている。この通信方式では、送信側で、完全相補系列の対を構成する要素系列を直列接続した直列系列を生成し、直列系列の１つにパイロット信号を乗せ、他の対系列にはチップ単位で遅延シフトした遅延シフト系列に送信データ信号を乗せて送信する。例えば、長さが４チップで２個の系列を要素系列とする２対の完全相補系列の後部１チップを前部外側に移動する操作をｋ回（０≦ｋ≦Ｌ−１）繰返して巡回シフト系列ＲＡ_mkを生成する。次いで、この巡回シフト系列を２回繰返して繰返し系列を生成する。更に、この繰返し系列の後部Ｌ−１個のチップを繰返し系列の前部外側に、ガイドチップとして付加し得られる対構成の要素系列を順に直列に接続して巡回形直列系列Ｇ_mk（ここで、ｍは組番号を表し０≦ｍ≦Ｍ−１となり、ｋは組を構成する要素番号を表し０≦ｋ≦Ｌ−１となる）を生成する。これを送信側においてパイロット信号ｐ及び送信データ信号ｄを拡散するために用いる。この拡散された送信データ信号は周波数変調され、伝送路上へ送信される。
【０００４】
一方、受信側では、受信信号に対し、前記繰り返し系列の複素共役
【外１】

で逆拡散を行い、パイロット応答信号Ｐとデータ応答信号ｑを求める。そして、パイロット応答信号Ｐからなる行列[Ｐ]とデータ応答信号ｑからなるべクトルｑを生成し、[Ｐ]^-1ｑなる代数演算を行うことにより送信データ信号を復調することが行なわれる。
【０００５】
図９は、従来構成における符号分割多重通信における受信装置側の機能ブロック図を示している。図に示す受信装置９００において、受信信号は、受信ベースバンド生成器９０２に入力され、送信側の各変調周波数に対応した局発周波数でそれぞれ復調され、これによって前記巡回形直列系列Ｇ_mkで拡散された受信ベースバンド信号が得られる。この信号は、各系列において２つに分岐され、一方が、遅延回路９０４を介して逆拡散のための演算回路９０６へ、他方が直接演算回路９０８へ入力される。演算回路９０８に直接入力された受信ベースバンド信号は、それが対象とする巡回形直列系列（例えば、Ｇ₀₀）の後部に含まれる繰り返し系列の複素共役
【外２】

と演算回路９０８において相関演算される。一方、前記遅延回路９０４に入力された受信ベースバンドは、ここでＬＮＴc秒分、すなわち１繰り返し系列＋１ガイドチップ分の遅延が与えられたのち、演算回路９０８において、巡回形直列系列Ｇ₀₀の前部に含まれる繰り返し系列の複素共役
【外３】

と相関演算される。前記遅延回路９０４によって同期された各演算回路９０６、９０８の出力は、加算回路９１０で加算され、これがデータ応答信号とされる。
【０００６】
【発明が解決しようとする課題】
しかしながら、従来の完全相補系列を用いた符号分割多重通信においては、前述のように、その受信装置側の各系列毎に遅延回路９０４及び加算回路９１０を装備する必要があり、その系列数が増加するに連れて、回路構成が大規模になるという問題があった。
【０００７】
従って、本発明の目的は、完全相補系列を用いた符号分割多重通信において受信装置側の回路構成を簡略化することが可能な符号分割多重通信方法及び装置を提供することにある。
【０００８】
【課題を解決するための手段】
前記目的を達成するため本発明は、完全相補系列を用いてデータ通信を行う符号分割多重通信方法において、送信側において、対構成の完全相補系列に基づいて生成される巡回形直列系列によって送信データ信号を拡散する手順と、前記送信データ信号を拡散した信号を所定の搬送波で周波数変調する手順と、を備え、受信側において、前記所定の搬送波に対応した所定の局発信号に基づいて、受信信号から受信ベースバンド信号を復調する手順と、前記受信ベースバンド信号を、巡回形零挿入直列系列によって逆拡散しデータ応答信号を得る手順と、を備え、前記巡回形直列系列が、長さＬの対構成の完全相補系列の後部１チップを前部外側に移動する操作をｋ回繰返して巡回シフト系列を生成し、該巡回シフト系列を複数回繰返して繰返し系列を生成し、該繰返し系列の後部Ｌ−１個のチップを繰返し系列の前部外側に付加し得られる対構成の要素系列を順に直列に接続して得られ、前記巡回形零挿入直列系列が、前記繰返し系列の前部外側にＬ−１個の０を付加し得られる対構成の要素系列を順に直列に接続して得られるものであることを特徴とする。
【０００９】
また、本発明は、完全相補系列を用いて送受信装置間でデータ通信を行う符号分割多重通信装置において、前記送信装置は、対構成の完全相補系列に基づいて生成される巡回形直列系列によって送信データ信号を拡散する拡散手段と、前記送信データ信号を拡散した信号を所定の搬送波で周波数変調する変調手段と、を備え、前記受信装置は、前記所定の搬送波に対応した所定の局発信号に基づいて、受信信号から受信ベースバンド信号を復調する復調手段と、前記受信ベースバンド信号を、巡回形零挿入直列系列によって逆拡散しデータ応答信号を得るデータ応答信号生成手段と、を備え、前記巡回形直列系列が、長さＬの対構成の完全相補系列の後部１チップを前部外側に移動する操作をｋ回繰返して巡回シフト系列を生成し、該巡回シフト系列を複数回繰返して繰返し系列を生成し、該繰返し系列の後部Ｌ−１個のチップを繰返し系列の前部外側に付加し得られる対構成の要素系列を順に直列に接続して得られ、前記巡回形零挿入直列系列が、前記繰返し系列の前部外側にＬ−１個の０を付加し得られる対構成の要素系列を順に直列に接続して得られるものであることを特徴とする。
【００１０】
次に、本発明のより具体的な解決手段について説明する。本発明においては、例えば、長さがＬチップでＭ個の系列を要素系列とするＭ対の完全相補系列の後部１チップを前部外側に移動する操作をｋ回（０≦ｋ≦Ｌ−１）繰返して巡回シフト系列を生成する。次いで、この巡回シフト系列をＮ回繰返して繰返し系列を生成する。更に、この繰返し系列の後部Ｌ−１個のチップを繰返し系列の前部外側に付加し得られる対構成の要素系列を順に直列に接続して巡回形直列系列Ｇ_mk（ここで、ｍは組番号を表し０≦ｍ≦Ｍ−１となり、ｋは組を構成する要素番号を表し０≦ｋ≦Ｌ−１となる）を生成する。これを送信側においてパイロット信号ｐ及び送信データ信号ｄを拡散するために用いる。
【００１１】
一方、前記繰返し系列の前部外側にＬ−１個の０を付加し得られる対構成の要素系列を順に直列に接続して、巡回形零挿入直列系列Ｚ_mk（ここで、ｍは組番号を表し０≦ｍ≦Ｍ−１となり、ｋは組を構成する要素番号を表し０≦ｋ≦Ｌ−１となる）を生成する。この巡回形零挿入直列系列Ｚ_mkの複素共役
【外４】

を受信側において受信信号を逆拡散するために用いる。巡回形直列系列と巡回形零挿入系列の双方は長さが（ＬＮ＋Ｌ−１）Ｍチップで、Ｌ個で１組を構成し、Ｍ組で構成する。
【００１２】
送信側では、巡回形直列系列Ｇ₀₀にパイロット信号ｐ＝１を乗算して信号ｓ₀₀₀を得る。また、ｍ≠０の巡回形直列系列Ｇ_mkにｍ≠０の送信データ信号ｄ_0mkを乗算して得られる信号を加算した信号ｓ_0mkを得る。そして信号ｓ₀₀₀と信号ｓ_0mkを加算して信号ｓ₀を得る。さらに、巡回形直列系列Ｇ_mkにｎ≠０の送信データ信号ｄ_nmkを乗算して得られる信号を加算して信号ｓ_nを得る。信号ｓ_nを次式で表す。
【００１３】
【数１】

【００１４】
次に、信号ｓ_nに搬送波信号ｆ_n(t)を乗算して加算した送信信号ｓ(t)を得る。搬送波信号ｆ_n(t)は次式で表される。
【００１５】
【数２】

【００１６】
ここでＴ_cは巡回形直列系列Ｇ_mkのチップ幅である。また、
【外５】

である。
よって、送信信号は次式で表される。
【００１７】
【数３】

【００１８】
送信信号が複数の伝搬路を伝搬し、それぞれの伝搬路で独立した遅延と位相回転および減衰が生じ、これらの影響を受けた合成信号が受信信号となる。ここで、伝搬路の遅延幅はチップＴ_cの整数倍とし、また、（Ｌ−１）Ｔ_c以下とする。実際の遅延幅はチップ幅Ｔ_cの実数倍となるが、等化回路にて遅延幅はチップ幅Ｔ_cの整数倍に波形整形することができる。波形整形された受信信号ｒ(t)は次式で表される。
【００１９】
【数４】

【００２０】
ここで、ａ_τは伝搬路の減衰係数であり、θ_τは伝搬路の位相回転角である。
【００２１】
受信側では、受信信号ｒ(t)を次式で与えられる局発信号
【外６】

で受信べースバンド信号ｒ_n(t)に変換する。
【００２２】
【数５】

【００２３】
受信べースパンド信号ｒ_n(t)を巡回形零挿入系列Ｚ_mkの複素共役
【外７】

と相関演算を行い相関出力Ｃ_nmkを得る。相関出力Ｃ_00kはパイロット応答信号となり次式で表される。
【００２４】
【数６】

【００２５】
また、パイロット応答信号以外の相関出力Ｃ_nmkはデータ応答信号となり次式で表される。
【００２６】
【数７】

【００２７】
ただし、mod(x,y)はxをyで割ったときの剰余を示す。
【００２８】
ここで、位相補正を行った位相補正パイロット応答信号Ｐ_nkを次式で与える。
【００２９】
【数８】

【００３０】
位相補正パイロット応答信号Ｐ_nkとデータ応答信号Ｃ_nmkとの間には次式の関係が成り立つ。
【００３１】
【数９】

【００３２】
よって、次式を演算することにより送信データｄ_nmkを復調することができる。
【００３３】
【数１０】

【００３４】
【発明の実施の形態】
以下、図示した一実施形態に基いて本発明を詳細に説明する。図１は本発明に係るパイロット支援形符号分割多重通信装置の一実施形態を示す機能ブロック図である。図において、符号分割多重通信装置１００は、後述する方法によって生成される巡回形直列系列Ｇ₀₀〜Ｇ₁₃を用いて、パイロット信号ｐ及び送信データ信号ｄ₀₁₀〜ｄ₁₁₃を拡散し、送信する送信装置２００、及び後述する方法によって生成される巡回形零挿入系列Ｚ₀₀〜Ｚ₁₃の複素共役
【外８】

〜
【外９】

を用いて、受信信号ｒ(t)を逆拡散し、送信データを復調する受信装置３００で構成される。
【００３５】
送信装置２００は、シリアルに入力される送信データ信号ｄ₀₁₀〜ｄ₁₁₃をパラレルに出力するシリアル／パラレル変換部２０２、巡回形直列系列Ｇ₀₀及びＧ₁₀〜Ｇ₁₃を用いてパイロット信号ｐ及び送信データ信号の一部ｄ₀₁₀〜ｄ₀₁₃を拡散する第１の乗算器群２０４と、巡回形直列系列Ｇ₀₀〜Ｇ₁₃を用いて送信データ信号の残りｄ₁₀₀〜ｄ₁₁₃を拡散する第２の乗算器群２０６と、パイロット信号を拡散した信号ｓ₀₀₀と送信データ信号の一部を拡散した信号ｓ₀₁₀〜ｓ₀₁₃とを全て加算して第１の送信ベースバンド信号ｓ₀を生成する第１の加算器２０８と、送信データ信号の残りを拡散した信号ｓ₁₀₀〜ｓ₁₁₃を全て加算して第２の送信ベースバンド信号ｓ₁を生成する第２の加算器２１０と、第１の送信バンド信号ｓ₀を第１の搬送波ｆ₀(t)で周波数変調する第１の変調器２１２と、第２の送信バンド信号ｓ₁を第２の搬送波ｆ₁(t)で周波数変調する第２の変調器２１４と、前記変調された２つの信号を加算して、送信信号ｓ(t)を生成する送信信号生成器２１６と、送信信号ｓ(t)を送信するアンテナ２１８を備えて構成される。
【００３６】
一方、受信装置３００は、受信信号ｒ(t)を受信するアンテナ３０２と、第１の局発信号
【外１０】

に基づいて、受信信号ｒ(t)から第１の受信ベースバンド信号ｒ₀(t)を生成する第１の受信ベースバンド生成器３０４と、第２の局発信号
【外１１】

に基づいて、受信信号ｒ(t)から第２の受信ベースバンド信号ｒ₁(t)を生成する第２の受信ベースバンド生成器３０６と、第１の受信ベースバンド信号ｒ₀(t)を、巡回形零挿入系列Ｚ₀₀〜Ｚ₁₃の複素共役
【外１２】

〜
【外１３】

によって逆拡散しパイロット応答信号Ｃ₀₀₀〜Ｃ₀₀₃を得るパイロット応答信号生成器３０８と、第１の受信ベースバンド信号ｒ₀(t)を、巡回形零挿入系列Ｚ₀₀〜Ｚ₁₃の複素共役
【外１４】

〜
【外１５】

によって逆拡散し第１のデータ応答信号Ｃ₀₁₀〜Ｃ₀₁₃を得る第１のデータ応答信号生成器３１０と、第２の受信ベースバンド信号ｒ₁(t)を、巡回形零挿入系列Ｚ₀₀〜Ｚ₁₃の複素共役
【外１６】

〜
【外１７】

によって逆拡散し第２のデータ応答信号Ｃ₁₀₀〜Ｃ₁₁₃を得る第２のデータ応答信号生成器３１２と、パイロット応答信号Ｃ₀₀₀〜Ｃ₀₀₃に基づいて、第１のデータ応答信号Ｃ₀₁₀〜Ｃ₀₁₃から送信データ信号ｄ₀₁₀〜ｄ₀₁₃を復調する第１の送信データ信号復調器３１４と、パイロット応答信号Ｃ₀₀₀〜Ｃ₀₀₃に基づいて、第１及び第２の搬送波間の位相補正値を算出し、位相補正パイロット応答信号Ｐ₀₀〜Ｐ₀₃を生成する位相補正器群３１６と、位相補正パイロット応答信号Ｐ₀₀〜Ｐ₀₃に基づいて、第２のデータ応答信号Ｃ₁₀₀〜Ｃ₁₁₃から送信データ信号ｄ₁₀₀〜ｄ₁₁₃を復調する第２及び第３の送信データ信号復調器３１８、３２０と、パラレルに入力される送信データ信号ｄ₀₁₀〜ｄ₁₁₃をシリアルに出力するパラレル／シリアル変換部３２２を備えて構成される。
【００３７】
次に、図２〜図８に従って、完全相補系列に基づいて、巡回形直列系列Ｇ₀₀〜Ｇ₁₃及び巡回形零挿入系列Ｚ₀₀〜Ｚ₁₃を生成する方法及び、これらの系列を用いてデータ通信を行なう手順について説明する。ここでは、長さがＬ＝４チップで、Ｍ＝２個の系列を要素系列とするＭ＝２対で構成する完全相補系列を用いた例を説明する。用いる完全相補系列を次式に示し、その波形を図２に示す。
【００３８】
【数１１】

【００３９】
ただし、＋は＋１を表し、−は−１を表す。
【００４０】
前記完全相補系列の後部１チップを前部外側に移動する操作をｋ回（０≦ｋ≦Ｌ−１）繰返してＡ₀₀、Ａ₀₁、Ａ₀₂、Ａ₀₃、Ａ₁₀、Ａ₁₁、Ａ₁₂、Ａ₁₃、Ｂ₀₀、Ｂ₀₁、Ｂ₀₂、Ｂ₀₃、Ｂ₁₀、Ｂ₁₁、Ｂ₁₂、Ｂ₁₃の巡回シフト系列を生成する。これを次式に示し、その生成過程と波形を図３に示す。
【００４１】
【数１２】

【００４２】
次に、各巡回シフト系列をＮ＝２回繰り返し、繰り返し系列ＲＡ₀₀、ＲＡ₀₁、ＲＡ₀₂、ＲＡ₀₃、ＲＡ₁₀、ＲＡ₁₁、ＲＡ₁₂、ＲＡ₁₃、ＲＢ₀₀、ＲＢ₀₁、ＲＢ₀₂、ＲＢ₀₃、ＲＢ₁₀、ＲＢ₁₁、ＲＢ₁₂、ＲＢ₁₃を生成する。これを次式に示し、その生成過程と波形を図４に示す。
【００４３】
【数１３】

【００４４】
次に、各繰り返し系列の後部３チップを前部外側に付加し得られる対構成の要素系列を順に直列に接続し、以上により送信側で用いる巡回形直列系列Ｇ₀₀、Ｇ₀₁、Ｇ₀₂、Ｇ₀₃、Ｇ₁₀、Ｇ₁₁、Ｇ₁₂、Ｇ₁₃を生成する。これを次式に示し、生成過程と波形を図５に示す。
【００４５】
【数１４】

【００４６】
一方、各繰返し系列の前部外側に３個の０を付加し得られる対構成の要素系列を順に直列に接続し、これによって受信側で用いる巡回形零挿入直列系列Ｚ₀₀、Ｚ₀₁、Ｚ₀₂、Ｚ₀₃、Ｚ₁₀、Ｚ₁₁、Ｚ₁₂、Ｚ₁₃を生成する。これを次式に示し、その生成過程と波形を図６に示す。
【００４７】
【数１５】

【００４８】
次に、図１に示した符号分割多重通信装置１００において、前記巡回形直列系列Ｇ₀₀〜Ｇ₁₃及び巡回形零挿入系列Ｚ₀₀〜Ｚ₁₃を用いてデータ通信を行なう手順について説明する。
【００４９】
送信装置２００側では、第１の乗算器群２０４において、巡回直列系列Ｇ₀₀にパイロット信号ｐ＝１を乗算して信号ｓ₀₀₀を得る。また、巡回直列系列をＧ_mk、送信データをｄ_nmkとし、Ｇ₁₀にｄ₀₁₀を乗じてｓ₀₁₀を、Ｇ₁₁にｄ₀₁₁を乗じてｓ₀₁₁を、Ｇ₁₂にｄ₀₁₂を乗じてｓ₀₁₂を、Ｇ₁₃にｄ₀₁₃を乗じてｓ₀₁₃を得る。そして、第１の加算器２０８においてｓ₀₀₀、ｓ₀₁₀、ｓ₀₁₁、ｓ₀₁₂、ｓ₀₁₃を全て加算して送信べースバンド信号ｓ₀を得る。送信べースバンド信号ｓ₀の生成過程と波形を図７に示す。さらに、第２の乗算器群２０６において、Ｇ₀₀にｄ₁₀₀を乗じてｓ₁₀₀を、Ｇ₀₁にｄ₁₀₁を乗じてｓ₁₀₁を、Ｇ₀₂にｄ₁₀₂を乗じてｓ₁₀₂を、Ｇ₀₃にｄ₁₀₃を乗じてｓ₁₀₃を、Ｇ₁₀にｄ₁₁₀を乗じてｓ₁₁₀を、Ｇ₁₁にｄ₁₁₁を乗じてｓ₁₁₁を、Ｇ₁₂にｄ₁₁₂を乗じてｓ₁₁₂を、Ｇ₁₃にｄ₁₁₃を乗じてｓ₁₁₃を得る。第２の加算器２１０において、ｓ₁₀₀、ｓ₁₀₁、ｓ₁₀₂、ｓ₁₀₃、ｓ₁₁₀、ｓ₁₁₁、ｓ₁₁₂、ｓ₁₁₃を全て加算して送信べースバンド信号ｓ₁を得る。送信べースパンド信号ｓ₁の生成過程と波形を図８に示す。
【００５０】
次に、第１の変調器２１２において信号ｓ₀に搬送波信号ｆ₀(t)を乗算して得た信号と、第２の変調器２１４において信号ｓ₁に搬送波信号ｆ₁(t)を乗算して得た信号とを、送信信号生成器２１６において加算して送信信号ｓ(t)を得、これをアンテナ２１８より送出する。搬送波信号ｆ_n(t)は次式で表される。
【００５１】
【数１６】

【００５２】
ここでＴ_cは巡回形直列系列Ｇ_mkのチップ幅である。また、
【外１８】

である。
【００５３】
送信信号が複数の伝搬路を伝搬し、それぞれの伝搬路で独立した遅延と位相回転および減衰が生じ、これらの影響を受けた合成信号が受信信号ｒ(t)となり、受信アンテナから入来する。ここで、伝搬路の遅延は３Ｔ_c以下とする。実際の遅延幅はチップ幅Ｔ_cの実数倍となるが、図１にて省略した等化回路にて遅延幅はチップ幅Ｔ_cの整数倍に波形整形できる。波形整形された受信信号ｒ(t)は次式で表される。
【００５４】
【数１７】

【００５５】
ここで、ａ_τは伝搬路の減衰係数であり、θ_τは伝搬路の位相回転角である。
【００５６】
受信装置３００のアンテナ３０２で受信信号ｒ(t)が受信されると、第１の受信ベースバンド生成器３０４で、受信信号ｒ(t)は局発信号
【外１９】

を乗じて受信べースバンド信号ｒ₀(t)に変換され、また、第２の受信ベースバンド生成器３０６で、同じ局発信号を乗じて受信べースパンド信号ｒ₁(t)に変換される。受信べースバンド信号ｒ₀(t)は、パイロット応答信号生成器３０８にて、
【外２０】

と相関演算を行いＣ₀₀₀を、
【外２１】

と相関演算を行いＣ₀₀₁を、
【外２２】

と相関演算を行いＣ₀₀₂を、
【外２３】

と相関演算を行いＣ₀₀₃を、また、第１のデータ応答信号生成器３１０にて、
【外２４】

と相関演算を行いＣ₀₁₀を、
【外２５】

と相関演算を行いＣ₀₁₁を、
【外２６】

と相関演算を行いＣ₀₁₂を、
【外２７】

と相関演算を行いＣ₀₁₃を得る。一方、受信べースバンド信号ｒ₁(t)は、第２のデータ応答信号生成器３１２にて、
【外２８】

と相関演算を行いＣ₁₀₀を、
【外２９】

と相関演算を行いＣ₁₀₁を、
【外３０】

と相関演算を行いＣ₁₀₂を、
【外３１】

と相関演算を行いＣ₁₀₃を、
【外３２】

と相関演算を行いＣ₁₁₀を、
【外３３】

と相関演算を行いＣ₁₁₁を、
【外３４】

と相関演算を行いＣ₁₁₂を、
【外３５】

と相関演算を行いＣ₁₁₃を得る。ここで、
【外３６】

は巡回形零挿入系列Ｚ_mkの複素共役を示す。また、相関演算のタイミングは、送信信号ｓ(t)に同期しているものとする。
【００５７】
ここで、Ｃ₀₀₀、Ｃ₀₀₁、Ｃ₀₀₂、Ｃ₀₀₃はパイロット応答信号となる。また、Ｃ₀₁₀、Ｃ₀₁₁、Ｃ₀₁₂、Ｃ₀₁₃は一組のデータ応答信号となり、Ｃ₁₀₀、Ｃ₁₀₁、Ｃ₁₀₂、Ｃ₁₀₃は一組のデータ応答信号となり、Ｃ₁₁₀、Ｃ₁₁₁、Ｃ₁₁₂、Ｃ₁₁₃は一組のデータ応答信号となる。
【００５８】
次に、位相補正器群３１６において、パイロット応答信号より位相補正パイロット応答信号Ｐ_nkが求められる。
【００５９】
【数１８】

【００６０】
位相補正パイロット応答信号Ｐ_nkは、
【００６１】
【数１９】

で一組となり、
【００６２】
【数２０】

で一組となる。
【００６３】
図１においてＷ_nkは位相補正角を示し、
【００６４】
【数２１】

となる。
【００６５】
一方、第１の送信データ信号復調器３１４においては、
【００６６】
【数２２】

の代数演算が行なわれ、これにより、送信データｄ₀₁₀、ｄ₀₁₁、ｄ₀₁₂、ｄ₀₁₃が復調される。また、第２の送信データ信号復調器３１８においては、前記位相補正パイロット応答信号Ｐ_nkを用いた、下記代数演算が行なわれる。
【００６７】
【数２３】

【００６８】
この演算により、送信データｄ₁₀₀、ｄ₁₀₁、ｄ₁₀₂、ｄ₁₀₃が復調される。さらに、また、第２の送信データ信号復調器３１８においても、前記位相補正パイロット応答信号Ｐ_nkを用いた、下記代数演算が行なわれる。
【００６９】
【数２４】

【００７０】
この演算により、送信データｄ₁₁₀、ｄ₁₁₁、ｄ₁₁₂、ｄ₁₁₃が復調される。これら各復調器で復調された送信データｄ₀₁₀〜ｄ₁₁₃は、パラレル／シリアル変換部３２２に入力され、ここでシリアルデータに変換される。以上により、伝搬路で独立した遅延と位相回転および減衰による影響を受けた受信信号ｒ(t)が、正確に元の送信データに復調される。
【００７１】
以上、本発明の一実施形態を図面に沿って説明した。しかしながら本発明は前記実施形態に示した事項に限定されず、特許請求の範囲の記載に基いてその変更、改良等が可能であることは明らかである。本実施形態においては、パイロット信号を乗せる巡回形直列系列と、送信データ信号を乗せる巡回形直列系列を異なるものとして信号を生成し、これを送信するようにしたが、送信データ信号を乗せる巡回形直列系列に対し、パイロット信号を間欠的に重畳させて送信信号を生成しても良い。
【００７２】
【発明の効果】
以上の如く本発明によれば、受信ベースバンド信号を逆拡散するために、繰り返し系列の前部外側にＬ−１個の０を付加し得られる対構成の要素系列を順に直列に接続して得られる巡回形零挿入直列系列Ｚ_mkの複素共役
【外３７】

を用いたため、完全相補系列を用いた符号分割多重通信において、その受信装置側の各系列に、遅延回路及び加算回路を備える必要がなくなる。よって、受信装置の回路構成が簡略化される。
【図面の簡単な説明】
【図１】本発明に係るパイロット支援形符号分割多重通信装置の一実施形態を示す機能ブロック図である。
【図２】長さがＬ＝４チップで、Ｍ＝２個の系列を要素系列とするＭ＝２対で構威する完全相補系列の波形を示す図である。
【図３】巡回シフト系列の生成過程と波形を示す図である。
【図４】繰り返し系列の生成過程と波形を示す図である。
【図５】巡回形直列系列の生成過程と波形を示す図である。
【図６】巡回形零挿入直列系列の生成過程と波形を示す図である。
【図７】送信べースパンド信号ｓ₀の生成過程と波形を示す図である。
【図８】送信べースパンド信号ｓ₁の生成過程と波形を示す図である。
【図９】従来構成における符号分割多重通信における受信装置側の機能ブロック図である。
【符号の説明】
１００符号分割多重通信装置
２００送信装置
２０２シリアル／パラレル変換部
２０４第１の乗算器群
２０６第２の乗算器群
２０８第１の加算器
２１０第２の加算器
２１２第１の変調器
２１４第２の変調器
２１６送信信号生成器
２１８アンテナ
３００受信装置
３０２アンテナ
３０４第１の受信ベースバンド生成器
３０６第２の受信ベースバンド生成器
３０８パイロット応答信号生成器
３１０第１のデータ応答信号生成器
３１２第２のデータ応答信号生成器
３１４第１の送信データ信号復調器
３１６位相補正器群
３１８第２の送信データ信号復調器
３２０第３の送信データ信号復調器
３２２パラレル／シリアル変換部[0001]
BACKGROUND OF THE INVENTION
The present invention relates to a completely complementary sequence pilot-assisted code division multiplexing communication method and apparatus, and more particularly, to a completely complementary sequence pilot-assisted code division multiplexing that can simplify the circuit configuration for demodulation on the receiver side that demodulates transmission data. The present invention relates to a communication method and apparatus.
[0002]
[Prior art]
A code division multiplexing (CDMA) communication system is widely used as a communication system for mobile communication. The code division multiplex communication method has an advantage that the number of signals that can be multiplexed in the same channel can be greatly increased as compared with frequency division multiplex communication (FDMA) and time division multiplex communication (TDMA). It is expected to spread.
[0003]
In code division multiplex communication, a comb-tooth spectrum communication system using a completely complementary sequence is widely adopted. In this communication method, on the transmission side, a series sequence in which element sequences constituting a pair of completely complementary sequences are connected in series is generated, a pilot signal is placed on one of the series sequences, and the other pair sequences are delayed in units of chips. A transmission data signal is placed on the shifted delay shift sequence and transmitted. For example, the operation of moving the rear one chip of two pairs of completely complementary series having a length of 4 chips and two series as element series is repeated k times (0 ≦ k ≦ L−1) repeatedly. A shift sequence RA _mk is generated. Next, this cyclic shift sequence is repeated twice to generate a repetitive sequence. Further, a cyclic series series G _mk (wherein the rear L-1 chips of the repetition series are sequentially connected in series with the paired element series that can be added as a guide chip outside the front part of the repetition series. , M represents a set number and 0 ≦ m ≦ M−1, and k represents an element number constituting the set and 0 ≦ k ≦ L−1). This is used for spreading the pilot signal p and the transmission data signal d on the transmission side. The spread transmission data signal is frequency-modulated and transmitted onto the transmission path.
[0004]
On the other hand, on the receiving side, the complex conjugate of the repetitive sequence with respect to the received signal.

The despreading is performed to obtain the pilot response signal P and the data response signal q. A matrix [P] composed of pilot response signals P and a vector q composed of data response signals q are generated, and a transmission data signal is demodulated by performing an algebraic operation of [P] ⁻¹ q.
[0005]
FIG. 9 is a functional block diagram on the receiving device side in code division multiplexing communication in the conventional configuration. In the receiving apparatus 900 shown in the figure, a received signal is input to a reception baseband generator 902 and demodulated at a local frequency corresponding to each modulation frequency on the transmission side, and thereby spread by the cyclic serial sequence G _mk . The received baseband signal is obtained. This signal is branched into two in each series, one being input to the arithmetic circuit 906 for despreading via the delay circuit 904 and the other being directly input to the arithmetic circuit 908. The received baseband signal directly input to the arithmetic circuit 908 is a complex conjugate of a repetitive sequence included in the rear part of the cyclic serial sequence (eg, G ₀₀ ) targeted by the received baseband signal.

The arithmetic circuit 908 calculates the correlation. Meanwhile, the reception baseband which is input to the delay circuit 904, where LNTc seconds min, i.e. 1 after the repeated sequence plus guide chips of delay is given, in the arithmetic circuit 908, before the recursive series series G ₀₀ Complex conjugate of repeating sequence included in part [External 3]

And the correlation is calculated. The outputs of the

arithmetic circuits

906 and 908 synchronized by the delay circuit 904 are added by an adder circuit 910, which is used as a data response signal.
[0006]
[Problems to be solved by the invention]
However, in the conventional code division multiplexing communication using completely complementary sequences, as described above, it is necessary to equip each receiving device side with a delay circuit 904 and an adding circuit 910, and the number of sequences increases. As a result, there has been a problem that the circuit configuration becomes large.
[0007]
Accordingly, an object of the present invention is to provide a code division multiplexing communication method and apparatus capable of simplifying the circuit configuration on the receiving apparatus side in code division multiplexing communication using a completely complementary sequence.
[0008]
[Means for Solving the Problems]
In order to achieve the above object, the present invention provides a code division multiplexing communication method for performing data communication using a complete complementary sequence, wherein transmission data is transmitted by a cyclic serial sequence generated based on a completely complementary sequence in a pair on the transmission side. And a procedure for frequency-modulating a signal obtained by spreading the transmission data signal with a predetermined carrier wave on the reception side based on a predetermined local signal corresponding to the predetermined carrier wave. A procedure for demodulating a received baseband signal from a signal, and a procedure for despreading the received baseband signal with a cyclic zero insertion serial sequence to obtain a data response signal, wherein the cyclic serial sequence has a length L The operation of moving the rear one chip of the completely complementary series of the pair configuration to the front outside is repeated k times to generate a cyclic shift series, and the cyclic shift series is repeated a plurality of times to repeat. A cyclic zero-insertion serial sequence obtained by generating a sequence and sequentially connecting pairs of element sequences obtained by adding the rear L-1 chips of the repetition sequence outside the front of the repetition sequence in series. Is obtained by sequentially connecting in series a paired element series obtained by adding L-1 0s to the front outer side of the repetitive series.
[0009]
The present invention also relates to a code division multiplexing communication apparatus that performs data communication between transmitting and receiving apparatuses using a completely complementary sequence, wherein the transmitting apparatus transmits a cyclic serial sequence generated based on a completely complementary sequence of a pair configuration. Spreading means for spreading a data signal; and modulation means for frequency-modulating a signal obtained by spreading the transmission data signal with a predetermined carrier; and the receiving device converts the signal into a predetermined local signal corresponding to the predetermined carrier. A demodulating means for demodulating a received baseband signal from a received signal, and a data response signal generating means for despreading the received baseband signal with a cyclic zero insertion serial sequence to obtain a data response signal, The cyclic serial sequence generates a cyclic shift sequence by repeating the operation of moving the rear one chip of the complete complementary sequence of length L in the pair configuration to the front outside k times, and generating the cyclic shift sequence. It is obtained by generating a repetition sequence by repeating a series of times, and sequentially connecting paired element sequences that can be obtained by adding the rear L-1 chips of the repetition sequence outside the front of the repetition sequence. The cyclic zero-insertion serial sequence is obtained by serially connecting a pair of element sequences obtained by adding L-1 0s to the outer front of the repetitive sequence. To do.
[0010]
Next, more specific solving means of the present invention will be described. In the present invention, for example, the operation of moving the rear one chip of the M pairs of completely complementary series having the length of L chips and M series as the element series to the outside of the front is performed k times (0 ≦ k ≦ L− 1) Repeatedly generate a cyclic shift sequence. Next, this cyclic shift sequence is repeated N times to generate a repetitive sequence. Further, a paired element series obtained by adding the rear L-1 chips of the rear part of the repetitive series to the outside of the front part of the repetitive series is sequentially connected in series to form a cyclic series series G _mk (where m is a set). The number represents 0 ≦ m ≦ M−1, and k represents the element number constituting the set, and 0 ≦ k ≦ L−1). This is used for spreading the pilot signal p and the transmission data signal d on the transmission side.
[0011]
On the other hand, a pair-structured element sequence obtained by adding L-1 0s to the outer front side of the repetitive sequence is connected in series in order, and a cyclic zero insertion series sequence Z _mk (where m is a set number) 0 ≦ m ≦ M−1, and k represents an element number constituting the set, and 0 ≦ k ≦ L−1). Complex conjugate of this cyclic zero insertion series Z _mk

Is used to despread the received signal at the receiving side. Both the cyclic serial sequence and the cyclic zero insertion sequence have a length of (LN + L-1) M chips, and one set is formed by L pieces, and is formed by M sets.
[0012]
On the transmission side, the cyclic serial sequence G ₀₀ is multiplied by the pilot signal p = 1 to obtain a signal s ₀₀₀ . Also, a signal s _0mk is obtained by adding a signal obtained by multiplying the _cyclic data series G _mk with m ≠ 0 by the transmission data signal d _0mk with m ≠ 0. Then, the signal s ₀₀₀ and the signal s _0mk are added to obtain the signal s ₀ . Furthermore, to obtain a signal s _n by adding the signal obtained recursive series sequence G _mk by multiplying the transmission data signal d _NMK of n ≠ 0. We represent the signal s _n by the following equation.
[0013]
[Expression 1]

[0014]
Next, a transmission signal s (t) obtained by multiplying the signal s _n by the carrier wave signal f _n (t) and adding it is obtained. The carrier wave signal f _n (t) is expressed by the following equation.
[0015]
[Expression 2]

[0016]
Here, T _c is the chip width of the cyclic serial series G _mk . Also,
[Outside 5]

It is.
Therefore, the transmission signal is expressed by the following equation.
[0017]
[Equation 3]

[0018]
A transmission signal propagates through a plurality of propagation paths, and independent delay, phase rotation, and attenuation occur in each propagation path, and a combined signal affected by these becomes a reception signal. Here, the delay width of the propagation path is an integral multiple of the chip T _{c and} is equal to or less than (L−1) T _c . The actual delay spread becomes a real number multiple of the chip width T _c, but delay spread in the equalizing circuit can be waveform-shaped to an integral multiple of the chip width T _c. The waveform-shaped received signal r (t) is expressed by the following equation.
[0019]
[Expression 4]

[0020]
Here, a _τ is the attenuation coefficient of the propagation path, and θ _τ is the phase rotation angle of the propagation path.
[0021]
On the receiving side, the received signal r (t) is a local signal given by the following equation.

Is converted into a received baseband signal r _n (t).
[0022]
[Equation 5]

[0023]
Complex conjugate of reciprocal zero insertion sequence Z _mk with received base spanned signal r _n (t)

And a correlation output C _nmk is obtained. The correlation output C _00k becomes a pilot response signal and is expressed by the following equation.
[0024]
[Formula 6]

[0025]
Further, the correlation output C _nmk other than the pilot response signal becomes a data response signal and is expressed by the following equation.
[0026]
[Expression 7]

[0027]
However, mod (x, y) indicates a remainder when x is divided by y.
[0028]
Here, the phase corrected pilot response signal P _nk that has been _subjected to phase correction is given by the following equation.
[0029]
[Equation 8]

[0030]
Equation relationship between the phase correction pilot response signal P _nk and data response signal C _NMK holds.
[0031]
[Equation 9]

[0032]
Therefore, the transmission data d _nmk can be demodulated by calculating the following equation.
[0033]
[Expression 10]

[0034]
DETAILED DESCRIPTION OF THE INVENTION
Hereinafter, the present invention will be described in detail based on the illustrated embodiment. FIG. 1 is a functional block diagram showing an embodiment of a pilot-assisted code division multiplexing communication apparatus according to the present invention. In the figure, code division multiplexing communication apparatus 100 spreads and transmits pilot signal p and transmission data signals d _{010 to} d ₁₁₃ using cyclic serial sequences G _{00 to} G ₁₃ generated by a method to be described later. Complex conjugate of cyclic zero insertion sequence Z _{00 to} Z ₁₃ generated by apparatus 200 and a method to be described later

~
[Outside 9]

Is used to despread the received signal r (t) and demodulate the transmission data.
[0035]
The transmission apparatus 200 uses the serial / parallel converter 202 that outputs serially input transmission data signals d _{010 to} d ₁₁₃ in parallel, and the cyclic series series G ₀₀ and G _{10 to} G ₁₃ to transmit the pilot signal p and transmission. A second multiplier 204 that spreads the remaining d _{100 to} d ₁₁₃ of the transmission data signal using a first multiplier group 204 that spreads a part of the data signal d _{010 to} d ₀₁₃ and a cyclic serial series G _{00 to} G ₁₃ . Multiplier group 206, a first transmission baseband signal s ₀ is generated by adding all signals s ₀₀₀ obtained by spreading the pilot signal and signals s _{010 to} s ₀₁₃ obtained by spreading a part of the transmission data signal. of an adder 208, a second adder 210 to generate a signal s ₁₀₀ ~s second ₁₁₃ adds all transmission baseband signal s ₁ that has diffused to the rest of the transmission data signal, the first transmission band the signal s ₀ in the first carrier f ₀ (t) Summing the first modulator 212 to the wave number modulation, a second modulator 214 for frequency modulating the second transmission band signal s ₁ in the second carrier f ₁ (t), the two signals the modulated The transmission signal generator 216 that generates the transmission signal s (t) and the antenna 218 that transmits the transmission signal s (t) are configured.
[0036]
On the other hand, the receiving apparatus 300 includes an antenna 302 that receives the reception signal r (t), and a first local oscillation signal.

And a first reception baseband generator 304 that generates a first reception baseband signal r ₀ (t) from the reception signal r (t), and a second local oscillation signal

Based on the received signal r (t), the second received baseband signal r ₁ (t) is generated from the second received baseband signal r ₁ (t), and the first received baseband signal r ₀ (t) , Complex conjugate of cyclic zero insertion series Z _{00 to} Z ₁₃

~
[Outside 13]

A pilot response signal generator 308 that despreads the signal to obtain pilot response signals C _{000 to} C ₀₀₃ and a first received baseband signal r ₀ (t) are complex conjugates of cyclic zero insertion sequences Z _{00 to} Z ₁₃ Outside 14]

~
[Outside 15]

The first data response signal generator 310 that despreads the first data response signals C _{010 to} C ₀₁₃ and the second received baseband signal r ₁ (t) by the cyclic zero insertion sequence Z ₀₀ to Complex conjugate of Z ₁₃ [Outside 16]

~
[Outside 17]

And the first data response signals C _{010 to} C based on the pilot response signals C _{000 to} C ₀₀₃ and the second data response signal generator 312 to obtain the second data response signals C _{100 to} C ₁₁₃ by despreading by _Based on the first transmission data signal demodulator 314 that demodulates the transmission data signals d _{010 to} d ₀₁₃ and the pilot response signals C _{000 to} C ₀₀₃ , the phase correction value between the first and second carriers is calculated. and a phase corrector group 316 which generates a phase correction pilot response signal P ₀₀ to P _03, based on the phase correction pilot response signal P ₀₀ to P _03, the transmission data from the second data response signal C ₁₀₀ -C ₁₁₃ second and third transmitted data signal demodulator 318 for demodulating a signal d ₁₀₀ to d _113, a parallel / serial conversion unit 322 for outputting a transmission data signal d ₀₁₀ to d ₁₁₃ that is input to the parallel to serial Ete constructed.
[0037]
Next, according to FIGS. 2 to 8, a method of generating cyclic serial sequences G _{00 to} G ₁₃ and cyclic zero insertion sequences Z _{00 to} Z ₁₃ based on perfect complementary sequences, and data using these sequences A procedure for performing communication will be described. Here, an example will be described in which the length is L = 4 chips and a completely complementary sequence composed of M = 2 pairs with M = 2 sequences as element sequences is used. The complete complementary series to be used is shown in the following equation, and its waveform is shown in FIG.
[0038]
## EQU11 ##

[0039]
However, + represents +1 and-represents -1.
[0040]
The operation of moving the rear one chip of the complete complementary series to the front outer side is repeated k times (0 ≦ k ≦ L−1) to repeat A ₀₀ , A ₀₁ , A ₀₂ , A ₀₃ , A ₁₀ , A ₁₁ , A _12. , A ₁₃ , B ₀₀ , B ₀₁ , B ₀₂ , B ₀₃ , B ₁₀ , B ₁₁ , B ₁₂ , B ₁₃ are generated. This is shown in the following equation, and the generation process and waveform are shown in FIG.
[0041]
[Expression 12]

[0042]
Next, each cyclic shift sequence is repeated N = 2 times, and the repeated sequences RA ₀₀ , RA ₀₁ , RA ₀₂ , RA ₀₃ , RA ₁₀ , RA ₁₁ , RA ₁₂ , RA ₁₃ , RB ₀₀ , RB ₀₁ , RB ₀₂ , RB ₀₃ , RB ₁₀ , RB ₁₁ , RB ₁₂ , RB ₁₃ are generated. This is shown in the following equation, and the generation process and waveform are shown in FIG.
[0043]
[Formula 13]

[0044]
Next, the paired element series obtained by adding the rear 3 chips of each repetition series to the outside of the front is connected in series, and the cyclic series series G ₀₀ , G ₀₁ , G ₀₂ , generating a _{_{_{G 03, G 10, G 11}}} , G 12, G 13. This is shown in the following equation, and the generation process and waveform are shown in FIG.
[0045]
[Expression 14]

[0046]
On the other hand, paired element sequences obtained by adding three zeros to the front outer side of each repetition sequence are connected in series in order, whereby cyclic zero insertion series sequences Z ₀₀ , Z ₀₁ , Z used on the receiving side are connected. _02, and generates a _{_{_{Z 03, Z 10, Z 11}}} , Z 12, Z 13. This is shown in the following equation, and the generation process and waveform are shown in FIG.
[0047]
[Expression 15]

[0048]
Next, in the code division multiplexing communication apparatus 100 shown in FIG. 1, a procedure for performing data communication using the cyclic serial sequences G _{00 to} G ₁₃ and the cyclic zero insertion sequences Z _{00 to} Z ₁₃ will be described.
[0049]
On the transmission device 200 side, the first multiplier group 204 multiplies the cyclic serial sequence G ₀₀ by the pilot signal p = 1 to obtain a signal s ₀₀₀ . Further, the cyclic serial series is G _mk , the transmission data is d _nmk , G ₁₀ is multiplied by d ₀₁₀ , s ₀₁₀ is multiplied by G ₁₁ , d ₀₁₁ is multiplied by s ₀₁₁ , and G ₁₂ is multiplied by d ₀₁₂ s _012. to yield the s ₀₁₃ multiplies the d ₀₁₃ to G _13. Then, the first adder 208 adds all s ₀₀₀ , s ₀₁₀ , s ₀₁₁ , s ₀₁₂ , and s ₀₁₃ to obtain a transmission baseband signal s ₀ . The generation process and waveform of the transmission baseband signal s ₀ are shown in FIG. Further, in the second multiplier group 206, the s ₁₀₀ multiplied by d ₁₀₀ to G _00, the s ₁₀₁ multiplies the d ₁₀₁ to G _01, the s ₁₀₂ multiplies the d ₁₀₂ to G _02, the G ₀₃ the s ₁₀₃ by multiplying the d _103, the s ₁₁₀ multiplies the d ₁₁₀ to G _10, the s ₁₁₁ multiplies the d ₁₁₁ to G _11, the s ₁₁₂ multiplies the d ₁₁₂ to G _12, d ₁₁₃ to G ₁₃ get the s ₁₁₃ is multiplied by a. In a second adder _{_{210, s 100, s 101,}} s 102, s 103, s 110, s 111, s 112, all s ₁₁₃ adds obtain transmission baseband signal s ₁ and. The generation process and waveform of the transmission base spanned signal s ₁ are shown in FIG.
[0050]
Next, the first modulator 212 multiplies the signal s ₀ by the carrier signal f ₀ (t), and the second modulator 214 multiplies the signal s ₁ by the carrier signal f ₁ (t). The transmission signal generator 216 adds the signals obtained in this way to obtain a transmission signal s (t), which is transmitted from the antenna 218. The carrier wave signal f _n (t) is expressed by the following equation.
[0051]
[Expression 16]

[0052]
Here, T _c is the chip width of the cyclic serial series G _mk . Also,
[Outside 18]

It is.
[0053]
A transmission signal propagates through a plurality of propagation paths, and an independent delay, phase rotation, and attenuation occur in each propagation path, and a combined signal affected by these becomes a reception signal r (t), which comes from a reception antenna. . Here, the delay of the propagation path is less 3T _c. The actual delay spread becomes a real number multiple of the chip width T _c but delayed width at equalization circuit is omitted in FIG. 1 can be waveform-shaped to an integral multiple of the chip width T _c. The waveform-shaped received signal r (t) is expressed by the following equation.
[0054]
[Expression 17]

[0055]
Here, a _τ is the attenuation coefficient of the propagation path, and θ _τ is the phase rotation angle of the propagation path.
[0056]
When the reception signal r (t) is received by the antenna 302 of the reception apparatus 300, the reception signal r (t) is converted into a local signal by the first reception baseband generator 304.

Is multiplied by the received baseband signal r ₀ (t), and the second received baseband generator 306 multiplies the same local signal to convert it to the received baseband signal r ₁ (t). The received baseband signal r ₀ (t) is received by the pilot response signal generator 308.
[Outside 20]

And C ₀₀₀ ,
[Outside 21]

And C ₀₀₁ ,
[Outside 22]

And C ₀₀₂ ,
[Outside 23]

And C ₀₀₃ , and in the first data response signal generator 310,
[Outside 24]

And C ₀₁₀ ,
[Outside 25]

And C ₀₁₁
[Outside 26]

And C ₀₁₂
[Outside 27]

And C ₀₁₃ is obtained. On the other hand, the received baseband signal r ₁ (t) is received by the second data response signal generator 312.
[Outside 28]

And C ₁₀₀ ,
[Outside 29]

And C ₁₀₁ ,
[Outside 30]

And C ₁₀₂ ,
[Outside 31]

And C ₁₀₃ ,
[Outside 32]

And C ₁₁₀ ,
[Outside 33]

And C ₁₁₁ ,
[Outside 34]

And C ₁₁₂ ,
[Outside 35]

And C ₁₁₃ is obtained. here,
[Outside 36]

Indicates the complex conjugate of the cyclic zero insertion sequence Z _mk . Further, it is assumed that the timing of the correlation calculation is synchronized with the transmission signal s (t).
[0057]
Here, C ₀₀₀ , C ₀₀₁ , C ₀₀₂ , and C ₀₀₃ are pilot response signals. Also, C ₀₁₀ , C ₀₁₁ , C ₀₁₂ , C ₀₁₃ are a set of data response signals, and C ₁₀₀ , C ₁₀₁ , C ₁₀₂ , C ₁₀₃ are a set of data response signals, C ₁₁₀ , C ₁₁₁ , C ₁₁₂ , C ₁₁₃ is a set of data response signals.
[0058]
Next, in the phase corrector group 316, the phase correction pilot response signal P _nk is obtained from the pilot response signal.
[0059]
[Formula 18]

[0060]
The phase correction pilot response signal _Pnk is
[0061]
[Equation 19]

In one set,
[0062]
[Expression 20]

It becomes a pair.
[0063]
In FIG. 1, W _nk indicates a phase correction angle,
[0064]
[Expression 21]

It becomes.
[0065]
On the other hand, in the first transmission data signal demodulator 314,
[0066]
[Expression 22]

The transmission data d ₀₁₀ , d ₀₁₁ , d ₀₁₂ , and d ₀₁₃ are demodulated. In addition, the second transmission data signal demodulator 318 performs the following algebraic calculation using the phase correction pilot response signal _Pnk .
[0067]
[Expression 23]

[0068]
By this calculation, the transmission data d ₁₀₀ , d ₁₀₁ , d ₁₀₂ , and d ₁₀₃ are demodulated. Further, the second transmission data signal demodulator 318 also performs the following algebraic calculation using the phase correction pilot response signal _Pnk .
[0069]
[Expression 24]

[0070]
By this calculation, transmission data d ₁₁₀ , d ₁₁₁ , d ₁₁₂ , and d ₁₁₃ are demodulated. The transmission data d _{010 to} d ₁₁₃ demodulated by each demodulator is input to the parallel / serial converter 322, where it is converted into serial data. As described above, the received signal r (t) affected by the delay, phase rotation, and attenuation independent of each other in the propagation path is accurately demodulated into the original transmission data.
[0071]
The embodiment of the present invention has been described with reference to the drawings. However, the present invention is not limited to the matters shown in the above-described embodiments, and it is obvious that changes, improvements, etc. can be made based on the description of the scope of claims. In the present embodiment, the cyclic serial sequence for carrying the pilot signal and the cyclic serial sequence for carrying the transmission data signal are generated and transmitted as different signals, but the cyclic type for carrying the transmission data signal is used. A transmission signal may be generated by intermittently superimposing a pilot signal on a serial sequence.
[0072]
【The invention's effect】
As described above, according to the present invention, in order to despread the received baseband signal, paired element sequences obtained by adding L-1 0s to the outer front of the repetitive sequence are sequentially connected in series. Complex conjugate of the obtained cyclic zero insertion series Z _mk

Therefore, in code division multiplex communication using a completely complementary sequence, it is not necessary to provide a delay circuit and an adder circuit for each sequence on the receiving device side. Therefore, the circuit configuration of the receiving device is simplified.
[Brief description of the drawings]
FIG. 1 is a functional block diagram showing an embodiment of a pilot-assisted code division multiplexing communication apparatus according to the present invention.
FIG. 2 is a diagram illustrating a waveform of a completely complementary sequence having a length of L = 4 chips and composed of M = 2 pairs in which M = 2 sequences are element sequences.
FIG. 3 is a diagram illustrating a cyclic shift sequence generation process and waveforms.
FIG. 4 is a diagram illustrating a generation process and a waveform of a repetitive sequence.
FIG. 5 is a diagram showing a generation process and a waveform of a cyclic series.
FIG. 6 is a diagram illustrating a generation process and a waveform of a cyclic zero insertion serial sequence.
FIG. 7 is a diagram illustrating a generation process and a waveform of a transmission base spanned signal s ₀ .
FIG. 8 is a diagram illustrating a generation process and a waveform of a transmission base spanned signal s ₁ .
FIG. 9 is a functional block diagram on the receiving device side in code division multiplexing communication in a conventional configuration.
[Explanation of symbols]
100 Code Division Multiplexing Communication Device 200 Transmitting Device 202 Serial / Parallel Conversion Unit 204 First Multiplier Group 206 Second Multiplier Group 208 First Adder 210 Second Adder 212 First Modulator 214 Second Modulator 216 Transmission signal generator 218 Antenna 300 Receiver 302 Antenna 304 First reception baseband generator 306 Second reception baseband generator 308 Pilot response signal generator 310 First data response signal generator 312 2 data response signal generator 314 first transmission data signal demodulator 316 phase corrector group 318 second transmission data signal demodulator 320 third transmission data signal demodulator 322 parallel / serial converter

Claims

In a code division multiplex communication method in which data communication is performed using a completely complementary sequence,
On the sending side,
Spreading the transmitted data signal with a cyclic serial sequence generated based on a fully complementary sequence of pairs;
A frequency modulation of a signal obtained by spreading the transmission data signal with a predetermined carrier wave, and
On the receiving side,
A procedure of demodulating a received baseband signal from a received signal based on a predetermined local signal corresponding to the predetermined carrier;
A procedure of despreading the received baseband signal with a cyclic zero insertion serial sequence to obtain a data response signal,
The cyclic serial sequence generates a cyclic shift sequence by repeating the operation of moving the rear one chip of the complete complementary sequence of length L paired to the front outside k times, and repeating the cyclic shift sequence a plurality of times. It is obtained by generating a repetitive sequence, and sequentially connecting paired element sequences that can be obtained by adding the rear L-1 chips of the repetitive sequence outside the front of the repetitive sequence,
The cyclic zero insertion serial sequence is obtained by sequentially connecting in series a pair of element sequences obtained by adding L-1 0s to the outer front of the repetitive sequence. Code division multiplexing communication method.

In a code division multiplexing communication device that performs data communication between transmitting and receiving devices using a completely complementary sequence,
The transmitter is
Spreading means for spreading a transmission data signal by a cyclic serial sequence generated based on a perfectly complementary sequence of pairs;
Modulation means for frequency-modulating a signal obtained by spreading the transmission data signal with a predetermined carrier wave,
The receiving device is:
Demodulation means for demodulating a received baseband signal from a received signal based on a predetermined local signal corresponding to the predetermined carrier;
A data response signal generating means for despreading the received baseband signal with a cyclic zero insertion serial sequence to obtain a data response signal;
The cyclic serial sequence generates a cyclic shift sequence by repeating the operation of moving the rear one chip of the complete complementary sequence of length L paired to the front outside k times, and repeating the cyclic shift sequence a plurality of times. It is obtained by generating a repetitive sequence, and sequentially connecting paired element sequences that can be obtained by adding the rear L-1 chips of the repetitive sequence outside the front of the repetitive sequence,
The cyclic zero insertion serial sequence is obtained by sequentially connecting in series a pair of element sequences obtained by adding L-1 0s to the outer front of the repetitive sequence. Code division multiplex communication device.