JP4787980B2 - Electron beam scanning antenna control circuit and electron beam scanning antenna apparatus provided with the control circuit - Google Patents

Description

  The present invention generally relates to an electron beam scanning antenna apparatus, and more particularly to an improvement in control technology of an electron beam scanning antenna in an electron beam scanning antenna apparatus.

  The electron beam scanning antenna device, for example, adjusts the phase of electromagnetic waves emitted from each of the antenna elements arranged in an array by using a phase shifter or the like, and the electromagnetic waves are emitted as an antenna beam in an arbitrary specific direction. Thus, the directivity of the emitted electromagnetic wave can be increased. Therefore, as its application, an automatic tracking type electron beam scanning antenna device (for example, mounted in a ship or an automobile) that directs an electromagnetic wave emitted in the direction of a moving target (artificial satellite, airplane, etc.), or on the ground There is an electron beam scanning antenna device mounted on a satellite for controlling the direction of the electron beam to be irradiated. These electron beam scanning antenna devices are provided with a phase shifter for each antenna element, and the direction in which the electron beam sensitivity is maximized (or the direction in which the directivity of the electron beam is increased) is dynamically controlled by a control circuit. It has the feature that it can be adjusted.

  FIG. 8 shows a conventional electron beam scanning antenna apparatus. A conventional typical electron beam scanning antenna device 800 includes an antenna element 801, a phase shifter 802, a power distributor 803, a transmitter 804, and a control circuit 805. The operation of the apparatus 800 will be outlined. First, a high frequency signal is output from the transmitter 804 and input to the power distributor 803. The power distributor 803 distributes the high-frequency signal into a plurality of parts, and the distributed high-frequency signal is input to each of the phase shifters 802. Each phase shifter 802 sets the phase of the high-frequency signal adjusted to emit a highly directional electron beam (hereinafter referred to as “main beam”). A high-frequency signal based on the phase set by the phase shifter 802 is input to the antenna element 801, becomes a main beam, and is radiated from the antenna element 801 to the space. When the receiving antenna is configured in relation to FIG. 8, the receiver 804b (not shown) replaces the transmitter 804, and the power combiner 803b (not shown) replaces the power distributor 803. Take.

  Here, the main beam is generated by calculating a necessary phase shift amount in the control circuit 805 and setting the calculation result in each of the phase shifters 802. That is, in the conventional system, when changing the direction of the main beam, the amount of phase shift required for all phase shifters is calculated individually by a computer, and all phase shifters are individually controlled by a control circuit. Processing was in progress. In this process, if the movement of the electron beam is to be controlled more smoothly, calculation for all phase shifters is required every shorter time, and high-speed control of the directivity of the electron beam becomes extremely difficult. There has been a problem that the power consumption of the entire beam scanning antenna device also increases.

  Therefore, in the prior art, an attempt has been made to realize an electron beam scanning antenna that can switch and control a beam at high speed with low power consumption and can improve reliability in order to solve the above-described problems (for example, patents). Reference 1). In this prior art, in order to direct the main beam radiated into the space in a predetermined direction, a set phase shift amount of a plurality of phase shifters is calculated in a control circuit, and the plurality of shifts based on the calculation result. By selecting a phase shifter to be controlled from the phase shifters and supplying power only to the selected phase shifter so as to direct the main beam in a predetermined direction, all the phase shifters are controlled. Without controlling the phase shifter, only the minimum necessary phase shifter is supplied and controlled.

JP 2003-152420 A

  However, also in the prior art and the above prior art, it is necessary to calculate all the set phase shift amounts of a plurality of target phase shifters in the control circuit, and the increase in the calculation amount in the computer, the phase shifter and the control The transmission time for setting values between circuits has been a problem for further speeding up. In addition, in the configuration in which control is performed for each phase shifter as in the prior art and the above-described prior art, the number of wirings between the phase shifter and the control circuit increases with an increase in function, which not only increases power consumption. Increasing the weight and space occupancy of the wiring cable occupying the entire apparatus becomes a problem. In other words, the conventional method of calculating the amount of phase shift for a plurality of configured antenna elements and transmitting it to each of the phase shifters leads to an increase in computer load, a complicated control circuit, and an increase in power consumption. As a result, an increase in weight and space occupancy due to the wiring cable occupying the entire apparatus are caused.

  Therefore, in view of the above problems, the present invention reduces the power consumption and heat generation of the control circuit in response to the miniaturization of the electron beam scanning antenna, reduces the weight of the control circuit and the entire apparatus, and is low in cost. An object of the present invention is to provide an electron beam scanning antenna control circuit that exhibits high-speed beam scanning performance, and an electron beam scanning antenna device including the control circuit.

An electron beam scanning antenna control circuit according to the present invention is an electron beam antenna control circuit for controlling an electron beam scanning antenna including at least a plurality of antenna elements and a phase shifter connected to each of the antenna elements. A phase shift amount calculation control circuit for calculating and controlling a part of the phase shift amount of each of the phase shifters as a control voltage, and a bilinear resistance network circuit having a plurality of resistors, The phase shifters are respectively connected to corresponding points of the resistor network through front end processors, and the resistor network is applied to the corresponding points for a part of each of the phase shifters. The control voltage as a phase shift amount generates a control voltage as a phase shift amount for each phase shifter at the corresponding point corresponding to another phase shifter, and the front-end processor Extracting the control voltage of each is the product from the corresponding point connected to each circuit, and sets a control value for the phase shifter of the respective.
An electron beam scanning antenna apparatus according to the present invention includes at least the electron beam scanning antenna control circuit.

  According to the present invention, only a few control amounts are calculated from the direction cosine representing the main beam direction, and the remaining control amount is automatically generated by a resistance network circuit (bilinear resistance network) or the like, which will be described later. The electron beam scanning can be performed at a reduced speed. Even if the number of antenna elements constituting the array increases, the number of signals to be transmitted directly from the computer interface to the control circuit does not increase, so that the wiring configuration of the entire electron beam scanning antenna apparatus can be kept simple. The weight of the entire apparatus can also be reduced. In addition, with the simplification of the circuit configuration, the reliability of the device is improved and low power consumption can be realized. Furthermore, as will be described later, since the control circuit can be configured with minute and inexpensive parts, the manufacturing cost and maintenance cost of the electron beam scanning antenna device can be reduced.

(Basic principle of the present invention)
An electron beam scanning antenna typically enables transmission and reception of electromagnetic waves with excellent directivity by arranging antenna elements in an array. Furthermore, by providing a phase shifter for each antenna element, the electron beam scanning antenna device has a feature that the direction in which the sensitivity of electromagnetic waves is maximized can be dynamically adjusted. The configuration of a general electron beam scanning antenna device is as described with reference to FIG.

Next, FIG. 9 shows a general relationship between the electron beam scanning antenna and the main beam direction. In FIG. 9, it is assumed that the electron beam scanning antenna is disposed on the xy plane. At this time, if the direction cosine of the main beam is given by (α, β, γ) as shown in FIG. 9, the desired beam direction is (θ, φ). In this case, θ is an angle (elevation angle) from the z-axis with respect to the direction cosine, and φ is a counterclockwise angle (azimuth angle) from the x-axis with respect to a line segment obtained by projecting the main beam onto the xy plane. ). Based on these definitions, the beam direction cosine (α, β, γ) can be expressed by the following equation.

と表わされる。ここで、ｉ及びｊは、１からＮまでの自然数である。そうすると、アンテナの四隅に置かれたアンテナ素子の中心座標は、それぞれ、

と表わすことができる。 Next, for example, if an N × N array with the distance between the centers of each antenna element as d is developed on a two-dimensional plane composed of orthogonal x-coordinates and y-coordinates, The center coordinates of each antenna element are

It is expressed as Here, i and j are natural numbers from 1 to N. Then, the center coordinates of the antenna elements placed at the four corners of the antenna are

Can be expressed as

だけずらす（移相する）必要がある。以下、Φ_ijを「移相量」ということとする。なお、ｋはマイクロ波の波長λによって決まる定数であって、

と表わすことができる。πは円周率である。また、α及びβは、所謂方向余弦であるから、

と表わすことができる。ここで、ｃ₁及びｃ₂は、ｘ-ｙ平面における座標の平行移動によって発生する係数であるが、すべてのアンテナ素子に共通に発生するものであるから指向性に影響を与えることはない。また、ｃ₃もすべてのアンテナ素子に共通であり、かつ、αにもβにも依存しないので指向性に影響を与えることはない。 Here, in order to set the direction of the electron beam scanning antenna as described above to (θ, φ) in polar coordinate display with the direction perpendicular to the xy plane (z-axis in FIG. 9) as the zenith. Is the phase of the antenna elements arranged at (x _i , y _j )

It is necessary to shift (shift) only. Hereinafter, Φ _{ij is referred} to as “phase shift amount”. K is a constant determined by the wavelength λ of the microwave,

Can be expressed as π is the circumference ratio. Also, since α and β are so-called direction cosines,

Can be expressed as Here, c ₁ and c ₂ are coefficients generated by translation of coordinates in the xy plane, but do not affect directivity because they are generated in common to all antenna elements. Also, c ₃ is common to all antenna elements and does not depend on α or β, so that directivity is not affected.

とすればよいが、具体的に例示すると煩雑となる一方で発明の本質に異なる所はないので、本明細書においては上述した簡素な構成に基づいて説明を進めることとする。 In addition, regarding the arrangement of the antenna elements, in order to be able to express even in a more general case (for example, when the antenna elements are arranged in a zigzag arrangement),

However, since it is complicated when specifically exemplified, there is no difference in the essence of the invention, and therefore, the description will proceed based on the above-described simple configuration.

(Specific configuration example of an electron beam scanning antenna control circuit according to the present invention and an electron beam scanning antenna apparatus provided with the control circuit)
FIG. 1 shows a configuration of an electron beam scanning antenna device 100 according to an embodiment of the present invention. The electron beam scanning antenna apparatus 100 includes a plurality of antenna elements 101, a phase shifter 102 connected to each antenna element, a power distributor 103, a transmitter 104, a control circuit 105, and a phase control signal generation circuit. 106 and a front-end processor 108. The operation of the apparatus 100 will be outlined. First, a high-frequency signal is output from the transmitter 104 and input to the power distributor 103. The power distributor 103 distributes the high-frequency signal into a plurality of parts, and the distributed high-frequency signal is input to each of the phase shifters 102. Each phase shifter 102 adjusts the phase of the high frequency signal adjusted to radiate the main beam. A high-frequency signal based on the phase set by the phase shifter 102 is input to the antenna element 101 and becomes a main beam, and is radiated from the antenna element 101 to the space.

Here, the directing direction of the main beam is determined by each set value of the phase shifter 102 based on the phase shift amount (control amount) information received from the phase control signal generation circuit 106 via the front end processor 108. . The front-end processor 108 is installed for each phase shifter, receives an analog signal from the phase control signal generation circuit 106 as described later, and generates a set value for each phase shifter 102 as a digital signal. For example, each front-end processor 108 is arranged at a grid point on the array antenna (substantially coincides with the position of the antenna element) and is connected to a corresponding point in the phase control signal generation circuit 106. For example, when the array antenna is configured as a square array composed of 8 × 8 lattice points (respectively lattice points P (i, j), where i and j are integers of 1 to 8), The front-end processor 108 on the lattice also has 8 × 8 corresponding points (respectively corresponding points Q (i, j)) configured in the phase shift control signal generation circuit, where i and j are integers of 1 to 8. ) Are connected to corresponding positions in the circuit having. That is, the front-end processor on the array antenna located at P (i, j) is connected to the corresponding point Q (i, j) of the phase control signal generation circuit.
The control circuit 105 calculates a control voltage as necessary, controls transmission / reception of analog / digital signals, and controls each module in the apparatus. Therefore, the control circuit 105 and the phase control signal generation circuit 106 function as an electron beam scanning antenna control circuit 107 for scanning the main beam. Note that a serial signal line (not shown) for directly controlling the front-end processor 108 is wired from the control circuit 105.

  Next, FIG. 2 shows a basic concept of the phase control signal generating circuit in the present invention. As described above, the electron beam scanning antenna apparatus according to the present invention includes the electron beam scanning antenna control circuit 107 including the control circuit 105 and the phase control signal generation circuit 106. The phase control signal generation circuit 106 is illustrated in FIG. It can be composed of a resistance network circuit (or a bilinear resistance network) as shown. Then, as shown in the figure, at a plurality of potential points (usually far more than N) in a resistor network having N applied voltage points (N is a natural number) from the first to Nth points. The basic concept of the present invention is to read out the automatically generated control voltages. In other words, the automatically generated control voltage means that a calculation operation by a computer as has been conventionally done is not required.

FIG. 3 shows the basic concept of the phase control signal generation circuit when N = 4. As shown in FIG. 3, the phase control signal generation circuit includes a square (or rectangular) resistor network circuit 300, and the first to fourth potential points 301 to 304 at the four corners are respectively connected to the first to fourth potential points 301 to 304. An applied voltage is applied. Here, a certain proportional relationship is established between the voltages applied to the four corners of the resistor network and the phases generated at the four corners of the antenna, which will be described in detail later. Here, the first applied voltage is V ₁ , the second applied voltage is V ₂ , the third applied voltage is V ₃ , and the fourth applied voltage is V ₄ . Thus, a control voltage is automatically generated at a predetermined potential point in the resistance network circuit 300, and the phase shift amount necessary for the phase shifter can be acquired by reading the control voltage. A plurality of potential points from which the control voltage can be read out can be provided (described later).

Next, FIG. 4 illustrates a configuration concept of the phase control signal generation circuit in the electron beam scanning antenna apparatus of the embodiment of the present invention. The phase control signal generation circuit shown in FIG. 4 includes a resistor network circuit 400. Among the first to fourth potential points 401 to 404 at the four corners, the first applied voltage V ₁ is applied to the first potential point 401. The second applied voltage V ₂ is applied to the second potential point 402, and the third applied voltage V ₃ is applied to the third potential point 403. The fourth potential point 404 is connected to automatic voltage generating means 405 for automatically generating the voltage V ₄ (= V ₁ + V ₃ −V ₂ ), and the applied voltages V _{1 to} V ₃ are set as described above. When applied to the first potential point 401 to the third potential point 403, the voltage V ₄ is automatically generated at the fourth potential point 404. The automatic voltage generating means 405 is composed of an operational amplifier, and voltages V ₁ , V ₂ , and V ₃ are applied to the input terminals, respectively. Next, it is derived that the voltage V ₄ automatically generated at the fourth potential point 404 is represented by V ₁ + V ₃ −V ₂ .

の位置に置かれたアンテナ素子に必要な移相量Φ_N1，Φ_NN，Φ_1N，Φ₁₁を指定することによってその他のアンテナ素子の移相量を自動的に決定することが基本的な動作原理である。 (Basic Principle of Phase Control Signal Generating Circuit According to the Present Invention)
In the electron beam scanning antenna control circuit according to the present invention, the four corners of the electron beam scanning antenna, that is,

The basic operation is to automatically determine the phase shift amount of the other antenna elements by specifying the phase shift amounts Φ _N1 , Φ _NN , Φ _1N , Φ ₁₁ necessary for the antenna element placed at the position of The principle.

具体的に移相量を決めるためには、ｃ₁，ｃ₂，ｃ₃をあらかじめ決めておかねばならないようにも思える。しかし、移相量は、相対的なものであるから共通項αｃ₁＋βｃ₂＋ｃ₃における係数ｃ₁，ｃ₂，ｃ₃は、具体的適用において取り扱いが容易になるように設定すればよい。 Here, the phase shift amounts at the four corners of this electron beam scanning antenna are expressed by the following equation using equation (10).

It seems that c ₁ , c ₂ , and c ₃ must be determined in advance to determine the amount of phase shift specifically. However, since the phase shift amounts are relative, the coefficients c ₁ , c ₂ , and c ₃ in the common term αc ₁ + βc ₂ + c ₃ may be set so as to be easily handled in a specific application.

における移相量を定数Φ₀とおけば、

が、可能なあらゆるα，βに対して成立しなければならない。そうすると、

を導くことができる。これらの係数を用いて式（１０）を書き改めると、

となる。 For example,

If the phase shift amount at is a constant Φ ₀ ,

Must hold for every possible α, β. Then

Can guide you. Rewriting equation (10) using these coefficients,

It becomes.

  When N in the above formula is an odd number, an antenna element exists at the coordinate. However, when N is an even number, there is no antenna element at the coordinate. Thus, in a specific application, the antenna element whose phase is to be fixed is not necessarily the central element.

である。したがって、以下のように、四隅の電圧を設定したときに、その他のＶ_ijがｉ，ｊに対して線形に変化するよう構成された、例えば抵抗網回路（又は、双線形抵抗ネットワーク）を用いると所要の目的を達成することができる。

On the other hand, if the proportional coefficient between the voltage V _ij applied to the phase shifter and the amount of phase shift is k ′ (such a phase shifter is called an analog phase shifter),

It is. Therefore, for example, a resistor network circuit (or a bilinear resistor network) configured so that the other V _ij changes linearly with respect to i and j when the voltages at the four corners are set as follows. And achieve the desired purpose.

A phase shifter that can be controlled by applying a digital signal to the analog phase shifter is called a digital phase shifter. When the digital phase shifter is controlled in the electron beam scanning antenna apparatus according to the present invention, V _ij is converted into a digital value using an AD converter or the like, and the digital signal is applied to the phase shifter. Can be controlled.

とおく。そうすると、式（２０）〜式（２３）を式（３１）〜式（３４）を経由して、式（３５）〜式（３８）に代入すると明らかなように、Ｖ₁，Ｖ₂，Ｖ₃，Ｖ₄の間には、

の関係が成り立つ。従って、計算機を使用してＶ₁，Ｖ₂，Ｖ₃，Ｖ₄の電圧を計算し、これらを抵抗網等に印加する代わりに、例えば、Ｖ₁，Ｖ₂，Ｖ₃の電圧は計算機により計算して抵抗網に印加する一方で、Ｖ₄については、

の関係を用いて、ハードウェアを用いて自動生成することができる。この自動生成の手段としては演算増幅器等を用いることができるが、その詳細構成については後述する。 Next, to simplify the discussion,

far. Then, as is clear from substituting Equations (20) to (23) into Equations (35) to (38) via Equations (31) to (34), V ₁ , V ₂ , V between _3, V ₄ is,

The relationship holds. Therefore, instead of calculating the voltages V ₁ , V ₂ , V ₃ , and V ₄ using a computer and applying them to a resistor network, for example, the voltages V ₁ , V ₂ , and V ₃ are calculated by the computer. while calculated and applied to the resistor network, the V ₄ is

Using this relationship, it can be automatically generated using hardware. An operational amplifier or the like can be used as the automatic generation means, and the detailed configuration thereof will be described later.

が成り立つことにも着目すれば、Ｖ₁，Ｖ₂の電圧は計算機によって計算して抵抗網等に印加する一方で、Ｖ₃及びＶ₄については、適切なハードウェアを用いて

の関係より自動生成することができる。この自動生成の手段としては演算増幅器等を用いることができるが、その詳細構成については後述する。 Furthermore, from the relational expression of Expression (25) and Expression (39)

Note that V ₁ and V ₂ are calculated by a computer and applied to a resistor network or the like, while V ₃ and V ₄ are used with appropriate hardware.

It can be automatically generated from the relationship. An operational amplifier or the like can be used as the automatic generation means, and the detailed configuration thereof will be described later.

FIG. 5 shows a specific circuit configuration of the phase control signal generating circuit shown in FIG. The phase control signal generation circuit in FIG. 5 is specifically configured as a resistance network circuit 500, and has potential points V ₁₁ , V ₁₅ , V ₅₁ , and V ₅₅ at four corners. Resistors R ₂ , R ₃ , R ₄ , R ₅ are connected in series between the potential point V ₁₁ and the potential point V _15, and the potential points V ₁₂ , V ₁₃ , V ₅ are connected between the resistors. ₁₄ is provided. Further, resistors R ₇ , R ₁₃ , and R ₁₉ are connected in series between the potential point V ₁₁ and the potential point V _51, and potential points V ₂₁ , V ₃₁ , and V ₄₁ are provided between the resistors. It has been. Similarly, resistors R ₂₅ , R ₂₆ , R ₂₇ , R ₂₈ are connected in series between the potential point V ₅₁ and the potential point V _55, and the potential points V ₅₂ , V _{53,. V54} is provided. Further, resistors R ₁₂ , R ₁₈ , R ₂₄ are connected in series between the potential point V ₅₅ and the potential point V _15, and potential points V ₂₅ , V ₃₅ , V ₄₅ are provided between the resistors. It has been. As described above, a voltage distribution circuit (ladder resistance circuit) that distributes the applied voltages at both ends at an equal ratio is formed between the potential points across the resistors connected in series (hereinafter, in FIG. 7). Is the same).

Between the potential point V ₂₁ and potential point V ₂₅ in FIG. 5, a unity gain buffer U1, resistors _{R 8, R 9, R 10} , R 11, unity gain buffer U2 is connected in series The unity gain buffers U1 and U2 are arranged so that their output sides face each other. Therefore, potential point V ₂₁ is the input side of the unity gain buffer U1: is connected to a (P positive input terminal), potential point V ₂₅ is the input side of the unity gain buffer U2: is connected to a (P positive input terminal) Yes. As described above, a voltage distribution circuit that distributes the applied voltages at both ends at an equal ratio without affecting the voltage division characteristics is configured between the potential point V ₂₁ and the potential point V ₂₅ (hereinafter, referred to as “voltage distribution circuit”). The same applies to other potential points in FIG. 5 and in FIG.

Similarly, between the potential point V ₃₁ and a potential point V ₃₅ in FIG 5, a unity gain buffer U3, resistors _{R 14, R 15, R 16} , R 17, unity gain buffer U4 are connected in series The unity gain buffers U3 and U4 are arranged so that their output sides face each other. Therefore, potential point V ₃₁ is the input side of the unity gain buffer U3: is connected to a (P positive input terminal), potential point V ₃₅ is the input side of the unity gain buffer U4: is connected to a (P positive input terminal) Yes.

In addition, a unity gain buffer U5, resistors R ₂₀ , R ₂₁ , R ₂₂ , R ₂₃ , and unity gain buffer U6 are connected in series between potential point V ₄₁ and potential point V ₄₅ in FIG. The unity gain buffers U5 and U6 are arranged so that their output sides face each other. Therefore, potential point V ₄₁ is the input side of the unity gain buffer U5: is connected to a (P positive input terminal), potential point V ₄₅ is the input side of the unity gain buffer U6: is connected to a (P positive input terminal) Yes.

  The unity gain buffers U1 to U6 in FIG. 5 have unity gain buffer configurations using operational amplifiers, but are not limited to this, and appropriate circuit configurations can be employed.

In FIG. 5, for convenience of description, for example, the voltage value at the potential point V ₁₂ is also set to V ₁₂ (see the lower enlarged view of FIG. 5). That V ₁₂ represents the position or the contact terminals of the term "potential point V _12", V ₁₂ denote the voltage value of the term "voltage V _12" or "control voltage V _12". The same applies to other potential points and voltage values in FIG. The resistors R _{1 to} R ₂₈ are obviously not required to have a resistance value within a specific range due to the nature of the present invention, but power consumption, time delay due to time constant, etc. are taken into consideration. However, a practical range of about 100Ω to 1KΩ can be used. In principle, the same resistance value is used, but it is also possible to improve the performance by appropriately fine-tuning (tuning) individual elements. The error in the resistance value is within about 0.5% (approximately 1: 200) even when a general inexpensive resistance element is used, and with sufficient accuracy to handle 7-bit information. is there. If an error of about 0.3% is used, it can be said that the accuracy is sufficient to handle 8-bit information. Therefore, the cost required for implementing the present invention can be kept extremely low.

  Also, the reason why the unity gain buffers U1 to U6 are used as described above when configuring the resistor network circuit 500 in FIG. 5 is to increase the bilinearity as the resistor network circuit so as not to affect the voltage division characteristics. It is to make it. That is, when the resistor network circuit 500 is configured in a lattice shape with only resistors, the linearity of the voltage distribution is deteriorated, and a biased distribution such as so-called “spherical aberration” is generated. Further, when the unity gain buffer is not used, it is necessary to individually correct the distribution with the bias as described above by a computer. Alternatively, it is necessary to finely adjust the resistance value of each resistor so that the voltage distribution approaches a square mesh.

The potential point V ₅₁ in FIG. 5 is connected to the output side of the operational amplifier as the automatic voltage generation means 505. As shown in FIG. 5, the voltages V1 and V3 are respectively applied in parallel through resistors on the input side of the automatic voltage generating means 505 (positive input terminal side), and the voltage V2 is applied to the other through the resistor. Yes (negative input terminal side). The output is fed back to the input (negative input terminal side) through a resistor.

The configuration and the voltage applied as described above, the potential point V ₅₁ control voltage V4 = V1 + V3-V2 is automatically generated. In addition, the bi-linearity of the resistance network circuit 500, the control voltage V ₁₂ is the potential point V ₁₂ is the control voltage V ₁₃ is the potential point V ₁₃ is the control voltage V ₁₄ is the potential point V ₁₄ is, potential point control voltage V ₂₁ to V ₂₁ is the control voltage V ₂₂ is the potential point V ₂₂ is the control voltage V ₂₃ is the potential point V ₂₃ is the control voltage V ₂₄ is the potential point V _24, potential point V ₂₅ the control voltage V ₂₅ is the control voltage V ₃₁ is the potential point V ₃₁ is the control voltage V ₃₂ is the potential point V ₃₂ is the control voltage V ₃₃ is the potential point V ₃₃ is the potential point V ₃₄ is control voltage V ₃₄ is the control voltage V ₃₅ is the potential point V _35, the control voltage V ₄₁ is the potential point V ₄₁ is the control voltage V ₄₂ is the potential point V ₄₂ is the potential point V ₄₃ control voltage V ₄₃ is the control voltage V ₄₄ is the potential point V _44, the control voltage V ₄₅ is the potential point V ₄₅ is the control voltage V ₅₂ is the potential point V ₅₂ is controlled in potential point V ₅₃ voltage V ₅₃ However, the potential V ₅₄ has a control voltage V ₅₄ are automatically generated bilinearly.

Next, FIG. 6 illustrates a configuration concept of another phase control signal generation circuit in the electron beam scanning antenna apparatus of the embodiment of the present invention. The phase control signal generation circuit shown in FIG. 6 is specifically configured as a resistance network circuit 600, and the first applied voltage is applied to the first potential point 601 among the first to fourth potential points 601 to 604 at the four corners. V ₁ is applied, and the second applied voltage V ₂ is applied to the second potential point 602. The third potential point 603 is connected to automatic voltage generating means 605 for automatically generating the voltage V ₃ , and the fourth potential point 604 is automatically generated for automatically generating the voltage V _4. Means 606 are connected. When the applied voltages V ₁ and V ₂ are applied to the first potential point 601 and the second potential point 602, respectively, the voltage V ₃ is applied to the third potential point 603 and the fourth potential point 604 is applied. Each of the voltages V ₄ operates so as to be automatically generated. The automatic voltage generators 605 and 606 are each constituted by a two-input operational amplifier. Voltages V ₁ and V ₀ are applied to the input of the automatic voltage generator 605, respectively, and the automatic voltage generator 606 has an input. Voltages V ₂ and V ₀ are applied, respectively. Here, the voltage V ₃ automatically generated at the third potential point 603 is V ₀ −V ₁ , and the voltage V ₄ automatically generated at the fourth potential point 604 is V ₀ −V _2. That's what I already mentioned.

FIG. 7 shows a specific circuit configuration of the phase control signal generating circuit shown in FIG. The phase control signal generation circuit in FIG. 7 is specifically configured by a resistance network circuit 700 and has potential points V ₁₁ , V ₁₅ , V ₅₁ , and V ₅₅ at four corners. Resistors R ₂ , R ₃ , R ₄ , R ₅ are connected in series between the potential point V ₁₁ and the potential point V _15, and the potential points V ₁₂ , V ₁₃ , V ₅ are connected between the resistors. ₁₄ is provided. Further, resistors R ₇ , R ₁₃ , and R ₁₉ are connected in series between the potential point V ₁₁ and the potential point V _51, and potential points V ₂₁ , V ₃₁ , and V ₄₁ are provided between the resistors. It has been. Similarly, resistors R ₂₅ , R ₂₆ , R ₂₇ , R ₂₈ are connected in series between the potential point V ₅₁ and the potential point V _55, and the potential points V ₅₂ , V _{53,. V54} is provided. Further, resistors R ₁₂ , R ₁₈ , R ₂₄ are connected in series between the potential point V ₅₅ and the potential point V _15, and potential points V ₂₅ , V ₃₅ , V ₄₅ are provided between the resistors. It has been.

Between the potential point V ₂₁ and potential point V ₂₅ in FIG. 7, a unity gain buffer U1, resistors _{R 8, R 9, R 10} , R 11, unity gain buffer U2 is connected in series The unity gain buffers U1 and U2 are arranged so that their output sides face each other. Therefore, potential point V ₂₁ is the input side of the unity gain buffer U1: is connected to a (P positive input terminal), potential point V ₂₅ is the input side of the unity gain buffer U2: is connected to a (P positive input terminal) Yes.

Similarly, between the potential point V ₃₁ and potential point V ₃₅ in FIG. 7, a unity gain buffer U3, resistors _{R 14, R 15, R 16} , R 17, unity gain buffer U4 are connected in series The unity gain buffers U3 and U4 are arranged so that their output sides face each other. Therefore, a potential point V ₃₁ is the input side of the unity gain buffer U3: is connected to a (P positive input terminal), potential point V ₃₅ is the input side of the unity gain buffer U4: is connected to a (P positive input terminal) Yes.

In addition, a unity gain buffer U5, resistors R ₂₀ , R ₂₁ , R ₂₂ , R ₂₃ , and unity gain buffer U6 are connected in series between potential point V ₄₁ and potential point V ₄₅ in FIG. The unity gain buffers U5 and U6 are arranged so that their output sides face each other. Therefore, potential point V ₄₁ is the input side of the unity gain buffer U5: is connected to a (P positive input terminal), potential point V ₄₅ is the input side of the unity gain buffer U6: is connected to a (P positive input terminal) Yes.

  The unity gain buffers U1 to U6 in FIG. 5 have unity gain buffer configurations using operational amplifiers, but are not limited to this, and appropriate circuit configurations can be employed.

In FIG. 7, for convenience of description, for example, the voltage value at the potential point V ₁₂ is also set to V ₁₂ (see the lower enlarged view of FIG. 7). That V ₁₂ represents the position or the contact terminals of the term "potential point V _12", V ₁₂ denote the voltage value of the term "voltage V _12" or "control voltage V _12". The same applies to other potential points and voltage values in FIG. Also, the resistors R _{1 to} R ₂₈ to be used are the same as those shown in FIG. 5. For example, even when a general inexpensive resistor element is used, the error is about 0.5% (approximately one pair). 200), and sufficient accuracy can be secured to handle 7-bit information. Therefore, the cost required for implementing the present invention can be kept extremely low.

  Also, the reason why the unity gain buffers U1 to U6 are used as described above when configuring the resistance network circuit 700 in FIG. 7 is to increase the bilinearity as the resistance network circuit so as not to affect the voltage division characteristics. It is to make it. That is, when the resistance network circuit 700 is configured in a lattice shape with only resistors, the linearity of the voltage distribution is deteriorated and a biased distribution such as so-called “spherical aberration” is generated. The buffers U1 to U6 are used as shown to improve the bilinearity as a resistance network circuit.

The potential point V ₁₁ in FIG. 7 is connected to the output side of the operational amplifier as the automatic voltage generating means 705. As shown in FIG. 7, the voltage V0 is applied to the input side of the automatic voltage generating means 705 via a resistor (positive input terminal side), and grounded between the resistor and the positive input terminal via another resistor. Has been. In addition, the voltage V1 is applied to the other via a resistor (negative input terminal side). The output is fed back to the input (negative input terminal side) through a resistor.

The potential point V ₅₁ in FIG. 7 is also connected to the output side of the operational amplifier as the automatic voltage generating means 706. As shown in FIG. 7, the voltage V0 is applied to the input side of the automatic voltage generation means 706 via a resistor (positive input terminal side), and grounded between the resistor and the positive input terminal via another resistor. Has been. In addition, the voltage V1 is applied to the other via a resistor (negative input terminal side). The output is fed back to the input (negative input terminal side) through a resistor.

The configuration and the voltage applied as described above, the control voltage of V3 = V0-V1 is the potential point V ₁₁ is automatically generated, the potential point V ₅₁ control voltage V4 = V0-V2 are automatically generated. In addition, the bi-linearity of the resistance network circuit 700, the control voltage V ₁₂ is the potential point V ₁₂ is the control voltage V ₁₃ is the potential point V ₁₃ is the control voltage V ₁₄ is the potential point V ₁₄ is, potential point control voltage V ₂₁ to V ₂₁ is the control voltage V ₂₂ is the potential point V ₂₂ is the control voltage V ₂₃ is the potential point V ₂₃ is the control voltage V ₂₄ is the potential point V _24, potential point V ₂₅ the control voltage V ₂₅ is the control voltage V ₃₁ is the potential point V ₃₁ is the control voltage V ₃₂ is the potential point V ₃₂ is the control voltage V ₃₃ is the potential point V ₃₃ is the potential point V ₃₄ is control voltage V ₃₄ is the control voltage V ₃₅ is the potential point V _35, the control voltage V ₄₁ is the potential point V ₄₁ is the control voltage V ₄₂ is the potential point V ₄₂ is the potential point V ₄₃ control voltage V ₄₃ is the control voltage V ₄₄ is the potential point V _44, the control voltage V ₄₅ is the potential point V ₄₅ is the control voltage V ₅₂ is the potential point V ₅₂ is controlled in potential point V ₅₃ voltage V ₅₃ However, the potential V ₅₄ has a control voltage V ₅₄ are automatically generated bilinearly.

(Applicability of the present invention)
In general, for example, an electron beam scanning antenna having a substantially circular peripheral shape is frequently used. On the other hand, in the embodiment of the present invention, the case of having a square (quadrangle) peripheral shape has been mainly described, but the present invention can also be applied to a faced array antenna having a more complicated peripheral shape. That is, even the electron beam scanning antenna having the complicated peripheral shape can be handled as constituting a part of a virtually larger square electron beam scanning antenna. Then, by controlling the phase shift amount of the virtual antenna element at the four corners of the square (quadrangle), the resistor network is configured so that V _ij inside thereof changes linearly with respect to i and j. be able to. Therefore, the electron beam scanning antenna control circuit and apparatus according to the present invention can be controlled by applying the technical idea of the present invention even if the antenna shape is an electron beam scanning antenna having a more complicated peripheral shape. .

  Further, in an electron beam scanning antenna used in a ship or the like, it is desirable that directivity can be controlled over a wide range of solid angles from the horizon to the zenith. Therefore, it is convenient if the electron beam scanning antenna can be developed on a hemispherical surface. On the other hand, the electron beam scanning antenna control circuit according to the present invention has been described mainly with respect to the control of the electron beam scanning antenna developed on a plane, but the electron beam scanning antenna developed on a surface having a three-dimensional shape such as a spherical surface. The same applies to the above. That is, even a three-dimensional shape can be covered with a combination of planar polygons such as a triangle, a quadrangle, and a pentagon with the required accuracy. Then, using the same method as the method for the quadrangle described above, It is possible to control an electron beam scanning antenna deployed in a planar polygon. Therefore, even the electron beam scanning antenna provided on the three-dimensional surface can be controlled by the electron beam scanning antenna control circuit and apparatus according to the present invention by dividing the surface into an appropriate shape.

  As described above, according to the present invention, it is possible to solve the problem of increase in apparatus weight and cost due to an increase in computer load, a complicated control circuit, and an increase in power consumption. The electron beam scanning antenna control circuit that reduces the power consumption and heat generation of the control circuit and reduces the weight of the control circuit and the entire apparatus, and that exhibits high-speed beam scanning performance at a low cost. An electron beam scanning antenna apparatus including a control circuit can be provided.

It is a block diagram which shows the structure of the electron beam scanning antenna apparatus in embodiment of this invention. It is explanatory drawing explaining interfaces, such as signal input / output of the front end processor and phase control signal generation circuit in the electron beam scanning antenna apparatus of embodiment of this invention. It is explanatory drawing explaining the basic concept of the phase control signal generation circuit of this invention. It is explanatory drawing explaining the structural concept of the phase control signal generation circuit in the electron beam scanning antenna apparatus of embodiment of this invention. FIG. 5 is a circuit explanatory diagram illustrating a specific circuit configuration of the phase control signal generating circuit shown in FIG. 4. It is explanatory drawing explaining the structural concept of the other phase control signal generation circuit in the electron beam scanning antenna apparatus of embodiment of this invention. FIG. 7 is a circuit explanatory diagram illustrating a specific circuit configuration of the phase control signal generating circuit shown in FIG. 6. It is a block diagram which shows the typical structure of the conventional electron beam scanning antenna apparatus. It is explanatory drawing which shows the general relationship between an electron beam scanning antenna and a main beam direction.

Explanation of symbols

DESCRIPTION OF SYMBOLS 100 Electron beam scanning antenna apparatus 101 Antenna element 102 Phase shifter 103 Divider 105 Control circuit 106 Phase control signal generation circuit (resistance network circuit, bilinear resistance network)
107 Electron Beam Scanning Antenna Control Circuit 108 Front End Processor (FEP)
300 Resistance network (bilinear resistance network)
405, 505, 605, 606, 705, 706 Voltage automatic generation means 801 Antenna element 802 Phase shifter 803 Divider 804 Transmitter 805 Control circuit

Claims (10)

An electron beam antenna control circuit for controlling an electron beam scanning antenna comprising a plurality of antenna elements and a phase shifter connected to each of the antenna elements,
A phase shift amount calculation control circuit for calculating and controlling a part of the phase shift amount of each of the phase shifters as a control voltage;
A bilinear resistance network having a plurality of resistors,
Each of the phase shifters is connected to a corresponding point of the resistor network circuit through a front-end processor,
The resistor network circuit has each phase shift to the corresponding point corresponding to another phase shifter by a control voltage as a phase shift amount applied to the corresponding point for a part of each of the phase shifters. Generating a control voltage as the amount of phase shift for the
The front-end processor extracts each of the generated control voltages from corresponding points connected to each of the resistor network circuits, and sets the extracted control voltages as control values for the respective phase shifters. Antenna control circuit. The plurality of antenna elements and the resistor network circuit are each configured in a rectangular shape,
The phase shift amount calculation control circuit calculates and controls the phase shift amounts at the four corners of the plurality of antenna elements configured in the rectangular shape as control voltages, and the control voltages are applied to the corresponding four corners on the resistance network circuit. 2. The electron beam antenna control circuit according to claim 1, wherein control is performed so that the voltage is applied as a control voltage. The plurality of antenna elements and the resistor network circuit are each configured in a rectangular shape,
The phase shift amount calculation control circuit calculates and controls the phase shift amount at three corners of the plurality of antenna elements configured in the rectangular shape as a control voltage, and the control voltage is applied to the corresponding three corners on the resistor network circuit. Control to apply as a control voltage,
The resistor network circuit is configured to automatically generate the control voltage of the remaining one corner from the control voltage applied to the corresponding three corners of the resistor network, and corresponds to the other phase shifter. 2. The electron beam antenna control circuit according to claim 1, wherein a control voltage as a phase shift amount for each phase shifter is generated at a corresponding point. The plurality of antenna elements and the resistor network circuit are each configured in a rectangular shape,
The phase shift amount calculation control circuit calculates and controls the phase shift amount at two corners of the plurality of antenna elements configured in the rectangular shape as a control voltage, and the control voltage is controlled by the corresponding two on the resistance network circuit. Control to apply as a control voltage to the corner,
The resistor network circuit is configured to automatically generate control voltages for the remaining two corners from control voltages applied to the corresponding two corners of the resistor network, and corresponds to other phase shifters. 2. The electron beam antenna control circuit according to claim 1, wherein a control voltage as a phase shift amount for each phase shifter is generated at the corresponding point. The plurality of antenna elements constitute an antenna array having a substantially circular peripheral shape,
The resistor network circuit is configured to correspond to a peripheral shape of the antenna array by a combination of a plurality of polygons, and each vertex of the plurality of polygons corresponds to a control voltage application point corresponding to the plurality of antenna elements. The electron beam antenna control circuit according to claim 1, wherein the electron beam antenna control circuit is attached.   4. The electron beam antenna control circuit according to claim 3, wherein the remaining one corner of the resistor network circuit is configured by an operational amplifier in which a control voltage applied to the three corners is applied to an input terminal. .   7. The electron beam antenna control according to claim 3, wherein the resistor network includes a voltage distribution circuit having at least one set of unity gain buffers formed of operational amplifiers. circuit. The remaining two corners of the resistor network are composed of a first operational amplifier and a second operational amplifier,
An applied voltage of at least one of the two corners on the resistor network is applied to the input terminal of the first operational amplifier,
5. The electron beam antenna control circuit according to claim 4, wherein at least one of the other two corners on the resistor network circuit is applied to an input terminal of the second operational amplifier.   9. The electron beam antenna control according to claim 4, wherein the resistor network comprises a voltage distribution circuit having at least one set of unity gain buffers configured by operational amplifiers. circuit.   An electron beam scanning antenna apparatus comprising the electron beam antenna control circuit according to claim 1.

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