JP4866645B2 - Waveguide-microstrip line conversion apparatus and method - Google Patents

Description

The present invention relates to microwave integrated circuits (MICs) and monolithic conversion devices, and more particularly to conversion between waveguides and microstrips for conversion devices operating at microwave and millimeter wave frequencies.

  In the past, design and development has been done to facilitate efficient conversion between waveguides and microstrips.

  These transformations can be used in various integrated circuit devices that operate in the RF, microwave and millimeter wave frequency bands.

  The conversion is useful for coupling between the front end of a system that transmits and receives electromagnetic (EM) waves and to act as a signal processing circuit that regulates, uses and / or converts EM waves into useful signals. be able to.

  FIG. 15 shows a conventional converter 1500 that converts between a waveguide and a microstrip (FIG. 8 of Patent Document 1).

  This conversion device includes an open-ended waveguide 1510 that is an input / output terminal, a substrate 1512, a terminal short-circuited waveguide (hereinafter referred to as a back short) 1514, a microstrip 1516, and an electrode 1518.

  The open-ended waveguide 1510 (opening width a and height b) can transmit or receive EM waves.

  The other end of the open-ended waveguide 1510 is attached to the substrate 1512.

  The substrate 1512 has a microstrip 1516 on which an electrode 1518 is formed.

  The back short 1514 is attached to the substrate 1512 on the opposite side to the open-ended waveguide 1510.

  As shown here, the back short 1514 is a terminated short-circuited waveguide having a length of at least a quarter wavelength (λ / 4) of the EM wave.

  In the conventional conversion device, the length of the back short 1514 is required to be sufficiently long in order to perform optimal conversion. An example is given below.

  For example, an incoming EM wave is received at the open end of the open-ended waveguide 1510 and propagates toward the substrate 1512 by the length of the open-ended waveguide 1510.

  A portion of the incident EM wave on the substrate 1512 is collected or converted by the electrode 1518.

  Some of the incident EM waves pass through the substrate 1512 and are reflected by the short-circuit end of the back short 1514.

  The reflected wave returns toward the electrode 1518 and is collected or converted at that electrode.

  Since the length of the conventional back short 1512 is λ / 4 or more, the reflected wave and the incident EM wave are combined in the same phase by the electrode 1518.

  The composite wave then induces a current at electrode 1518 that is conducted along microstrip 1516.

  FIG. 16 shows an equivalent circuit 1600 that models a conventional converter 1500.

  The first subcircuit 1610 models the open-ended waveguide 1510 and has a characteristic impedance Z1.

  The second subcircuit 1616 models the microstrip 1516 and has a characteristic impedance Z2.

  It is desirable to provide a matching circuit 1614 that connects the equivalent subcircuits so that power transmission is maximized.

  In order to design the matching circuit 1614, it is desirable to optimize the parameters of the open-ended waveguide 1510 and the microstrip 1516 so that the EM energy input from the open-ended waveguide 1510 is appropriately applied to the microstrip 1516. Changed.

  The first problem of the conventional conversion device 1500 is that it is difficult to perform impedance matching between the open-ended waveguide 1510 and the microstrip 1516 having relatively large differences in impedance. That is.

  For example, the characteristic impedance of the open-ended waveguide 1510 for frequency in the microwave region is usually about 300-500Ω, and the characteristic impedance of the microstrip 1516 for the same frequency is 50Ω.

  When the impedances are so different and the EM field interacts within the waveguide, it is difficult to achieve a suitable matching circuit 1614 and an elaborate three-dimensional circuit design must be utilized.

  Another problem with the conventional converter 1500 is the constraint that the back short 1514 must generally be longer than λ / 4.

  In other words, the back short circuit 1514 is required to be equivalent to an “open circuit” in view of a-a ′ illustrated in FIG. 16.

  As the frequency is lower, the back short length is longer. And when a frequency is lower than 10 GHz, it becomes a big problem in designing a converter.

  Since the size of the conventional conversion device was large, there was a problem that it could not be applied to a small device. .

In addition, the conventional conversion device has a problem of higher cost and lower reliability because the components are complex and the number of parts is large.
JP 2003-298322 A

  Therefore, the present invention relates to a waveguide-microstrip conversion device, and an object thereof is to reduce the size thereof and solve the above problems.

  An embodiment of the present invention includes an open-ended waveguide that is an input / output terminal, a substrate coupled to the open-ended waveguide, a resonator coupled to the substrate, and an electromagnetic coupling to the resonator. A waveguide-microstrip line conversion device comprising a microstrip line and a back short located opposite to the open-ended waveguide with respect to the substrate.

  Another embodiment of the present invention receives an electromagnetic wave, collects an incident part of the received electromagnetic wave, generates a first electromagnetic wave that resonates at a desired frequency using the incident part of the received electromagnetic wave, Reflecting the received electromagnetic wave to the collector side by a short circuit, generating a second electromagnetic wave that resonates at a desired frequency using the incident part of the received electromagnetic wave, and coupling the first and second electromagnetic waves. This is a wave tube-microstrip line conversion method.

  Still another embodiment of the present invention is formed integrally with an open-ended waveguide as an input / output terminal, a substrate coupled to the open-ended waveguide, an electrode coupled to the substrate, and the electrode. The electrode is installed at a location deviated from the center line of the resonator, and two slits are provided on both sides adjacent to the electrode on the resonator. A waveguide comprising: a microstrip line electromagnetically coupled to the resonator; and a terminal short-circuited waveguide positioned opposite to the open-ended waveguide with respect to the substrate. -A microstrip line converter.

  Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.

  The same reference numbers in different drawings denote the same or equivalent components.

  Also, the following detailed description does not limit the invention, and the scope of the invention is defined by the appended claims and their equivalents.

  FIG. 1 shows a first embodiment of a waveguide-microstrip line converter 100 in which electromagnetic (EM) waves propagate between the waveguide and the microstrip.

  The waveguide-microstrip line converter 100 includes an open-ended waveguide 110 serving as an input / output terminal, a substrate 112, a miniaturized back short 114, a microstrip 116, a resonator 118, and an electrode 120.

  The above-mentioned “miniaturization” means the size reduction of the back short 114 in all directions and dimensions including the propagation direction of the EM wave.

  For example, the miniaturized back short 114 is a back short having a length equal to or shorter than a quarter wavelength (λ / 4) of the EM wave in the dimension of the propagation direction of the EM wave.

  Note that the scale meaning the miniaturized back short 114 may be an arbitrary fraction less than 1 and is not limited to an integer fraction of the wavelength (λ).

  The embodiments of the present invention can be used mainly with EM waves having frequencies in the microwave region.

  However, EM waves are not limited to microwave frequencies and can operate in higher or lower frequency bands.

  For example, the embodiment can be applied to an EM wave having a frequency belonging to the RF frequency band.

  The substrate 112 is physically coupled to the opposite side of the distal opening of the open tip waveguide 110.

  On the opposite side of the substrate 112 that couples to the open-ended waveguide 110, the substrate 112 is physically coupled to the back short 114.

  The physical coupling of the substrate 112 and the waveguide can be accomplished by adhesives, fasteners, combinations thereof, and any other method in the prior art.

  Since the substrate 112 is disposed substantially perpendicular to the openings of the open-ended waveguide 110 and the back short 114, the substrate 112 is also directed to the direction of the EM wave propagating within the open-ended waveguide 110 and the substrate 112. It is almost vertical.

  However, other relative positional relationships of the substrate 112, the back short 114, and the open-ended waveguide 110 are possible as other embodiments of the present invention.

  The substrate 112 is coupled to a support structure 122, which may be, for example, a microwave integrated circuit (MIC) that performs processing operations and / or other functions on EM waves or related signals. A part of another conversion device and / or a conductor or the like.

  The back short 114 can be reduced in size with respect to the dimension of the propagation direction of the EM wave, and the size thereof is λ / 4 or less.

  The back short 114 can be realized using a waveguide having any shape such as a rectangular parallelepiped, a cylinder, and a trapezoidal column.

  In addition, the back short 114 can be realized using a printed circuit board material (PCB) having one or more layers, whereby a small thin back short is integrated with other circuits of the MIC to convert the device size Enables further downsizing.

  As an example, the multilayer PCB has a stepped portion in one layer, so that a back short can be formed, and an EM wave can be appropriately reflected at the stepped portion.

  The stepped layer can be formed with a metal coating or other surface layer to cause EM wave reflection.

  Another layer may be formed on the back short layer and include electrode 120 and resonator 118.

  The back short circuit using the PCB can be realized by a technique known to those skilled in the art.

  The open-ended waveguide 110 may be any generally known waveguide, and a rectangular parallelepiped waveguide is mainly used, but a cylindrical waveguide and a trapezoidal column waveguide are also used. Any other known waveguide can be used.

  In an embodiment, the open-ended waveguide 110 has a rectangular opening having a width of about 22 mm and a height of 10 mm, and is a rectangular parallelepiped having a length of about 25 mm.

  In this embodiment, the back short 114 is 7.3 mm, which is equal to or slightly less than λ / 4, and the height and width of the opening are the same dimensions as the open-ended waveguide 110.

  The substrate 112 is provided with the microstrip 116, the resonator 118, and the electrode 120 on the substrate surface on the opening side of the open-ended waveguide 110.

  The substrate 112 is formed from any dielectric material known to those skilled in the art in the prior art, such as a material used during PCB manufacture (eg, BT Resin or FR4 material).

  In the embodiment, the thickness of the substrate 112 is about 0.25 mm and has a dielectric constant of 3.5.

  The microstrip 116 is arranged in parallel with the electric field of the EM wave and tap-feeds the resonator 118.

  Tap feed here also applies to connecting the components directly so that they are electromagnetically coupled.

  In this embodiment, the resonator 118 can tap-feed the electrode 120.

  Microstrip 116 may be connected to other parts of the microwave circuit to further process signals associated with EM waves.

  The microstrip 116, resonator 118, and electrode 120 are generally formed from copper, but may be formed from aluminum or other materials known in the art to those skilled in the art.

  Since the microstrip 116, the resonator 118, and the electrode 120 can be formed by etching the surface layer of the substrate 112, there is an advantage that the microstrip 116, the resonator 118, and the electrode 120 can be formed once in the process of manufacturing the substrate 112.

  The waveguide-microstrip line converter 100 can be used for transmission / reception of EM waves.

  The reason why the received EM wave propagates in the waveguide-microstrip line converter 100 is as follows.

  Conventionally, transmission of EM waves using the waveguide-microstrip line converter 100 is considered to occur in the reverse manner of reception of EM waves due to interaction.

  First, the EM wave is received at the opening of the open-ended waveguide 110.

  The EM wave propagates in the waveguide and hits the surface layer of the substrate 112 including the electrode 120.

  Electrode 120 collects the incident portion of the EM wave that was hit and couples it with resonator 118.

  The remaining portion of the electromagnetic wave that hits passes through the substrate 112 toward the back short 114.

  The collected portion passes through resonator 118, where a first resonance occurs at a desired frequency utilizing energy received from the collected electromagnetic waves.

  The resonant frequency is determined by the size and shape of the resonator.

  The resonance frequency can also be changed by changing the thickness of the resonator 118 or by selecting the material to be produced.

  The portion of the impact EM wave that has passed through the substrate 112 but was not initially collected by the electrode 120 reaches the back short 114 and is reflected at the terminal short circuit location.

  The reflected EM wave propagates back toward the collecting unit 120.

  The reflected EM wave passes through the resonator 118 in order to generate a second reflected wave having the same frequency as the first reflected wave.

  The first and second resonant waves are combined and the combined EM wave passes over the microstrip 116.

  From the microstrip 116, the synthetic EM wave is further processed by signal processing circuitry (eg, a microwave integrated circuit).

FIG. 2 shows a detailed view of the exemplary resonator 118, electrode 120 and microstrip 116 disclosed in the first embodiment of the present invention.

  In this embodiment, the microstrip 116 is patterned on a substrate 112 that has a tap feed to the resonator 118.

  The resonator 118 has a height of C1 and a width of D1.

  The electrode 120 can tap feed the resonator 118 and has a maximum width A1 and height B1.

  In normal prior art, the electrode 120 and the resonator 118 are considered to be electromagnetically coupled by a method other than tap feeding.

  For example, as shown in other embodiments below, these elements can be inductively coupled.

  The resonance frequency of the resonator 118 is determined to some extent by the values of C1 and D1.

  The values of A1 and B1 also determine to some extent how much energy is coupled to the resonator 118 and how efficiently energy is coupled to the resonator 118.

  For example, in order to achieve the simulation result of the frequency characteristic as shown in the graph of FIG. A1 = 4 mm and B1 = 2.08 mm may be set.

  The electrode 120 functions like a real antenna and converts EM wave energy into current.

  The shape of the electrode 120 may be a triangle, a circle, an ellipse, or the like.

  The dimensions and shape of the electrode 120 determine the efficiency of converting EM wave energy into current.

  In order not to couple with the waveguide, the resonator 118 is arranged in the open-ended waveguide 110 so as to face the opening direction of the waveguide.

  That is, a substantial portion of the energy of the EM wave propagating through the waveguide 110 is directly coupled to the resonator 118, but is collected by the electrode 120 and further passes over the resonator 118.

  FIG. 3 shows a typical simulation result for estimating the frequency characteristic of the first embodiment of the present invention.

  The simulation results presented herein are provided by 3D EM simulation, which is a known technique. These embodiments are PC programs called “HFF” provided by Ansoft.

  The graph shown in FIG. 3 shows the magnitude of the impedance associated with the parameters of the scattering matrices S11 and S21 as a function of frequency.

  S11 may be considered as the magnitude of the reflected EM wave, and S21 may be considered as the magnitude of the EM wave passing through the waveguide-microstrip line converter 100.

  In the illustrated graph, the frequency response shows a microwave range of 8.5 to 10.5 GHz, but other frequency bands can be shown as needed.

  S11 and S21 represent values measured between the end of the open-ended waveguide 110 and the end of the microstrip 116.

  As can be seen from FIG. 3, the curve simulating the magnitude of S11 shows a considerable “dip” around 9 GHz, which means that EM energy with the desired frequency tends not to be reflected.

  In this example, it can be seen that the reflection drops to -35 dB in the vicinity of 9 GHz.

  In the curve simulating the magnitude of S21, the frequency passes in the vicinity of 9 GHz, and energy having an undesirable frequency is attenuated in the vicinity of 10 GHz.

  FIG. 4 shows an equivalent circuit model related to the first embodiment of the present invention.

  This equivalent circuit is used to predict the frequency response and draw the curves of S11 and S21 shown in FIG.

  Port 1 represents an open-ended waveguide 110 that is an input / output terminal, and is electromagnetically coupled to the resonator 118 via the electrode 120.

  The coupling between the open-ended waveguide 110 and the electrode 120 is modeled by the first coil pair 410.

  Each coil of the first coil pair 410 has an inductance value of L = 1e-9 Henry and a resistance value of 0Ω.

  The first coil pair 410 is modeled so that it is physically coupled to an equivalent resonator 412.

  An equivalent resonator 412 is connected in series with the second coil pair 414 and models tap feed coupling between the resonator 118 and the microstrip 116.

  Each coil of the second coil pair has an inductor having an inductance of 1e-9 Henry and a resistance value of 0Ω.

  Finally, port 2 of equivalent circuit 400 becomes microstrip 116.

  FIG. 5 shows a waveguide-microstrip line converter 500 according to a second embodiment of the present invention.

  The waveguide-microstrip line converter 500 includes a back short 514, a resonator 518, and an electrode 520.

  Elements common to the first embodiment are also shown, but are not listed here for brevity.

  In this embodiment, the back short 514 has a length of λ / 8 with respect to the dimension in the propagation direction of the EM wave, and is approximately half the size of the first embodiment.

  By changing the size of the resonator pad 518, it is possible to further reduce the back short circuit.

  The electrode 520 has another size to effectively adjust the transmission of EM wave power received by the waveguide 510 to the resonator 518.

  The resonator 518 has a smaller height and width than the resonator 118 shown in the first embodiment.

  FIG. 6 shows a typical simulation result for estimating the frequency characteristic of the second embodiment of the present invention shown in FIG.

  This graph shows the magnitude of the impedance associated with the parameters of the scattering matrices S11 and S21 within the frequency range of 8.5 GHz to 10.5 GHz.

  S11 may be considered as the magnitude of the reflected EM wave, and S21 may be considered as the magnitude of the EM wave passing through the waveguide-microstrip line converter 100.

  As described above, S11 and S21 represent values measured between the end of the open-ended waveguide 110 and the end of the microstrip 116.

  As can be seen from FIG. 6, the curve simulating the magnitude of S11 shows a considerable “sag” around 9 GHz, which means that EM energy with the desired frequency tends not to be reflected.

  In this example, it can be seen that the reflection drops to −15 dB in the vicinity of 9 GHz.

  This attenuation level is small compared to the example shown in FIG. 3, but is sufficient for applications where the waveguide-microstrip line converter 500 is used.

  In the curve simulating the magnitude of S21, the frequency passes in the vicinity of 9 GHz, and energy having an undesirable frequency is attenuated in the vicinity of 10 GHz.

  FIG. 7 shows a waveguide-microstrip line converter 700 according to a third embodiment of the present invention.

  The waveguide-microstrip line converter 700 includes a back short 714, a microstrip 716, and a resonator 718.

  Elements common to the first embodiment are also shown, but are not listed here for brevity.

  In the waveguide-microstrip line conversion device 700, the structure of the microstrip 716 and the resonator 718 is changed, so that the electrode on the substrate 112 becomes unnecessary.

  In conventional embodiments, tap feed is used to couple the resonator and the microstrip.

  Since the waveguide-microstrip line converter 700 is characterized by electromagnetic coupling between the microstrip 716 and the resonator 718, there is no direct physical coupling between the two.

  FIG. 8 shows a detailed view of an exemplary resonator 718 and microstrip 716 disclosed in the third embodiment of the present invention.

  The resonator 718 includes a probe 718a that is directly integrated with the resonator.

  The microstrip 716 has an electromagnetic coupling element 716a that directly integrates with the microstrip line, which is disposed in the vicinity of the resonator 718.

  The electromagnetic field coupling element 716a is disposed in the vicinity of the resonator 718 so that the electromagnetic field coupling with the resonator 718 is maximized.

  Probe 718a and electromagnetic coupling element 716a are configured to act as electrodes that collect energy from EM waves.

  FIG. 9 shows a waveguide-microstrip line converter 900 according to a fourth embodiment of the present invention.

  The waveguide-microstrip line converter 900 includes a back short 914, a microstrip 916, a first resonator 918a, a second resonator 918b, and a collection device 920.

  Elements common to the first embodiment are also shown, but are not listed here for brevity.

  Waveguide-microstrip line converter 900 further includes a pair of resonators that are not directly coupled, but instead are electromagnetically coupled.

  The electrode 920 is coupled to the first resonator 918a by tap feeding.

  The first resonator 918a is electromagnetically coupled to the second resonator 918b.

  The second resonator 918b is coupled to the microstrip 916 by tap feeding.

  In this embodiment, the two resonators behave as two resonator filters.

  In the waveguide-microstrip line converter 900, the resonators 918a and 918b are etched on the same side of the substrate 112.

  Alternatively, each resonator is also coupled to the front and back of the single layer substrate 112.

  The size of the electrode is varied to maximize the energy coupled to the first resonator 918a.

  FIG. 10 shows a waveguide-microstrip line conversion apparatus 1000 according to a fourth embodiment of the present invention.

  The waveguide-microstrip line converter 1000 includes a multilayer substrate 1012, a back short 1014, a microstrip 1016, a first resonator 1018a, a second resonator 1018b, and a collection device 1020.

  Elements common to the first embodiment are also shown, but are not listed here for brevity.

  Waveguide-microstrip line converter 1000 further includes a pair of resonators that are not directly coupled, but instead are electromagnetically coupled.

  The electrode 1020 is coupled to the first resonator 1018a by tap feeding.

  The first resonator 1018a is electromagnetically coupled to the second resonator 1018b.

  The second resonator 1018b is coupled to the microstrip 1016 by tap feeding.

  In this embodiment, the two resonators 1018a and 1018b behave as two resonator filters.

  In the waveguide-microstrip line converter 1000, the resonators 1018a and 1018b can be arranged in different layers of the multilayer substrate 1012.

  The first resonator 1018 a and the electrode 1020 are etched on the side closest to the opening of the open-ended waveguide 110 when viewed from the multilayer substrate 1012.

  The second resonator 1018 b and the microstrip 1016 are etched on the side closest to the back short 1014 when viewed from the multilayer substrate 1012.

  FIG. 11 shows a waveguide-microstrip line converter 1100 according to a sixth embodiment of the present invention, which is composed of a resonator 1118 and an offset electrode 1120.

  In this embodiment, the offset electrode 1120 is directly coupled to the resonator 1118 at a position shifted to the left or right from the center line of the resonator 1118.

  Specifically, the arrangement position of the offset electrode 1120 is slightly shifted from the center line in the lateral dimension of the resonator 1118.

  The resonator 1118 has, for example, a width D11 of 8 mm and a height C11 of 4 mm.

  The offset electrode 1120 has a maximum width of 4 mm and a height of 2.08 mm.

  The offset location E11 of the offset electrode 1120 may be 1 mm from the center line of the resonator 1118.

  By adopting this structure, not only the reflection level on the low frequency band side but also the undesirable frequency can be reduced on the high frequency band side.

  This is described in more detail below.

  FIG. 12 shows typical simulation results for estimating the frequency characteristics of the sixth embodiment of the present invention.

  Above the frequency range of 8.5 GHz to 10.5 GHz, this graph shows the magnitude of impedance associated with the parameters of the scattering matrix, S11 and S21.

  S11 may be considered as the magnitude of the reflected EM wave, and S21 may be considered as the magnitude of the EM wave passing through the waveguide-microstrip line converter 100.

  As described above, S11 and S21 represent values measured between the end of the open-ended waveguide 110 and the end of the microstrip 116.

  As can be seen from FIG. 12, the curve simulating the magnitude of S11 shows a considerable “sag” around 9 GHz, which means that EM energy with the desired frequency tends not to be reflected.

  In this example, not only the reflection is lowered to −45 dB in the vicinity of 9 GHz, but also an effect of reflecting an undesired frequency as shown by “bump” of S11 at 10 GHz. In the curve simulating the magnitude of S21, the frequency passes in the vicinity of 9 GHz, and energy having an undesirable frequency is rapidly attenuated in the vicinity of 10 GHz.

  FIG. 13a shows a waveguide-microstrip line converter 1300 according to a seventh embodiment of the present invention.

  The waveguide-microstrip line converter 1300 includes a back short 1314, a resonator 1318, and an offset electrode 1320.

  In this embodiment, the offset electrode 1320 is directly coupled to the resonator 1318 at a location shifted to the left or right from the center line of the resonator 1318.

  As in the previous embodiment, the position of the offset electrode 1320 is slightly shifted from the center line in the lateral dimension of the resonator 1318.

  As shown in FIG. 13b, the resonator 1318 has two cuts on either side of the location where it is connected to the offset electrode 1320.

  The first cut 1318a is on one side of the offset electrode 1320 and the second cut 1318b is on the other side of the offset electrode 1320.

  With this structure, the frequency characteristic of the waveguide-microstrip line converter 1300 can be changed by shifting the position of the cut-off frequency as shown in FIG. 14 to be described later, and further on the lower frequency band side. In addition to lowering the reflection level, it is possible to maintain the effect that unwanted frequencies can be reduced on the higher frequency band side.

  FIG. 14 shows the frequency response of curves S11 and S21, as will be described in detail below.

  FIG. 14 shows typical simulation results for estimating the frequency characteristics of the seventh embodiment of the present invention.

  Here, by changing the resonator 1318, the sizes of the curves S11 and S21 can be changed.

  As described above, S11 and S21 represent values measured between the end of the open-ended waveguide 110 and the end of the microstrip 116.

  As can be seen from FIG. 14, the frequency response curve varies with cuts 1318 a and 1318 b made in the resonator 1318.

  The curve simulating the magnitude of S11 shows a considerable “sag” around 9 GHz to 9.5 GHz, which means that EM energy with the desired frequency tends not to be reflected.

  This embodiment also has an effect of reflecting an undesired frequency, as indicated by “dull” in S11, and this “dull” is shifted to 10.5 GHz.

  The curve simulating the size of S21 also shows the effect of the cuts 1318a and 1318b made in the resonator 1318. The frequency is transmitted in the 9.5 GHz region, and the energy having an unnecessary frequency is 10.5 GHz. In the vicinity, it drastically decreased to about -25 dB.

  Other embodiments of the invention will be apparent to those skilled in the art from consideration of the specification and practice of the invention disclosed herein.

  It is intended that the specification and examples be considered as exemplary for the true scope and spirit of the invention as indicated by the following claims.

1 shows a first embodiment of a waveguide-microstrip line converter of the present invention. 1 represents a typical resonator, electrode and microstrip of a first embodiment of the present invention. The result of the typical simulation which is estimating the frequency characteristic of 1st Example of this invention is shown. The equivalent circuit model of the 1st example of the present invention is shown. 2 shows a waveguide-microstrip line converter according to a second embodiment of the present invention. The result of the typical simulation which is estimating the frequency characteristic of 2nd embodiment of this invention is shown. 3 shows a waveguide-microstrip line converter according to a third embodiment of the present invention. Figure 3 shows a typical resonator and microstrip of a third embodiment. 4 shows a waveguide-microstrip line converter according to a fourth embodiment of the present invention. 5 represents a fifth embodiment of the present invention and a matched waveguide-microstrip line converter. 6 shows a typical resonator and electrode of a sixth embodiment of the present invention. 10 shows the result of a typical simulation estimating frequency characteristics associated with a sixth embodiment of the present invention. a shows a waveguide-microstrip line converter according to a seventh embodiment of the present invention. b shows a resonator with a cut in the seventh embodiment of the present invention. FIG. 10 shows the result of a typical simulation estimating frequency characteristics associated with the seventh embodiment of the present invention. FIG. 1 represents a conventional transducer between a waveguide and a microstrip consistent with the prior art. Fig. 16 shows an equivalent circuit modeling the conversion device shown in Fig. 15;

Claims (10)

An open-ended waveguide that is an input / output terminal;
A substrate coupled to the open-ended waveguide;
A resonator coupled to the substrate;
An electrode installed on the substrate and electromagnetically coupled to the resonator;
A microstrip line that is electromagnetically coupled to the resonator and is substantially perpendicular to the propagation direction of the electromagnetic wave propagating in the open-ended waveguide;
A back short located opposite to the open-ended waveguide with respect to the substrate;
Consists of
The electrode is installed at a location shifted to either of the center line of the resonator ,
2. A waveguide-microstrip line converter according to claim 1, wherein two slits are provided on both sides adjacent to the electrode in a direction perpendicular to the resonator. 2. The waveguide-microstrip line converter according to claim 1, wherein the back short is a terminal short-circuited waveguide having a size smaller than ¼ of the wavelength of the electromagnetic wave in a direction in which the electromagnetic wave propagates. . 2. The waveguide-microstrip line converter according to claim 1, wherein the back short circuit comprises at least one printed circuit board provided with stepped portions. The back short according to claim 1 is a terminal short-circuited waveguide having a size smaller than an arbitrary fraction less than 1 of the wavelength of the electromagnetic wave in a direction in which the electromagnetic wave propagates. Microstrip line converter. The waveguide-microstrip line converter according to claim 1 includes a second resonator coupled to the first resonator, and an electrode is coupled to the second resonator. 6. The waveguide-microstrip line converter according to claim 5 , wherein the two resonators are coupled to the substrate on opposite sides. 7. The waveguide-microstrip line converter according to claim 6 , further comprising a multilayer printed board. The waveguide to microstrip line conversion device according to claim 5 ,
A probe integrated with the resonator;
Further comprising an electromagnetic coupling element integrated with the microstrip line,
By arranging a microstrip line having an electromagnetic coupling element at the tip in the vicinity of a resonator having the probe, it becomes easy to collect input from the waveguide and convert it to a microstrip line. It is characterized by that. Receive electromagnetic waves,
Collecting the incident part of the received electromagnetic wave;
Generating a first electromagnetic wave that resonates at a desired frequency using the incident part of the received electromagnetic wave;
Reflect the received electromagnetic wave to the collector side with a miniaturized back short,
Generating a second electromagnetic wave that resonates at a desired frequency using the incident part of the received electromagnetic wave;
Combining the first and second electromagnetic waves;
A waveguide-microstrip line conversion method comprising:
An electrode for collecting incident electromagnetic waves;
A back short that reflects the electromagnetic wave;
A resonator in which the first and second electromagnetic waves resonate;
A substrate on which the electrode and the resonator are electromagnetically coupled,
The electrode is installed at a location shifted to either of the center line of the resonator ,
2. A waveguide-microstrip line conversion method characterized in that two slits are provided on both sides adjacent to an electrode in a direction perpendicular to the resonator. 10. The waveguide-microstrip line conversion method according to claim 9 , wherein the back short circuit is a terminal short-circuited waveguide having a size smaller than 1/4 of the wavelength of the electromagnetic wave in a direction in which the electromagnetic wave propagates. .