JP5129966B2 - XY axis motor control method and apparatus for XY automatic feed stitching machine - Google Patents

Description

  The present invention relates to an XY-axis motor control method and apparatus for an XY-direction automatic feed stitching machine, and more particularly to vibration suppression control of an XY motor control device used for an XY-direction automatic feed stitching machine.

  In an XY-direction automatic feed sewing machine such as a pattern sewing machine or a pattern sewing machine as illustrated in FIG. 1, the sewing product is held in synchronization with a needle bar N that moves up and down as the spindle motor rotates. Sewing is performed by moving the cloth holder H in the X and Y directions.

  As an example of the XY positioning device, as shown in FIG. 2, it has a pair of left and right Y axis driving units (hereinafter referred to as YL axis and YR axis) for movement in the Y direction, and X installed on the X axis driving unit. The shaft drive unit (X axis) is configured to move in the X direction.

  For driving the X and Y axes, a ball screw, a pinion gear, a linear motor, and the like are used in addition to the rotary motor M + timing belt B illustrated in the figure.

  In general, mechanical mechanism parts such as the cloth holding body H and the XY shaft parts X, YL, and YR tend to be light in weight and low in vibration.

  Since the motor M and the cloth holder H to be controlled are connected via the timing belt B, it can be regarded as a resonance system in which the motor and the load are coupled by a low-rigid elastic body. In a resonance system, vibrations caused by shaft torsion or the like often occur and cause a problem. When vibration occurs, the control gain must be suppressed, and the response of the speed control system cannot be improved, and adverse effects such as variations in the sewing pitch and a decrease in driving speed occur.

  Since an actual resonance system has many vibration modes and natural frequencies, it is modeled as a multi-inertia resonance system as illustrated in FIG. 3, Jm is the inertia of the motor M, Kf1, Kf2,... Are spring constants, Ja1, Ja2,.

  This multi-inertia resonance system is represented by a block diagram as shown in FIG. In FIG. 4, θm is the rotation angle (motor position) of the motor M, θa is the rotation angle (load position) of the load A, T is the torque, s is the Laplace operator, subscript m is the motor, subscript a is the load, subscript dis Is a disturbance, subscript reac is a torsional reaction force.

  For such resonance suppression and disturbance suppression control, methods such as state feedback control, H∞ control, slow disturbance observer control, resonance ratio control (see Non-Patent Document 1) have been proposed.

Japanese Patent No. 3381880 Yuki et al. “Vibration Suppression Control of Two-Inertia Resonance System by Resonance Ratio Control”, D. Vol. 113, No. 10, (pp. 1162–1169)

  However, state feedback control and H∞ control require strict modeling of the control target, complicated control system, and enormous amount of calculation, which requires a high-speed, high-performance CPU, leading to an increase in cost. Therefore, there is a problem in application to a sewing machine.

  On the other hand, slow disturbance observer control and resonance ratio control can be realized at low cost because it consists of a relatively simple control system, and it is easy to respond on-site, such as adjustment and only gain adjustment. Yes, it is very practical for application to sewing machine products.

  However, in the non-resonant control described in Non-Patent Document 1, the system is modeled as a two-inertia resonance system. There is a problem that the effect on high-order vibration is low, such as inducing the next resonance.

  On the other hand, Patent Document 1 describes that a separate phase advance filter is provided in the servo system, but the configuration is complicated, requires a detailed calculation, requires a long calculation time, and is realized by an inexpensive control device. become unable. The design is complicated, and it is difficult to find a parameter with a stable response.

  The present invention has been made to solve the above-mentioned conventional problems, and with a simple configuration, stabilizes all resonance poles including not only the primary resonance mode but also higher-order vibration modes. The task is to plan.

The present invention applies the resonance ratio control to the primary resonance mode and the phase lead compensation to the higher order vibration mode when controlling the XY-axis motor of the XY-direction automatic feed stitching machine. At this time, the phase lead compensation is performed by changing the ratio of the nominal value of the motor inertia used by the disturbance observer in the resonance ratio control and the actual value of the motor inertia so as to stabilize all the resonance poles. Thus, the above-mentioned problems have been solved.

  That is, the motor drive system of the XY positioning device can be regarded as a two-inertia resonance system in which the motor and the load are coupled by a low-rigid elastic shaft. Therefore, the vibration control and disturbance of the two-inertia resonance load are performed using the resonance ratio control. Perform suppression control. Further, the higher-order vibration poles are stabilized by using phase advance compensation to stabilize all the resonance poles.

  Further, the phase lead compensation is performed by changing the ratio of the nominal value of the motor inertia used by the disturbance observer in the resonance ratio control and the actual motor inertia value, so that separate phase lead compensation means is unnecessary. It is what.

  Further, the phase lead compensation pole and the zero point are arranged inside the resonance ratio control pole so that both the phase lead compensation and the resonance ratio control are compatible.

The present invention also nominal relative high rigidity torsional reaction force is negligible load line Unisaishite the phase lead compensation using only the disturbance observer, the phase lead compensation, the motor inertia to be used by the disturbance observer what Do line by varying the ratio of the value of the actual motor inertia value is obtained by the so stabilized all resonant pole.

The present invention also comprises a resonance ratio control means applied to the primary resonance mode, a phase lead compensation means applied to the secondary or higher order vibration mode, and the resonance ratio The present invention provides an XY-axis motor control device for an XY-direction automatic feed stitching machine characterized in that the control means comprises a disturbance observer and an axial torsional reaction force estimation observer .

  In the present invention, in addition to the resonance ratio control, phase lead compensation is performed. Therefore, for the primary resonance mode, the resonance ratio control effective for suppressing vibration of the two-inertia resonance system is applied, and higher order is applied. For the vibration mode, all the resonance poles can be stabilized by stabilizing the resonance poles using phase advance compensation.

That is, in the sewing machine that moves the cloth by XY, a resin or metal cloth presser type in which only a sewing portion is deleted is used in order to press the cloth flutter. This presser foot can hold the cloth part as close to the needle drop point as possible, so that stable sewing can be performed. Therefore, according to the present invention, if the XY operation is stable against changes in the sewing product and the sewing speed, the needle drop point can be pressed, and more stable sewing is possible.

  Here, in the phase lead compensation control, for example, the nominal value Jmn of the motor inertia used in the disturbance observer in the resonance ratio control is set to be larger than the actual motor inertia value Jm (Jmn> Jm). Phase lead compensation control can be realized without adding phase lead compensation means.

  In addition, when the control is based on a disturbance observer, it is possible to ensure robustness while having a vibration suppressing effect. That is, it is possible to perform control while suppressing the influence on friction, disturbance, and the like, and the synchronism between the main shaft and the XY axis and the synchronism between the left and right axes are improved, so that the quality of sewing can be improved.

  Furthermore, since the control system is simple and the amount of calculation is small compared to state feedback control and H∞ control, it is not necessary to use an expensive CPU or the like. Design and adjustment are also easy.

  Further, for a highly rigid load in which the axial torsional reaction force can be ignored, phase lead compensation can be performed using only a disturbance observer.

  Hereinafter, embodiments of the present invention will be described in detail with reference to the drawings.

  FIG. 5 shows an overall block diagram of the control device according to the first embodiment of the present invention. Although only one axis is shown in the figure, it is common to all axes. Although the load is shown as a two-inertia resonance system, the same applies to a multi-inertia resonance system.

  In this control apparatus, resonance ratio control is performed using the disturbance observer 10 as shown in FIG. 6 and the axial torsional reaction force estimation observer 20 as shown in FIG. 8 to perform vibration suppression control of the multi-inertia resonance system.

  By applying the disturbance observer 10 on the motor side, the influence of various disturbances acting on the motor can be offset and eliminated, and a robust acceleration control system shown in FIG. 7 can be constructed. By ensuring robustness, it is possible to perform control while suppressing the influence on friction, disturbance, and the like, and it is possible to improve the synchronism of the YL axis and the YR axis.

  The disturbance torque Tdism acting on the motor can be expressed as follows.

Tdism = (Jm−Jmn) (d ² θm / dt ² ) + (Ktn−Kt) Ia ^ref
+ Tfric + Dm (dθm / dt) + Treac (1)

Here, Ia ^ref represents the current reference value, the first term on the right side of the equation is the inertia variation torque, the second term is the torque ripple, the third term is the Coulomb friction torque, the fourth term is the viscous friction torque, and the fifth term. Represents the axial torsional reaction force.

The disturbance torque Tdisa acting on the load acts on the motor by being included in the shaft torsional reaction force Treac. When the current reference value Ia ^ref and the motor speed can be detected, the disturbance torque Tdism defined by the equation (1) is passed through the first-order low-pass filter by the disturbance observer 10 shown in FIG. Presumed. In FIG. 6, Icmp is a compensation current for compensating for disturbance torque to ensure robustness.

By feeding back the estimated disturbance torque Tdism ^* , it is possible to construct a control system that is robust against the disturbance.

  The robust control system based on the disturbance observer 10 is an acceleration control system as shown in FIG. It can be seen that the influence of the disturbance torque Tdism is eliminated by setting the disturbance observer gain Gdis large. As a result, the motor removes the torsional reaction force Treac and becomes a robust control system that is not affected by the load side.

  By applying the disturbance observer 10 to the motor side, the shaft torsion reaction force Treac, which is the only information on the load side, is canceled out and removed, so that vibration on the load side is induced.

  Therefore, the axial torsional reaction force Treac is estimated using the axial torsional reaction force estimation observer 20 having substantially the same structure as the disturbance observer 10.

In the disturbance torque Tdis of the equation (1), the influence of the motor inertia fluctuation torque can be eliminated by setting the nominal value Jmn of the motor inertia to the value identified by the acceleration test. Further, by identifying and subtracting the Coulomb friction torque Tfric and the viscous friction torque Dm (d ² θm / dt ² ) by a constant velocity test, the shaft torsional reaction force Treac is estimated as follows.

Treac ^* = Tdism ^* −Tfric−Dm (dθm / dt) (3)

  A block diagram of the axial torsional reaction force estimation observer 20 is shown in FIG. Greac is a cutoff frequency of the first-order low-pass filter included in the axial torsional reaction force estimation observer 20.

  FIG. 9 shows a system in which the axial torsional reaction force Treac is fed back to the controlled object that constitutes the acceleration control system by applying the disturbance observer 10 to the motor side. Kr is a feedback gain of the torsional reaction force Treac, and can be set arbitrarily.

Acceleration reference value (d ² θm / dt ² ) in this system The transfer function from ^ref to motor position θm and the transfer function from motor position θm to load position θa are as follows.

  Further, the motor resonance frequency ωm and the load resonance frequency ωa are defined as follows.

  Here, the resonance ratio K is defined by the following equation.

  The load resonance frequency ωa is an inverse resonance frequency that acts as a zero point on the motor side. ωa does not include an arbitrary parameter and is determined by the controlled object. In addition, it is impossible to control the state feedback on the motor side.

  On the other hand, ωm is a resonance frequency on the motor side and can be arbitrarily set by the shaft torsional reaction force feedback gain Kr.

  By using the equations (6) and (7), FIG. 9 is equivalently converted to the block diagram of FIG. From the figure, it can be seen that the load-side resonance pole ωa cancels out with the motor-side reverse resonance zero point unless there is no zero-point operation due to motor-side feedforward and there is no pole-zero cancellation on the motor side.

  The resonance ratio control feeds back the shaft torsion reaction force Treac, and the resonance ratio K can be arbitrarily set by the shaft torsion reaction force feedback gain Kr.

Controlling the resonance ratio K is equivalent to controlling the virtual motor inertia. When the resonance ratio K is large, that is, when the feedback gain Kr is large, the motor inertia becomes smaller than the load inertia, and the load side It becomes easy to be affected. The reverse is also true.

Resonance ratio K is K = √5 (10)
By setting to, it is possible to set a gain excellent in vibration suppression and quick response to any two-inertia resonance system.

  Each gain is as follows.

Kr = 4 / Ja (11)
Kp = ωa ² (12)
Kv = 4ωa (13)

  Here, if the disturbance applied to the motor M is composed only of the disturbance torque Tdism due to parameter variation, it is expressed as the following equation.

When the transfer function from the motor acceleration reference value (d ² θm / dt ² ) ^ref to the acceleration response value d ² θm / dt ² is determined in consideration of parameter variations, the following equation is obtained.

  Here, assuming that the fluctuation of the torque constant is sufficiently small, the nominal values Jmn and Ktn used in the disturbance observer 10 are set as follows.

Jmn = αJm (16)
Ktn = Kt (17)

  Conventionally, control is performed so that Jm = Jmn, that is, α = 1.

  Substituting equations (16) and (17) into equation (15) yields the following equation.

  When this equation (18) is represented by a block diagram, it is as shown in FIG.

From FIG. 11, a phase compensation 30 of (s + Gdis) / {(1 / α) s + Gdis} is added to the acceleration reference value (d ² θm / dt ² ) ^ref , and the high-pass filter is applied to the disturbance Tdism. It can be said that this is equivalent to multiplying the cutoff frequency by α.

here,
When α <1 Phase lag compensation, disturbance observer gain reduction When α> 1, Phase lead compensation, disturbance observer gain increase

  That is, by changing the ratio α between the nominal value Jmn of the motor inertia used in the disturbance observer 10 and the actual motor inertia value Jm, there is an effect of changing the phase compensation of the acceleration reference value and the cutoff frequency of the disturbance observer.

  Subsequently, the vibration suppression effect when the nominal value Jmn of the motor inertia used in the disturbance observer 10 in the multi-inertia resonance system is changed is shown using the root locus.

  FIG. 12 shows the poles (x marks) and zeros (◯ marks) of the multi-inertia resonance system on the complex plane. Re is a real axis and Im is an imaginary axis. It can be seen that the poles and zeros of the multi-inertia resonance system are alternately arranged on the imaginary axis Im.

  In the following description, for the sake of simplicity, an analysis is performed for the case where phase compensation is performed using a two-inertia resonance system as a load. FIG. 13 shows a block diagram when phase compensation is performed for the two-inertia resonance system. Here, θcmd is a position command value (can be arbitrarily set), and Cp is a proportional control gain.

  The transfer function of FIG. 13 is as follows.

  The characteristic changes depending on the value of the phase compensator 30. That is, the phase compensator 30 performs phase delay compensation when 0 <α <1. If the poles and zeros at this time are Plag and Zlag, they are expressed as follows.

Plag = [0, 0, jωm, −jωm, −αGdis] (23)
Zlag = [jωa, −jωa, Gdis] (24)

  This is illustrated in FIG. X is a pole and ○ is a zero point.

  Here, the angle formed by the pole -αGdis of the phase delay compensator 30 and the vibration pole s = jωm is θp, and the angle formed by the antiresonance zero s = jωa is Φp. Further, the angle formed by the zero point -Gdis of the phase delay compensator 30 and the vibration pole s = iωm is θz, and the angle formed by the antiresonance zero s = jωa is Φz.

At this time, the starting angle θi ^d (i = 1 to 5) of each pole and the arrival angle θi ^a (i = 1 to 3) of the zero point are calculated as follows.

θ1 ^d = −π
θ2 ^d = −π
θ3 ^d = θz−θp + (π / 2)
θ4 ^d = − {θz−θp + (π / 2)}
θ1 ^a = −Φz + Φp− (π / 2)
θ2 ^a = − {− Φz + Φp− (π / 2)}

  FIG. 15 shows a root locus when phase lag compensation is performed on a three-inertia resonance system. When the proportional control gain Cp is changed, it can be confirmed that the system always moves in an unstable direction.

  On the other hand, the phase compensator 30 performs phase lead compensation when α> 1. If the poles and zeros at this time are Plead and Zlead, they are expressed as follows.

Plead = [0, 0, jωm, −jωm, −Gdis] (25)
Zlead = [jωa, −jωa, Gdis] (26)

  This is illustrated in FIG.

  Here, the angle formed by the pole -αGdis of the phase lead compensator 30 and the vibration pole s = jωm is θp, and the angle formed by the antiresonance zero s = iωa is Φp. Further, the angle formed by the zero point -Gdis of the phase advance compensator 30 and the resonance pole s = iωm is θz, and the angle formed by the antiresonance zero s = iωa is Φz.

At this time, the starting angle θi ^d (i = 1 to 5) of each pole and the arrival angle θi ^a (i = 1 to 3) of the zero point are calculated as follows.

θ1 ^d = −π
θ2 ^d = −π
θ3 ^d = θz−θp + (π / 2)
θ4 ^d = − {θz−θp + (π / 2)}
θ1 ^a = −Φz + Φp− (π / 2)
θ2 ^a = − {− Φz + Φp− (π / 2)}

  FIG. 17 shows a root locus when phase lead compensation according to the present invention is performed on a three-inertia resonance system. When the proportional control gain Cp is changed, it can be confirmed that the system always moves in a stable direction.

  Similar results can be obtained with respect to higher-order resonance systems. That is, it can be seen that the vibration suppression control of the multi-inertia resonance system can be performed by performing the phase lead compensation.

  In the present embodiment, the phase lead compensation is performed by changing the ratio α between the motor inertia nominal value Jmn and the actual motor inertia value Jm used in the disturbance observer 10 in the resonance ratio control. This is realized without adding the compensator 30.

  In order to achieve both the phase lead compensation and the resonance ratio control, it is necessary to arrange the phase lead compensation pole and the zero point inside the resonance ratio control pole. That is, by setting the pole arrangement of the entire control system as shown in FIG. 18, the primary vibration mode is positively suppressed by the resonance ratio control, and the higher vibration modes are the original ones. Since the influence is small, stability can be ensured by phase advance compensation.

  In the first embodiment, the control system has a low rigidity in which the motor and the load are coupled by the flexible drive shaft and the shaft torsion becomes a problem. However, the load and the shaft have a high rigidity and the shaft torsion compensation. 19 is not necessary, the phase torsion compensation control can be configured only by the disturbance observer 10 by omitting the axial torsional reaction force estimation observer as in the second embodiment shown in FIG.

  Also in the second embodiment, due to the effect of phase lead compensation, it is possible to stabilize all the resonance poles as in the first embodiment.

  In the above-described embodiment, P (proportional) control is used for the speed calculation unit. However, the type of speed calculation control is not limited to this, and PI (proportional integral) control, PD (proportional derivative) control, PID (proportional integral derivative) control or the like may be used. Further, instead of using the torsional reaction force estimation observer, a method of measuring the load side position using a linear encoder or the like is also possible.

  In the above description, the rotary motor + timing belt is taken as an example, but the present invention can also be applied to a ball screw, a pinion gear, a linear motor, and the like.

  In the above description, the pair of left and right Y-axis drive units of the YL axis and the YR axis is taken as an example for the movement in the Y direction, but the present invention can also be applied to driving with only one axis.

The block diagram which shows an example of the application object of this invention (A) Overall plan view and (B) Uniaxial perspective view showing the configuration of the XY positioning device. Same model diagram Same block diagram Overall block diagram of the first embodiment of the present invention Block diagram showing the configuration of the disturbance observer used in the first embodiment Block diagram of an acceleration control system composed of the disturbance observer Block diagram showing the configuration of the torsional reaction force estimation observer used in the first embodiment Block diagram showing shaft torsion reaction force feedback Equivalent block diagram of FIG. The block diagram which shows the phase compensation by the parameter fluctuation | variation of the disturbance observer used in 1st Embodiment Figure showing the poles and zeros of a multi-inertia resonance system Similarly, block diagram when phase compensation is performed for a two-inertia resonance system The figure which shows the arrangement | positioning of the pole and zero point at the time of phase delay compensation in the comparative example of 0 <α <1 The figure which shows a root locus at the time of performing phase delay compensation similarly to a three inertia resonance system The figure which shows the arrangement | positioning of the pole and zero point at the time of phase lead compensation in this invention which was set to (alpha)> 1 The figure which shows a root locus at the time of performing phase lead compensation by the present invention similarly to a three inertia resonance system The figure which shows the pole arrangement | positioning in 1st Embodiment. Whole block diagram of 2nd Embodiment of this invention

Explanation of symbols

M ... Motor A ... Load 10 ... Disturbance observer 20 ... Shaft torsion reaction force feedback 30 ... Phase compensator

Claims (4)

When applying the resonance ratio control to the primary resonance mode and applying the phase lead compensation to the higher order vibration mode ,
An XY-axis motor for an XY-direction automatic feed stitching machine characterized in that the phase advance compensation is performed by changing a ratio of a nominal value of motor inertia used in a disturbance observer in resonance ratio control to an actual motor inertia value. Control method. 2. The XY-axis motor control method for an XY-direction automatic feed stitching machine according to claim 1, wherein the phase lead compensation pole and the zero point are arranged inside the resonance ratio control pole. When performing phase advance compensation using only a disturbance observer for a rigid load with negligible axial torsional reaction force ,
An XY-axis motor control method for an XY-direction automatic feed stitching machine, wherein the phase advance compensation is performed by changing a ratio of a nominal value of motor inertia used in the disturbance observer to an actual value of motor inertia . Resonance ratio control means applied to the primary resonance mode;
Phase lead compensation means applied to higher order vibration modes of the second order or higher ,
An XY-axis motor control device for an XY-direction automatic feed stitching machine, wherein the resonance ratio control means comprises a disturbance observer and an axial torsional reaction force estimation observer .

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