JP6971272B2 - Phased array antennas, antenna devices, transmitters, wireless power transfer systems and wireless communication systems - Google Patents

Description

The present invention relates to a phased array antenna in which a plurality of antenna elements are arranged, and an antenna device, a transmission device, a wireless power transmission system, and a wireless communication system having the phased array antenna.

Conventionally, an antenna having a plurality of two-dimensionally arranged antenna elements and capable of controlling the directivity pattern (beamforming) of the entire antenna by controlling the phase and amplitude of the signal of each antenna element is known. There is.

Patent Document 1 discloses a phased array antenna in which a plurality of phase shifters are provided so as to correspond to each of the plurality of antenna elements, and each phase shifter is controlled by a control device. In this phased array antenna, the control device calculates the phase shift value of each phase shifter and transmits it to each phase shifter. Further, the signal generated by one signal source is distributed to a plurality of signals by a distribution circuit, and the plurality of signals output from the distribution circuit are each phase-shifted by a phase shifter, amplified by an amplifier, and supplied to an antenna element. Will be done.

Japanese Patent No. 6456579

In the above-mentioned conventional phased array antenna, a plurality of phase shifters are provided so as to correspond to each of the plurality of antenna elements, and each phase shifter is controlled by a control device. Therefore, a control system is required for each phase shifter. There is a problem that the control system becomes complicated. In particular, long-distance wireless communication and wireless power transmission that perform two-dimensional beamforming require a large-open phased array antenna, but in order to configure a large-open phased array antenna, the number of antenna elements is increased to make each antenna. Attempting to control the phase shifter of the element causes an increase in the number of control systems.

The phased array antenna according to one aspect of the present invention includes a plurality of linear array units, a plurality of first transmission lines, one or a plurality of first phase shifters, a second transmission line, and one or a plurality of second transmission lines. Equipped with a phase shifter. The plurality of linear array units have a plurality of antenna elements arranged in the first direction, and are arranged in a second direction intersecting the first direction. The plurality of first transmission lines extend along the longitudinal direction of each of the plurality of linear array portions, and have a plurality of first coupling portions that are coupled to a plurality of antenna elements of the linear array portion. The one or more first phase shifters shift the phase by a first phase difference (Δφe) between the first coupling portions adjacent to each other in each of the plurality of first transmission lines. The second transmission line extends along the arrangement direction of the plurality of linear array portions and has a plurality of second coupling portions to be coupled to the ends of the plurality of first transmission lines. The one or more second phase shifters shift the phase by a second phase difference (Δφa) between the second coupling portions adjacent to each other on the second transmission line.

In the phased array antenna, the first phase shifter is a hybrid coupling type analog phase shifter whose phase change amount changes according to an applied voltage, and DC voltages different from each other at both ends of the first transmission line. (Vdc1, Vdc2) may be applied.

In the phased array antenna, the plurality of first coupling portions may each include a coupling device having a gap. Here, the voids of the plurality of first coupling portions in the first transmission line may be narrower as the distance from the second coupling portion of the first transmission line with the second transmission line increases.

In the phased array antenna, a plurality of array units having the plurality of linear array units are provided.
Each of the plurality of array units may include a plurality of third phase shifters that shift the transmission signal or the reception signal by the third phase difference set for each of the array units.
Here, the third phase difference (Δφn) phase-shifted by the plurality of third phase shifters is such that the equiphase planes of the plurality of array units in the overall target directivity direction of the phased array antenna are on the same plane. It may be set to be located.

The traveling wave type antenna device according to another aspect of the present invention includes a plurality of phased array antennas including the plurality of array units, and each of the plurality of phased array antennas is a spatial arrangement of the plurality of phased array antennas. Based on the positional relationship, a high-frequency signal shifted so that the equiphase planes of the plurality of phased array antennas in the overall target directing direction of the antenna device are located on the same plane is supplied.

The transmitting device according to another aspect of the present invention includes the traveling wave type antenna device, a plurality of phase control transmitters for generating transmission signals having a predetermined frequency and phase to be supplied to each of the plurality of phased array antennas, and a plurality of phase control transmitters. A plurality of fourth phases that shift by a fourth phase difference between a synchronization signal path that supplies a synchronization signal of the frequency to the plurality of phase control transmitters and a plurality of synchronization signal supply units that are adjacent to each other in the synchronization signal path. It is equipped with a phase shifter.

The transmitter according to still another aspect of the present invention includes a plurality of phased array antennas, a plurality of phase control transmitters for generating transmission signals having a predetermined frequency and phase to be supplied to each of the plurality of phased array antennas, and the above-mentioned. A plurality of fourth shifts that shift by a fourth phase difference between a synchronous signal path that supplies a synchronous signal of the frequency to a plurality of phase control transmitters and a plurality of synchronous signal supply units that are adjacent to each other in the synchronous signal path. It is equipped with a phased array.

In the wireless power transmission system according to still another aspect of the present invention, at least one of the transmitting antenna and the receiving antenna for wireless power transmission is one of the above-mentioned phased array antennas.
In the wireless communication system according to still another aspect of the present invention, at least one of the transmitting antenna and the receiving antenna of the wireless communication is one of the above-mentioned phased array antennas.

The electromagnetic wave transmitted or received by the phased array antenna may be a microwave or a millimeter wave.

According to the present invention, it is possible to provide a phased array antenna having a simple configuration in which the number of control systems for phase control of an antenna element is reduced.

Explanatory drawing which shows the arrangement example of the antenna element of the phased array antenna which concerns on one Embodiment of this invention. (A) to (c) are explanatory views which show an example of the main direction of the directional beam which can be controlled in the phased array antenna which concerns on this embodiment, respectively. Explanatory drawing which shows an example of the schematic structure of the phased array antenna which concerns on this embodiment. It is explanatory drawing which shows an example of the structure of the beam steering circuit in the elevation direction in the 4th linear array part of the phased array antenna of FIG. It is explanatory drawing which shows an example of the structure of the beam steering circuit in the azimuth direction in the phased array antenna of FIG. An explanatory diagram showing an example of the relationship between the phase difference of the phase shifter and the steering angle in the phased array antenna according to the present embodiment. The block diagram which shows an example of the schematic structure of the transmission apparatus provided with the phased array antenna which concerns on this embodiment. An explanatory diagram showing an example of a schematic configuration of a phased array antenna according to another embodiment of the present invention. An explanatory diagram showing an example of the relationship between the phase difference of the phase shifter in the phased array antenna of FIG. 8, the steering angle, and the equiphase plane. It is explanatory drawing which shows an example of the computer simulation result which calculated the relationship between the phase difference (Δφ2-Δφ1) of the tuning phase shifter in the phased array antenna of FIG. 8 and the profile of the gain of a directional beam. FIG. 8 is a block diagram showing an example of a schematic configuration of a transmitter including the phased array antenna of FIG. An explanatory diagram showing an example of a schematic configuration of a traveling wave type antenna device according to still another embodiment of the present invention. The explanatory view which shows an example of the transmission device which includes the traveling wave type antenna device of FIG.

Hereinafter, embodiments of the present invention will be described with reference to the drawings.
The phased array antenna according to the present embodiment is an antenna device having a plurality of antenna elements arranged two-dimensionally or three-dimensionally. The phased array antenna is capable of beamforming in which the phase shift and signal of the transmitted or received signal are controlled among a plurality of antenna elements and the direction of the directional main beam is directed in an arbitrary direction.

Further, the phased array antenna of the present embodiment is suitable for a large-opening transmission phased array antenna in long-distance wireless communication or wireless power transmission that requires beamforming. Wireless power transmission using microwaves not only requires beamforming, but also requires an antenna opening area according to the transmission distance. For example, when the power transmission target is a vehicle on the ground (transmission distance is 1 m or less), the antenna opening area is 1 m ² or less, but the power transmission target is a drone flying over a relatively low altitude (for example, 100 m or less). In the case of an air vehicle (power transmission distance is 100 m or less), it is assumed that ^{the antenna opening area is several m 2.} Furthermore, air vehicles (power transmission) such as stratospheric-staying unmanned aircraft, stratosphere platforms, and HAPS (high-altitude platform stations, high-altitude pseudo-satellite) that fly in the stratosphere at relatively high altitudes (for example, several hundred meters or more and 20 km or less). When the distance is 20 km or less), the antenna opening area is several tens of m ² . Further, in the case of a space solar power plant or the like (transmission distance is 3600 km or less) located at a higher altitude (for example, several tens of kilometers or more and 3600 km or less), the antenna opening area is assumed to be ^{several km 2.} As described above, since the antenna opening area expands (the number of antenna elements increases) according to the transmission distance in wireless transmission, a simple and inexpensive phased array antenna is required. The phased array antenna of the present embodiment is suitable for a large-opening phased array antenna that can be beamformed, is simple, and is inexpensive in such a long-distance wireless power transmission system.

In this embodiment, a case where the phased array antenna is mainly configured as a transmitting antenna will be described, but the phased array antenna of the present embodiment can also be configured as a receiving antenna. Further, in the present embodiment, the case of a phased array antenna in which the number of antenna elements arranged two-dimensionally is 16 (= 4 × 4) will be mainly described, but the number of antenna elements of the phased array antenna is shown in the figure. It is not limited to the example of.

FIG. 1 is an explanatory diagram showing an arrangement example of antenna elements of a phased array antenna according to an embodiment of the present invention. In FIG. 1, the phased array antenna 10 is a wireless transmission device that transmits electromagnetic waves of a predetermined frequency (for example, microwaves or millimeter waves) to transmit power, and four sets of linear array units 100 (1) to 100 (1) to 100 ( 4) is provided. The four sets of linear array units 100 (1) to 100 (4) have four antenna elements 110 (1,1) to 110 (1,1) to 110 (4) arranged at predetermined intervals dy in the Y direction (first direction) in the drawing, respectively. It has 1,4), 110 (2,1) to 110 (2,4), 110 (3,1) to 110 (3,4), 110 (4,1) to 110 (4,4). The four sets of linear array units 100 (1) to 100 (4) are arranged at predetermined intervals dx in the X direction (second direction) intersecting the Y direction in the drawing. The distance dy in the Y direction and the distance dx in the X direction (second direction) of the antenna element 110 may be the same distance d.

The antenna element 110 is, for example, a dipole antenna, but may be another type of antenna element such as a slot antenna, a horn antenna, or a microstrip antenna. Further, the antenna element 110 may be an antenna capable of transmitting and receiving electromagnetic waves on a single plane of polarization, or may be an antenna capable of transmitting and receiving electromagnetic waves on a plurality of planes of polarization or electromagnetic waves on a circular plane of polarization.

In the illustrated example, the arrangement direction (X direction) of the linear array units 100 (1) to 100 (4) is substantially orthogonal to the arrangement direction (Y direction) of the antenna elements in each linear array unit. However, the crossing angle in the arrangement direction may deviate from 90 degrees. Further, in the illustrated example, the case where the arrangement surface of the antenna element is substantially flat is shown, but the arrangement surface of the antenna element may be a curved surface.

2 (a) to 2 (c) are explanatory views showing an example of the main direction of the directional beam Bm that can be controlled by the phased array antenna 10 according to the present embodiment, respectively. The X-axis and the Y-axis in FIG. 2 are coordinate axes (reference axes) orthogonal to each other defined on the element arrangement surface 10s on which the antenna element 110 of the phased array antenna 10 is arranged, respectively, and are the X directions in FIG. And corresponds to the Y direction. The Z axis in FIG. 2 is an axis perpendicular to the element arrangement surface 10s of the phased array antenna 10. Beam steering that changes the main direction of the directional beam Bm of the phased array antenna 10 around the Z axis is possible.

In FIG. 2A, the azimuth angle ψa and the elevation angle ψe are angles that define the main direction of the directional beam Bm of the electromagnetic wave transmitted and received by the phased array antenna 10. The azimuth angle ψa is the azimuth angle in the main direction of the directional beam Bm, and is a projection in which the main direction of the directional beam Bm is projected onto the element placement surface 10s with reference to the X axis which is the reference axis on the element placement surface 10s. The angle of the direction Bm'. The elevation angle ψe is an elevation angle in the main direction of the directional beam Bm, and is an angle in the main direction of the directional beam Bm with respect to the element arrangement surface 10s.

FIG. 2B shows a beam steering angle θe in the elevation direction with respect to the Z axis in the YZ plane in the main direction of the directional beam Bm that can be controlled by the phased array antenna 10. The beam steering angle θe on the YZ plane can be changed by controlling the phase difference Δφe between the antenna elements arranged in the Y direction of the linear array unit 100.

FIG. 2C shows a beam steering angle θa in the azimuth direction with respect to the Z axis in the ZX plane in the main direction of the directional beam Bm that can be controlled by the phased array antenna 10. The beam steering angle θa on the ZX plane can be changed by controlling the second phase difference Δφa between the antenna elements arranged in the X direction of the linear array unit 100.

FIG. 3 is an explanatory diagram showing an example of a schematic configuration of the phased array antenna 10 according to the present embodiment. The phased array antenna 10 includes a plurality of first transmission lines 120 and a plurality of first phase shifters 121.

The first transmission line 120 extends along the longitudinal direction of each of the plurality of linear array units 100 (see the Y direction in FIG. 1), and a plurality of first couplings coupled to the plurality of antenna elements 110 of the linear array unit 100. It has a portion 122.

The first phase shifter (also referred to as “steering phase shifter in the elevation direction”) 121 places the high frequency signal RF first among the first coupling portions 122 adjacent to each other in each of the plurality of first transmission lines 120. Only the phase difference (Δφe) is transferred. The first phase difference (Δφe) is a phase difference for setting the beam steering angle θe in the elevation direction (see FIG. 2B) corresponding to the elevation angle ψe which is the elevation angle in the main direction of the directional beam Bm. Is.

Further, the phased array antenna 10 includes a second transmission line 130 and a plurality of second phase shifters 131.

The second transmission line 130 extends along the arrangement direction of the plurality of linear array units 100 (see the X direction in FIG. 1), and one end of each of the plurality of first transmission lines 120 (lower side in the figure). It has a plurality of second coupling portions 132 to be coupled to the end portion). A capacitor C1 for blocking a DC component is provided between the second coupling portion 132 and the first transmission line 120.

The second phase shifter (also referred to as “steering phase shifter in the azimuth direction”) 131 transmits a high frequency signal RF between the second coupling portions 132 adjacent to each other in the second transmission line 130 with a second phase difference (Δφa). Only phase shift. The second phase difference (Δφa) is a phase difference for setting the beam steering angle θa in the azimuth direction (see FIG. 2C) corresponding to the azimuth angle ψa, which is the azimuth angle in the main direction of the directional beam Bm. be.

At one end of the second transmission line 130 (the end opposite to the high frequency signal source 20 which is the transmission signal generation part), a second phase difference (Δφa) is provided via an inductor L1 that cuts off an AC component. A DC voltage Vdc1 [V] is applied to control the voltage.

A capacitor C2 for blocking a DC component is provided between the other end of the second transmission line 130 (the end on the high frequency signal source 20 side) and the high frequency signal source 20.

Since the potential of the DC component at the end of the second transmission line 130 on the high frequency signal source 20 side is zero potential, the voltage Vdc1 [V] of the DC component is applied between the ends of the second transmission line 130. It has become. The voltage Vdc1 [V] controls the second phase difference (Δφa) of the second phase shifter 131 configured by the hybrid coupling type analog phase shifter described later.

Further, a first phase difference (Δφe) is provided to one end of the plurality of first transmission lines 120 (the end opposite to the second transmission line 130) via an inductor L0 that cuts off an AC component. A DC voltage Vdc2 [V] for control is applied. The voltage 0 [V] to Vdc2 [V] controls the first phase difference (Δφe) of the first phase shifter 121 configured by the hybrid coupling type analog phase shifter described later.

FIG. 4 is an explanatory diagram showing an example of the configuration of the beam steering circuit 101 in the elevation direction in the fourth linear array unit 100 (4) surrounded by the broken line of the phased array antenna 10 of FIG. Each of the plurality of first coupling portions 122 coupled to the plurality of antenna elements 110 in the first transmission line 120 faces the lower end surface of the antenna element 110 via predetermined voids s, thereby transmitting a high frequency signal RF. It constitutes a coupler that transmits to the antenna element 110 in a non-contact manner.

The gaps s of the coupler in the plurality of first coupling portions 122 are narrowed as the distance from the second coupling portion with the second transmission line 130 to which the high frequency signal is supplied to the first transmission line 120 is increased so that the degree of coupling is increased. You may. As a result, even when the high frequency signal RF transmitted on the first transmission line 120 is attenuated, the strength of the high frequency signal RF transmitted to the plurality of antenna elements 110 does not vary among the antenna elements and becomes uniform with each other. Can be.

Further, in FIG. 4, each of the plurality of first phase shifters 121 is a hybrid coupling type analog phase shifter whose phase change amount changes according to the applied voltage. The first phase shifter 121 is a kind of variable reactance circuit capable of shifting the phase in the range of, for example, 0 ° to 90 °, and is a varicap diode 121d which is a variable capacitance element whose capacitance changes depending on an applied voltage. It has a configuration connected by a transmission line (impedance line) 121c shorter than 1/4 wavelength of the target signal. In the example of FIG. 4, the plurality of first phase shifters 121 each shift the high frequency signal RF by the first phase difference (Δφe) due to the voltage (Vdc2) [V] applied to the first transmission line 120. .. At the time of input to the first transmission line 120, the high-frequency signal RF has already been phase-shifted by three times the second phase difference Δφa by the three second phase shifters 131 of the second transmission line 130. The phases of the electromagnetic waves radiated from the four antenna elements 110 are 3Δφa, 3Δφa + Δφe, 3Δφa + 2Δφe, and 3Δφa + 3Δφe, respectively.

FIG. 5 is an explanatory diagram showing an example of the configuration of the beam steering circuit 102 in the azimuth direction surrounded by the broken line in the phased array antenna 10 of FIG. In FIG. 5, for convenience of illustration, the antenna element 110 closest to the second transmission line 130 is shown among the antenna elements 110 of the plurality of linear array units 100 described above.

Regarding the arrangement direction of the plurality of linear array units 100 (left-right direction in the figure), the gaps s of the coupler in each linear array unit 100 are narrowed as the distance from the high frequency signal source 20 (the right side in the figure). The degree of coupling may be increased. As a result, even when the high frequency signal RF transmitted on the second transmission line 130 is attenuated, the strength of the high frequency signal RF transmitted to the plurality of antenna elements 110 of each linear array unit 100 does not vary among the antenna elements. Can be made uniform with each other.

Further, in FIG. 5, each of the plurality of second phase shifters 131 is a hybrid coupling type analog phase shifter whose phase change amount changes according to the applied voltage, similarly to the above-mentioned first phase shifter 121. .. The second phase shifter 131 is a kind of variable reactance circuit capable of shifting the phase in the range of, for example, 0 ° to 90 °, and is a varicap diode 131d which is a variable capacitance element whose capacitance changes depending on an applied voltage. It has a configuration connected by a transmission line (impedance line) 131c shorter than 1/4 wavelength of the target signal. In the example of FIG. 5, the high frequency signal RF is phase-shifted by the second phase difference (Δφa) by the voltage (Vdc1) [V] applied to the second transmission line 130. The phases of the electromagnetic waves radiated from the antenna element 110 on the front side of the four linear array portions in the figure are 0 °, Δφa, 2Δφa, and 3Δφa, respectively.

FIG. 6 is an explanatory diagram showing an example of the relationship between the phase difference φ (φe, φa) of the phase shifters 121 and 131 and the steering angle θ (θe, θa) in the phased array antenna 10 according to the present embodiment. In FIG. 6, for the sake of simplicity, the phase differences φe and φa that are phase-shifted by the phase shifters 121 and 131 are referred to as the phase difference φ, and the steering angles θe and θa in the elevation direction and the azimuth direction are steered. Notated as an angle θ. Further, DC Vdc is applied to both ends of the transmission lines 120 and 130 including the plurality of phase shifters 121 and 131.

In FIG. 6, when the wavelength of the high-frequency signal RF is λ [m], the distance between the antenna elements 110 is d [m], and the number of antenna elements 110 is n, the steering angle θ in the main direction of the directional beam Bm is θ. Can be calculated by the following equation (1).

FIG. 7 is a block diagram showing an example of a schematic configuration of a transmission device 1 including a phased array antenna 10 according to the present embodiment. In FIG. 7, the transmitting device 1 serves as a phased array antenna 10 having the above-described configuration, a high frequency signal source 20 that generates a high frequency signal RF supplied to the phased array antenna 10, and a control signal supplied to the phased array antenna 10. It includes a DC power supply 30 that generates DC voltages Vdc1 and Vdc2, and a control unit 40.

The control unit 40 has, for example, based on the position information of the transmission target and the position information of the phased array antenna 10 or the transmission device 1 itself, the beam steering angle θe in the elevation direction of the directional beam Bm and the beam steering in the azimuth direction. Determine the target angle of the angle θa. Further, the control unit 40 determines the target values of the DC voltages Vdc1 and Vdc2 as control signals supplied to the phased array antenna 10 based on the target angles of the beam steering angles θe and θa, and outputs the DC voltages Vdc1 and Vdc2. The DC power supply 30 is controlled so as to do so. Further, the control unit 40 may control ON / OFF and the frequency of the high frequency signal RF output from the high frequency signal source 20.

As described above, in the embodiment illustrated in FIGS. 1 to 7, the main direction of the directional beam Bm of the phased array antenna 10 having 16 (4 × 4) antenna elements 110 is set to two phase control systems (DC voltage). Since it can be controlled by Vdc1 and Vdc2), the device configuration can be simplified and the cost can be reduced. Moreover, the variable angle range in the main direction of the directional beam Bm is not limited. On the other hand, in the conventional phased array antenna, 16 phase control systems are required to individually control the phases of the 16 antenna elements, which complicates the device configuration and increases the cost. Further, in the conventional sub-array configuration in which one phase shifter is provided for the array unit having a plurality of antenna elements, the steerable angle is greatly limited.

In this embodiment, the phased array antenna may be composed of a plurality of array units each having the above-mentioned plurality of linear array units.

FIG. 8 is an explanatory diagram showing an example of a schematic configuration of a phased array antenna 11 according to another embodiment of the present invention. In FIG. 8, the same reference numerals are given to the parts common to those in FIG. 3, and the description thereof will be omitted. Further, the example of FIG. 8 is an example in which two sets of array units 10 (1) and 10 (2) are provided in the X direction (horizontal direction) in the drawing, but three or more sets are provided in the X direction (horizontal direction). The array units may be deployed and provided, or two or more sets of array units may be deployed and provided in the Y direction (vertical direction) in the drawing.

In FIG. 8, the phased array antenna 11 includes two sets of array units 10 (1) and 10 (2) having 16 (4 × 4) antenna elements 110. Further, the plurality of array units 10 (1) and 10 (2) have a third phase difference (Δφ1) between the array units 10 (1) and 10 (2) and the high frequency signal source 20 as a transmission signal generator, respectively. , Δφ2) are provided with a plurality of third phase shifters (also referred to as “tuning phase shifters”) 133 (1) and 133 (2) that shift the phase of the high frequency signal RF. The third phase shifter 133 is provided between the second transmission line 130 and the high frequency signal source 20 together with the capacitor C2 for blocking the DC component, for example. The third phase shifters 133 (1) and 133 (2) are high-frequency signals by the third phase difference Δφn (n = 1, 2) for adjusting the equiphase plane in the main direction of the directional beam Bm by the entire antenna. It is a phase shifter for phase shifting RF. The phase shifter 133 (1) can be omitted.

The third phase differences Δφ1 and Δφ2, which are phase-shifted by the third phase shifters 133 (1) and 133 (2), are a plurality of array units with respect to the overall target directivity direction (the main direction of the directional beam Bm) of the phased array antenna 11. The equiphase planes of 10 (1) and 10 (2) are set to be located on the same plane.

FIG. 9 is an explanatory diagram showing an example of the relationship between the phase difference of the phase shifter in the phased array antenna of FIG. 8 and the steering angle and the equiphase plane. In FIG. 9, the same reference numerals are given to the parts common to those in FIG. 3, and the description thereof will be omitted.

The third phase shifters 133 (1) and 133 (2) are hybrid-coupled types in which the amount of phase change changes according to the applied voltage, as in the case of the first phase shifter 121 and the second phase shifter 131, respectively. It may be an analog phase shifter of. In each of the third phase shifters 133 (1) and 133 (2), a high frequency signal RF is input via the capacitor C3, the phase is transferred by the third phase difference Δφ1 and Δφ2, and then the antenna element is passed through the capacitor C4. It is output to the side.

The third phase differences Δφ1 and Δφ2 of the third phase shifters 133 (1) and 133 (2) are controlled by Vdc3 (1) and Vdc3 (2) applied via the inductor L3 that cuts off the AC component, respectively. NS.

In FIG. 9, a plurality of third phase differences Δφ1 and Δφ2 of the third phase shifters 133 (1) and 133 (2) with respect to the overall target directivity direction (main direction of the directional beam Bm) of the phased array antenna 11, respectively. The array units 10 (1) and 10 (2) are set so that their equiphase planes are located on the same plane, for example, as follows. That is, the wavelength of the high-frequency signal RF is λ [m], the distance between the antenna elements 110 of the array units 10 (1) and 10 (2) is d [m], and the array units 10 (1) and 10 (2) are respectively. Assuming that the number of antenna elements 110 of the above is n and the steering angle in the main direction of the directional beam Bm is θ, the third phase differences Δφ1 and Δφ2 of the third phase shifters 133 (1) and 133 (2) are It is set to satisfy the following equation (2). However, FIGS. 8, 9 and equation (2) assume a condition in which an in-phase signal is input to the third phase shifters 133 (1) and 133 (2). When the in-phase signal is not input, the output phases of the third phase shifters 133 (1) and 133 (2) are defined as φ1 and φ2, and Δφ1 and Δφ2 in FIGS. 8, 9 and (2) are φ1 and φ1. It may be replaced with φ2 respectively.

FIG. 10 shows the relationship between the phase difference (Δφ2-Δφ1) of the tuning phase shifters 133 (1) and 133 (2), which are the third phase shifters in the phased array antenna of FIG. 8, and the gain profile of the directional beam. It is explanatory drawing which shows an example of the computer simulation result which calculated. FIG. 10 shows the results of coupled analysis of three-dimensional electromagnetic field analysis and high-frequency circuit analysis on the antenna circuit model of FIG. In this computer simulation, the antenna element shape is a circular patch antenna, and linearly polarized waves are assumed. The analysis frequency was set to 5.8 GHz, and the array antenna spacing was set to 0.6 wavelength. The overall target directivity direction of the phased array antenna 11 (main direction of the directional beam Bm) is a direction inclined by 10 ° in the Z-axis direction from the element arrangement surface of the phased array antenna 11 (beam steering angle θa in the azimuth direction θa = 10 °). ).

The solid line in FIG. 10 shows the phase difference (Δφ2-Δφ1) of the phase shifters 133 (1) and 133 (2) tuned so that the equiphase planes of the array units 10 (1) and 10 (2) are located on the same plane. ) Is set to 160 °. From this result, it can be seen that the directional beam Bm has a single main direction and is located in the direction of the beam steering angle θa = 10 ° in the target azimuth direction. On the other hand, the broken line in FIG. 10 is a simulation result when the phase difference (Δφ2-Δφ1) of the tuning phase shifters 133 (1) and 133 (2) is set to 0 °. From this result, it can be seen that there are two main directions of the directional beam Bm, which are deviated from the direction of the beam steering angle θa = 10 ° in the target azimuth direction.

FIG. 11 is a block diagram showing an example of a schematic configuration of a transmission device 1 including the array units 10 (1) and 10 (2) of the phased array antenna of FIG. In FIG. 11, the transmission device 1 supplies high frequency signals to the plurality of array units 10 (1) and 10 (2) having the above-described configuration and the array units 10 (1) and 10 (2) of the phased array antenna, respectively. A high-frequency signal source 20 that generates RF, and a DC power supply 30 that generates DC voltages Vdc1, Vdc2, Vdc3 (1), and Vdc3 (2) as control signals to be supplied to the array units 10 (1) and 10 (2). , The control unit 40 is provided.

The control unit 40, for example, is based on the position information of the transmission target and the position information of the array units 10 (1), 10 (2) of the phased array antenna or the transmission device 1 itself, and the elevation direction of the directional beam Bm. The target angles of the beam steering angle θe and the beam steering angle θa in the azimuth direction are determined, and the DC voltages Vdc1 and Vdc2 as control signals supplied to the phased array antenna 10 based on the target angles of the beam steering angles θe and θa are determined. The target value of is determined, and the DC power supply 30 is controlled so as to output the DC voltages Vdc1 and Vdc2. Further, the control unit 40 adjusts the equiphase plane in the main direction of the directional beam Bm by the array units 10 (1) and 10 (2) of the phased array antenna based on the target angles of the beam steering angles θe and θa. The target values of the DC voltages Vdc3 (1) and Vdc3 (2) for the purpose are determined, and the DC power supply 30 is controlled so as to output the DC voltages Vdc3 (1) and Vdc3 (2). Further, the control unit 40 may control ON / OFF and the frequency of the high frequency signal RF output from the high frequency signal source 20.

As described above, in the embodiment illustrated in FIGS. 8 to 11, there are four main directions of the directional beam Bm of the multi-array unit integrated phased array antenna 11 having 32 (4 × 8) antenna elements 110. Since it can be controlled by the phase control system (DC voltage Vdc1, Vdc2, Vdc3 (1), Vdc3 (2)), the device configuration can be simplified and the cost can be reduced. Moreover, the variable angle range in the main direction of the directional beam Bm is not limited.

FIG. 12 is an explanatory diagram showing an example of a schematic configuration of the traveling wave type antenna device 2 according to still another embodiment. In particular, the traveling wave type antenna device 2 illustrated in FIG. 12 is suitable for a long-distance wireless power transmission system and a wireless communication system because it can form a simple and inexpensive antenna device capable of beamforming with a large opening. ..

In FIG. 12, the antenna device 2 includes a plurality of (M) phased array antennas 11 (1) to 11 (M) arranged in a predetermined direction (X direction in the illustrated example). The plurality of phased array antennas 11 (1) to 11 (M) are two-dimensionally arranged (N) array units 10 (1,1), 10 (1,2), ...,, respectively. It is provided with 10 (2,1), 10 (2,2), .... The phased array antennas 11 (1) to 11 (M) in FIG. 12 include a total of four array units 10 in 2 rows and 2 columns, and the array units 10 are in the X and Y directions in the drawings. 3 or more may be provided.

FIG. 13 is an explanatory diagram showing an example of a transmission device 1 including the traveling wave type antenna device 2 of FIG. In the transmission device 1 of FIG. 13, a high-power electromagnetic wave can be radiated in the direction of the target. In FIG. 13, the transmitter 1 is a high-frequency signal RF (1) to high power for each of the above-mentioned traveling wave type antenna device 2 and the plurality of phased array antennas 11 (1) to 11 (M) of the antenna device 2. It includes phase control transmitters 24 (1) to 24 (M) for supplying RF (M) and distributors 25 (1) to 25 (M).

The phase control transmitters 24 (1) to 24 (M) are, for example, phase control vacuum tube transmitters using a vacuum tube capable of outputting a high frequency signal of high power, and are output from the reference signal source 21 and transmit the synchronous signal path 22. High-frequency signals RF (1) to RF (M) having a predetermined frequency and phase are output based on the injection synchronization signal S transmitted via. The first phase control transmitter 24 (1) from the left in the figure outputs a high frequency signal RF (1) having a phase θs1 synchronized with the injection synchronization signal S.

Further, the plurality of phase shifters 23 (1) to 23 (1) to 23 (1) to transfer the injection synchronization signal S by a predetermined fourth phase difference (Δθs) between the plurality of synchronization signal supply units 22a adjacent to each other in the synchronization signal path 22. It is equipped with M-1). Each of the plurality of phase shifters 23 (1) to 23 (M-1) is a hybrid coupling type analog phase shifter in which the amount of phase change changes according to the applied voltage. By the phase shifters 23 (1) to 23 (M-1), injection synchronization is performed to the second and subsequent phase control transmitters 24 (2), 24 (3), ..., 24 (M), respectively. The high frequency signals RF (2), RF (3), ..., RF (M) of the phases θs1 + Δθs, θs1 + Δθs × 2, ···, θs1 + Δθs × (M-1) synchronized with the signal S are output.

The distributors 25 (1) to 25 (M) distribute the high frequency signals RF (1) to RF (M) output from the phase control transmitters 24 (1) to 24 (M) into N units, respectively. It is supplied to the phased array antennas 11 (1) to 11 (M). The distributors 25 (1) to 25 (M) are, for example, waveguide type distributors capable of decomposing high-frequency signals having high power.

The control unit 40 determines, for example, the target angles of the beam steering angle θe in the elevation direction of the directional beam Bm and the beam steering angle θa in the azimuth direction based on the position information of the transmission target and the position information of the antenna device 2. do. Further, the control unit 40 has a DC voltage corresponding to the fourth phase difference (Δθs) in which the phase shifters 23 (1) to 23 (M-1) shift based on the target angles of the beam steering angles θe and θa. The DC power supply 30 is controlled so that Vdc4 is applied to the end portion 22b of the synchronization signal path 22. Further, the control unit 40 controls the ON / OFF and frequency of the injection synchronization signal S output from the reference signal source 21, and the high frequency signal RF output from the phase control transmitters 24 (1) to 24 (M). (1) The ON / OFF and frequency of RF (M) may be controlled.

As described above, according to the phased array antenna 10 of the present embodiment, the phase control of the antenna element 110 is performed without limiting the variable angle range in the main direction of the directional beam Bm as compared with the phased array antenna of the conventional sub-array configuration. The number of control systems can be suppressed, and a simple and inexpensive configuration can be achieved.

Further, the phased array antenna 10 of the present embodiment is used for at least one of the transmitting antenna and the receiving antenna for wireless power transmission in the wireless power transmission system, and is used for at least one of the transmitting antenna and the receiving antenna for wireless communication in the wireless communication system. Can be done.

The processing steps described herein and the components of the phased array antenna, transmitter, wireless power transfer system and wireless communication system can be implemented by various means. For example, these processes and components may be implemented in hardware, firmware, software, or a combination thereof.

Regarding hardware implementation, means such as a processing unit used to realize the above steps and components in an entity (for example, various wireless communication devices, Node Bs, terminals, hard disk drive devices, or optical disk drive devices) One or more application-specific ICs (ASICs), digital signal processors (DSPs), digital signal processing devices (DSPDs), programmable logic devices (PLDs), field programmable gate arrays (FPGAs), processors , Controllers, microcontrollers, microprocessors, electronic devices, other electronic units designed to perform the functions described herein, computers, or combinations thereof.

Further, for firmware and / or software implementation, means such as a processing unit used to realize the above components are programs (eg, procedures, functions, modules, instructions) that execute the functions described herein. , Etc.) may be implemented. In general, any computer / processor readable medium that clearly embodies the firmware and / or software code is a means such as a processing unit used to implement the steps and components described herein. May be used to implement. For example, the firmware and / or software code may be stored in memory and executed by a computer or processor, for example, in a control device. The memory may be mounted inside the computer or processor, or it may be mounted outside the processor. The firmware and / or software code may be, for example, a random access memory (RAM), a read-only memory (ROM), a non-volatile random access memory (NVRAM), a programmable read-only memory (PROM), or an electrically erasable PROM (EEPROM). ), FLASH memory, floppy (registered trademark) discs, compact discs (CDs), digital versatile discs (DVDs), magnetic or optical data storage devices, etc. good. The code may be executed by one or more computers or processors, or the computers or processors may be made to perform functional embodiments described herein.

Further, the medium may be a non-temporary recording medium. Further, the code of the program may be read and executed by a computer, a processor, or another device or device machine, and the format thereof is not limited to a specific format. For example, the code of the program may be any of source code, object code, and binary code, or may be a mixture of two or more of these codes.

Also, the description of the embodiments disclosed herein is provided to allow one of ordinary skill in the art to manufacture or use the present disclosure. Various amendments to this disclosure will be readily apparent to those of skill in the art and the general principles defined herein are applicable to other variations without departing from the spirit or scope of this disclosure. Therefore, this disclosure is not limited to the examples and designs described herein, but should be recognized in the broadest range consistent with the principles and novel features disclosed herein.

1: Transmitting device 2: Antenna device 10, 11: Phased array antenna 10 (1), 10 (2): Array unit 10s: Element arrangement surface 11: Phased array antenna 20: High frequency signal source 21: Reference signal source 22: Synchronous Signal path 22a: Synchronous signal supply unit 22b: End 23: Phase shifter 24: Phase control transmitter 25: Distributor 30: DC power supply 40: Control unit 100, 100 (1) to 100 (4): Linear array unit 101, 102: Beam steering circuit 110: Antenna element 120: First transmission line 121: First phase shifter 121d: Barracta diode 122: First coupling portion 130: Second transmission line 131: Second phase shifter 131d: Variactor diode 132: 2nd coupling part 133: 3rd phase shifter (tuning phase shifter)

Claims (7)

It ’s a phased array antenna.
A plurality of linear array units having a plurality of antenna elements arranged at equal intervals in the first direction and arranged at equal intervals in a second direction intersecting with the first direction.
A plurality of first transmission lines extending along the longitudinal direction of each of the plurality of linear array portions and having a plurality of first coupling portions coupled to a plurality of antenna elements of the linear array portion.
One or more first phase shifters inserted between the first coupling portions adjacent to each other in each of the plurality of first transmission lines and phase-shifting by the first phase difference (Δφe).
A second transmission line extending along the arrangement direction of the plurality of linear array portions and having a plurality of second coupling portions coupled to the ends of the plurality of first transmission lines.
It comprises one or more second phase shifters inserted between the second coupling portions adjacent to each other in the second transmission line and phase-shifted by a second phase difference (Δφa).
Each of the plurality of first phase shifters is a hybrid coupling type in which the first phase difference (Δφe) changes according to the applied DC voltage between the input end and the output end in the direction along the first transmission line. It is an analog phase shifter of
A DC voltage (Vdc2) is applied to each of the plurality of ends of the plurality of first transmission lines far from the second coupling portion.
The first coupling portion of the plurality is a coupler having a gap between the antenna elements,
The voids of the plurality of first coupling portions in the first transmission line are narrower as the distance from the second coupling portion of the first transmission line with the second transmission line increases.
Each of the plurality of second phase shifters is a hybrid coupling type in which the second phase difference (Δφa) changes according to the applied DC voltage between the input end and the output end in the direction along the second transmission line. It is an analog phase shifter of
A DC voltage (Vdc1) is applied to one end of the second transmission line, and a high-frequency signal source is connected to the other end via a capacitor for blocking the DC component.
The second coupling portion of said plurality, the the said end portion to which a DC voltage (Vdc2) is applied to the first transmission line is a coupler having a gap between the end portion on the opposite side,
Wherein the plurality of voids of the second coupling portion of the second transmission line is narrower as the distance from the high frequency signal source, phased array antenna, characterized in that. In the phased array antenna of claim 1,
A plurality of array units having the plurality of linear array units are provided.
Each of the plurality of array units is a phased array antenna, comprising a plurality of third phase shifters that shift a transmission signal or a reception signal by a third phase difference set for each of the array units. In the phased array antenna of claim 2,
The third phase difference phase-shifted by the plurality of third phase shifters is set so that the equiphase planes of the plurality of array units in the overall target directivity direction of the phased array antenna are located on the same plane. A phased array antenna that features that. It is a traveling wave type antenna device.
A plurality of phased array antennas including the plurality of array units according to claim 2 or 3 are provided.
Each of the plurality of phased array antennas has the same phase plane of each of the plurality of phased array antennas in the overall target directing direction of the antenna device based on the spatial arrangement positional relationship of the plurality of phased array antennas. An antenna device characterized in that a high-frequency signal phase-shifted so as to be located in is supplied. It ’s a transmitter,
The traveling wave type antenna device of claim 4 and
A plurality of phase control transmitters that generate transmission signals having a predetermined frequency and phase to be supplied to each of the plurality of phased array antennas.
A synchronization signal path that supplies a synchronization signal of the frequency to the plurality of phase control transmitters,
A transmission device comprising a plurality of fourth phase shifters that shift the phase by a fourth phase difference between a plurality of synchronous signal supply units adjacent to each other in the synchronous signal path. It ’s a wireless power transmission system.
A wireless power transmission system, characterized in that at least one of a transmitting antenna and a receiving antenna for wireless power transmission is a phased array antenna according to any one of claims 1 to 5. It ’s a wireless communication system.
A wireless communication system, wherein at least one of a transmitting antenna and a receiving antenna for wireless communication is a phased array antenna according to any one of claims 1 to 5.

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