JP6978186B2 - Two-dimensional, electronically steerable artificial impedance surface antenna - Google Patents

Description

The present disclosure relates to antennas in general, and in particular to electronically steerable antennas. More specifically, the present disclosure relates to an electronically steerable artificial impedance antenna that can be steered in two dimensions.

In various applications, it may be desirable to have the ability to electronically steer the antenna in two directions. As used herein, "steering" an antenna may include directing the main gain lobe, or main lobe, of the radiation pattern of the antenna in a particular direction. Manipulating the antenna electronically means manipulating the antenna using electronic means rather than mechanically. Steering an antenna with respect to two dimensions can be called two-dimensional steering.

In general, 2D steering is typically provided by a phased array antenna. However, commonly available phased array antennas have electronic configurations that are more complex and / or more expensive than desired. As a result, it may be desirable to have some other type of antenna that can be electronically steered in two dimensions and is less costly than a phased array antenna.

Artificial impedance surface antennas (AISAs) can be cheaper than phased array antennas. Artificial impedance surface antennas have an artificial impedance surface that has impedance that is spatially modulated over the artificial impedance surface according to the ability to match the phase plane between the surface wave on the artificial impedance surface and the desired far-field radiation pattern. It can be achieved by emitting surface waves over AIS). The basic principle of operation of an artificial impedance surface antenna is to use the momentum of the grid of this modulated artificial impedance surface to match the wave vector of the wavefront of the surface wave excited by the desired plane wave.

Some low-cost artificial impedance surface antennas may only be able to be electronically steered in one dimension. In some cases, mechanical steering may be used to steer a one-dimensional artificial impedance surface antenna in two dimensions. However, mechanical steering may not be desirable in certain applications.

Artificial impedance surface antennas that can be electronically steered in two dimensions have been described in the prior art. However, this type of antenna is more expensive and electronically complex than desired. For example, electronically manipulating this type of antenna in two dimensions may require a complex network of voltage controls for a two-dimensional array of impedance devices. This network is used to create a pattern of any impedance that can generate beam steering in any direction.

In an exemplary example, the 2D artificial impedance surface antenna may be implemented as a grid of metal patches on a dielectric substrate. Each metal path can be called an impedance element. The surface wave impedance of the artificial impedance surface can be locally controlled at each position on the artificial impedance surface by applying a variable voltage to the voltage variable varicaps connected between each patch of the plurality of patches. A varicap is a diode in a semiconductor device, which has a capacitance that depends on the applied voltage.

The surface wave impedance of the artificial impedance surface can be adjusted by the capacitive load inserted between the patches. Each patch is electrically connected to an adjacent patch on all four sides with a variable voltage varicap capacitor. The voltage is applied to the varicap through the electric vias connected to each patch. The electrical vias may be electrical connections that pass through the plane of one or more adjacent layers in the electronic circuit.

A portion of the patch may be electrically connected to the ground plane using an electrical via that extends from the center of each patch to the dielectric substrate. The rest of the patch can be electrically connected to a voltage source that penetrates the dielectric substrate and into a through hole in the ground plane to this voltage source.

Computer control allows any desired impedance pattern to be applied to the artificial impedance surface within the limits of varicap tunability and within the limits of the surface wave characteristics of the artificial impedance surface. One of the limitations of this method is that the vias provide inductance to the artificial impedance surface that shifts the surface wave bandgap to lower frequencies, so the vias can significantly reduce the operating bandwidth of the artificial impedance surface. That is. As the varicap is adjusted to higher capacitance, the inductance of the artificial impedance surface increases, which can further reduce the frequency of the surface wave bandgap. As a result of the surface wave bandgap, it is not possible for artificial impedance surfaces to be used beyond the bandgap frequency. In addition, the surface wave bandgap limits the range of surface wave impedance to the extent that the artificial impedance surface can be tuned.

Thus, a specific artificial impedance surface antenna that can be electronically steered in two dimensions, as described above, is cheaper and less complex than the commonly available two-dimensional artificial impedance surface antennas. May be desired in the application. Therefore, it is desirable to have methods and devices that take into account at least some of the above problems, as well as other possible problems.

In one exemplary embodiment, the device comprises a plurality of radiating elements and a plurality of surface wave feeds. Each radiating element of the plurality of radiating elements is a plurality of surface wave channels configured such that each surface wave channel of the plurality of surface wave channels restricts the path of the surface wave and includes a plurality of switch elements and a plurality of impedance elements. including. One surface wave feed of multiple surface wave feeds is configured to carry high frequency signals over one surface wave channel of multiple surface wave channels of one radiation element of multiple radiation elements. It is configured to connect to the transmission line.

In another exemplary embodiment, the antenna system comprises a plurality of radiating elements and a plurality of surface wave feeds. Each radiating element of the plurality of radiating elements includes a plurality of surface wave channels configured such that each surface wave channel of the plurality of surface wave channels restricts the path of the surface wave. Each surface wave channel of the plurality of surface wave channels includes a plurality of impedance elements arranged on the surface of the dielectric substrate and a plurality of switch elements arranged on the surface of the dielectric substrate. Each switch element of a plurality of switch elements simply has two states. The plurality of surface wave feeds are configured to connect a plurality of surface wave channels of each radiating element of the plurality of radiating elements to a plurality of transmission lines.

Yet another exemplary embodiment provides a method for electronically manipulating an antenna system. The surface wave is propagated along each surface wave channel of the plurality of surface wave channels formed in each radiation element of the plurality of radiation elements in order to form a radiation pattern. Each surface wave channel of the plurality of surface wave channels formed in each radiation element of the plurality of radiation elements is a high frequency signal using the surface wave feed of one of the plurality of surface wave feeds associated with the plurality of radiation elements. Connected to a transmission line configured to carry. The main lobe of the radiation pattern is electronically steered by controlling the voltage applied to a plurality of switch elements connecting the plurality of impedance elements in each surface wave channel of the plurality of surface wave channels.

Features and functions can be achieved independently in the various embodiments of the present disclosure, or can be combined in yet other embodiments, further details are understood with reference to the following description and drawings. Can be

New features that are considered to be the features of the exemplary embodiment are described in the appended claims. However, when read in conjunction with the accompanying drawings, not only the exemplary embodiments and preferred embodiments thereof, but also their further objectives and features, see the following detailed description of the exemplary embodiments of the present disclosure. Will be best understood by.

It is a figure which shows the antenna system in the form of the block diagram by an exemplary embodiment. It is a figure which shows the antenna system by an exemplary embodiment. It is a side view of a part of a tunable artificial impedance surface antenna by an exemplary embodiment. It is a figure which shows the different configuration of the antenna system by an exemplary embodiment. It is a figure which shows another configuration of the antenna system by an exemplary embodiment. It is a side view of the dielectric substrate by an exemplary embodiment. It is a figure which shows the dielectric substrate which has the material embedded pocket by an exemplary embodiment. It is a figure which shows the antenna system by an exemplary embodiment. It is another figure which shows the antenna system by an exemplary embodiment. It is a figure which shows the antenna system which has a different voltage controller by an exemplary embodiment. It is a figure which shows the still another configuration of the antenna system by an exemplary embodiment. It is a figure which shows the still another configuration of the antenna system by an exemplary embodiment. It is a figure which shows a part of the antenna system by an exemplary embodiment. It is a figure which shows the antenna system which has two high frequency assemblies by an exemplary embodiment. It is a figure which shows another antenna system by an exemplary embodiment. It is a figure which shows the different structure of the artificial impedance surface antenna in the antenna system in the form of the block diagram by an exemplary embodiment. It is a figure which shows the artificial impedance surface antenna by an exemplary embodiment. It is sectional drawing side view of the artificial impedance surface antenna by an exemplary embodiment. It is a figure which shows the impedance pattern of the artificial impedance surface antenna by an exemplary embodiment. It is a figure which shows a part of the artificial impedance surface antenna by an exemplary embodiment. It is sectional drawing side view of the artificial impedance surface antenna by an exemplary embodiment. It is a figure which shows the artificial impedance surface antenna in the form of the block diagram by an exemplary embodiment. It is a figure which shows the radiating element by an exemplary embodiment. It is an enlarged view of a part of the surface wave channel by an exemplary embodiment. It is a figure which shows the radiating element by an exemplary embodiment. It is a figure which shows the process for electronically steering an antenna system in the form of a flow diagram by an exemplary embodiment. It is a figure which shows the process for electronically steering an antenna system in the form of a flow diagram by an exemplary embodiment. It is a figure which shows the process for electronically steering an antenna system in the form of a flow diagram by an exemplary embodiment.

Next, with reference to the drawings, in particular with reference to FIG. 1, an example of an antenna system in the form of a block diagram is shown by exemplary embodiments. The antenna system 100 can include an antenna 102, a voltage controller 104, a phase shifter 106, and a high frequency module 108. In this exemplary example, the antenna 102 is in the form of an artificial impedance surface antenna (AISA) 110.

The antenna 102 is configured to transmit and / or receive the radiation pattern 112. Radiation pattern 112 is a plot of the gain of antenna 102 as a function of direction. The gain of antenna 102 can be considered as a performance parameter for antenna 102. In some cases, the "gain" is considered to be the peak value of the gain.

The antenna 102 is configured to electronically control the radiation pattern 112. If the antenna 102 is used for transmission, the radiation pattern 112 may be the strength of the radio waves transmitted from the antenna 102 as a function of direction. When the antenna 102 is used for transmission, the radiation pattern 112 can be referred to as the transmission pattern. The gain of the antenna 102 can explain to what extent the antenna 102 converts electric power into electromagnetic radiation such as radio waves and transmits the electromagnetic radiation in a specified direction at the time of transmission.

If the antenna 102 is used for reception, the radiation pattern 112 may be the sensitivity of the antenna 102 to radio waves as a function of direction. When the antenna 102 is used for reception, the radiation pattern 112 can be referred to as the reception pattern. The gain of the antenna 102 can explain to what extent the antenna 102 converts electromagnetic radiation such as radio waves and reaches power from a specified direction at the time of reception.

The transmission pattern and the reception pattern of the antenna 102 may be the same. Therefore, the transmission pattern and the reception pattern of the antenna 102 can be simply referred to as a radiation pattern 112.

The radiation pattern 112 can include a main lobe 116 and one or more side lobes. The main lobe 116 can be a lobe in the direction in which the antenna 102 is directed. When the antenna 102 is used for transmission, the main lobe 116 is located in the direction in which the antenna 102 transmits the strongest radio waves in order to form a high frequency beam. When the antenna 102 is used for transmission, the main lobe 116 can also be referred to as the main gain lobe of the radiation pattern 112. When the antenna 102 is used for reception, the main lobe 116 is located in the direction in which the antenna 102 is most sensitive to the received radio waves.

In this exemplary example, the antenna 102 is configured to electronically steer the main lobe 116 of the radiation pattern 112 in the desired direction 114. The main lobe 116 of the radiation pattern 112 can be electronically steered by controlling the phi steer angle 118 and theta steer angle 120 to which the main lobe 116 is directed. The phi steering angle 118 and theta steering angle 120 are spherical coordinates. When the antenna 102 is operating in the XY plane, the phi steering angle 118 is the angle of the main lobe 116 with respect to the X axis in the XY plane. The theta steering angle 120 is the angle of the main lobe 116 with respect to the Z axis orthogonal to the XY plane.

The antenna 102 can operate in the XY plane by having an array 122 of radiating elements placed in the XY plane. As used herein, an "array" of items can include one or more items arranged in rows and / or columns. In this exemplary example, the array 122 of radiating elements may be a single radiating element or a plurality of radiating elements. In an exemplary example, each radiating element in the radiating element array 122 can take the form of a surface wave waveguide structure on an artificial impedance surface.

Radiating element 123 can be taken as an example of one radiating element in an array 122 of radiating elements. The radiating element 123 may be configured to emit radiation that contributes to the radiating pattern 112.

As shown in the figure, the radiating element 123 is mounted using the dielectric substrate 124. The dielectric substrate 124 can be mounted as a layer of dielectric material. The dielectric material is an electrical insulator that can be polarized by an applied electric field.

The radiating element 123 can include one or more surface wave channels formed on the dielectric substrate 124. For example, the radiating element 123 can include a surface wave channel 125. The surface wave channel 125 is configured to limit the path of surface waves propagating along the dielectric substrate 124, and in particular the surface wave channel 125.

In an exemplary example, the array 122 of radiating elements may be positioned and arranged approximately parallel to the X axis and separated along the Y axis. Also, when a plurality of surface wave channels are formed on a dielectric substrate, these surface wave channels may be formed and arranged substantially parallel to the X axis and separated along the axis.

In this exemplary example, impedance and tunable elements located on a dielectric substrate can be used to form each surface wave channel of the radiating element within the radiating element array 122. For example, the surface wave channel 125 may be composed of a plurality of impedance elements 126 and a plurality of tunable elements 128 arranged on the surface of the dielectric substrate 124. A plurality of impedance elements 126, a plurality of tunable elements 128, and a dielectric substrate 124 together form an artificial impedance surface, from which radiation is generated.

One of the plurality of impedance elements 126 can be mounted in a plurality of different ways. In an exemplary example, the impedance element may be mounted as a resonant element. In an exemplary example, the impedance device may be mounted as an element made of a conductive material. The conductive material may be, for example, a metallic material, but is not limited thereto. Depending on the mounting, the impedance element may be mounted as a metal strip, a patch of conductive paint, a metal mesh material, a metal film, a deposit of a metal substrate, or some other type of conductive element. In some cases, the impedance element may be, for example, a split ring resonator (SRR), an electrically connected resonator (ECR), a structure consisting of one or more metamaterials, or some other type of structure. It may be mounted as a resonance structure such as an element or an element.

As used herein, metamaterials can be artificial materials that have been engineered to have properties that may not be found in nature. The metamaterial may be a collection of various individual elements formed from the material of a conventional microscope. These conventional materials can include, but are not limited to, for example, metals, metal alloys, plastic materials, and other types of materials. However, these conventional materials can be arranged in a repeating pattern. The properties of metamaterials are not based on the composition of the metamaterial, but on the rigorously designed structure of the metamaterial. In particular, the exact shape, geometry, size, orientation, placement, or combination thereof is accurate to produce metamaterials with certain properties that may not be found in nature or easily found. Can be designed to.

Each of the plurality of tunable elements 128 can be an element that can be controlled, i.e., adjusted to change the angle of one or more surface waves propagating along the radiating element 123. In this exemplary example, each of the plurality of tunable elements 128 may be an element having a capacitance that can be varied based on the voltage applied to the tunable element.

In an exemplary example, the plurality of impedance elements 126 take the form of a plurality of metal strips 132 and the plurality of tunable elements 128 take the form of a plurality of varicaps 134. Each of the plurality of varicaps 134 may be a diode of the semiconductor device having a capacitance depending on the voltage applied to the diode of the semiconductor device.

In an exemplary example, multiple metal strips 132 can be placed in rows extending along the X axis. For example, the plurality of metal strips 132 may be periodically dispersed on a dielectric substrate 124 along the X axis. The plurality of varicaps 134 can be electrically connected to the plurality of metal strips 132 on the surface of the dielectric substrate 124. Specifically, at least one varicap of the plurality of varicaps 134 can be placed between each metal strip of a pair of adjacent metal strips of the plurality of metal strips 132. Also, the plurality of varicaps 134 can be aligned so that all of the varicap connections on each metal strip have the same polarity.

The dielectric substrate 124, the plurality of impedance elements 126, and the plurality of tunable elements 128 may be configured for the surface wave channel 125, and in particular the design configuration 136 selected for the radiating element 123. Depending on the implementation, each radiating element in the radiating element array 122 may have the same or different selected design configurations.

As shown, the selected design configuration 136 may include multiple design parameters such as impedance element width 138, impedance element spacing 140, tunable device spacing 142, and substrate thickness 144. Not limited. The width 138 of the impedance element can be the width of one of the plurality of impedance elements 126. The width 138 of the impedance element can be selected to be the same or different for each of the plurality of impedance elements 126, depending on the implementation.

The impedance element spacing 140 can be the spacing of the plurality of impedance elements 126 with respect to the X-axis. The spacing 142 of the tunable elements can be the spacing of the plurality of tunable elements 128 with respect to the X-axis. Further, the thickness 144 of the substrate can be the thickness of the dielectric substrate 124 on which a specific waveguide is mounted.

The values of the different parameters of the selected design configuration 136 can be selected, for example, based on, but not limited to, the radiation frequency configured to operate the antenna 102. Other considerations include, for example, the desired impedance modulation for the antenna 102.

Since the plurality of impedance elements 126 can be electrically connected to the plurality of tunable elements 128, the voltage can be applied to the plurality of tunable elements 128 by applying the voltage to the plurality of impedance elements 126. Specifically, the voltage applied to the plurality of impedance elements 126 and the voltage applied to the plurality of tunable elements 128 can change the capacitance of the plurality of tunable elements 128. By changing the capacitance of the plurality of tunable elements 128, the surface impedance of the antenna 102 can be changed in order. Changing the surface impedance of the antenna 102 changes the generated radiation pattern 112.

That is, by controlling the voltage applied to the plurality of impedance elements 126, the capacitance of the plurality of tunable elements 128 can be changed. By changing the capacitance of the plurality of tunable elements 128, the capacitance coupling and the impedance between the plurality of impedance elements 126 can be changed, that is, modulated. The theta steering angle 120 can be changed by changing the capacitance coupling and impedance between the plurality of impedance elements 126, that is, by modulating them.

A voltage controller 104 can be used to apply a voltage to a plurality of impedance elements 126. The voltage controller 104 can include a plurality of voltage sources 146, a plurality of grounds 148, a plurality of voltage lines 150, and / or a plurality of other types of components. In some cases, the voltage controller 104 can be referred to as a voltage control network. As used herein, a "number of" item may include one or more items. For example, multiple voltage sources 146 can contain one or more voltage sources, multiple grounds 148 can contain one or more grounds, and multiple voltage lines 150 can contain one or more voltages. Can include lines.

One of the multiple voltage sources 146 can take the form of, for example, a digital-to-analog converter (DAC), a variable voltage source, or some other type of voltage source, but is limited thereto. It's not something. A plurality of grounds 148 can be used to ground at least a portion of the plurality of impedance elements 126. Multiple voltage lines 150 can be used to transmit voltage from multiple voltage sources 146 and / or multiple grounded 148s to multiple impedance elements 126. In some cases, each of the plurality of voltage lines 150 can be referred to as a via. In an exemplary example, the plurality of voltage lines 150 can take the form of a plurality of metal vias.

In an exemplary example, each of the plurality of impedance elements 126 can receive a voltage from one of the plurality of voltage sources 146. In another exemplary example, some of the plurality of impedance elements 126 may receive voltage from multiple voltage sources 146 through the corresponding portions of the plurality of voltage lines 150, while the plurality of impedance elements 126. Other portions may be electrically connected to a plurality of grounds 148 via corresponding portions of the plurality of voltage lines 150.

In some cases, the controller 151 can be used to control multiple voltage sources 146. The controller 151 can be considered as part of the antenna system 100 or separate from the antenna system 100, depending on the implementation. The controller 151 may be implemented using a microprocessor, an integrated circuit, a computer, a central processing unit, multiple computers communicating with each other, or some other type of computer or processor.

The surface wave 152 propagated along the array 122 of the radiating element may be connected to the plurality of transmission lines 156 by the plurality of surface wave feeds 130 arranged on the dielectric substrate 124. The surface wave feed of one of the plurality of surface wave feeds 130 may be any device capable of converting the surface wave into a high frequency signal and / or the high frequency signal into a surface wave. In an exemplary example, the surface wave feed of one of the plurality of surface wave feeds 130 is located at the end of each waveguide in the array 122 of radiating elements on the dielectric substrate 124.

For example, when the antenna 102 is in receive mode, one or more surface waves propagating along the radiating element 123 are received by the corresponding surface wave feeds of the plurality of surface wave feeds 130 and the corresponding high frequency signals. Can be converted to 154. The high frequency signal 154 may be transmitted to the high frequency module 108 through one or more of the plurality of transmission lines 156. The high frequency module 108 can then serve as a high frequency signal 154 for reception and processing accordingly.

Depending on the implementation, the high frequency module 108 can function as a transmitter, receiver, or a combination of both. In some exemplary examples, the high frequency module 108 can be referred to as the transmit / receive module 158. In some cases, the high frequency module 108 can be referred to as a high frequency source if it is configured for transmission.

In some cases, the high frequency signal 154 may pass through the phase shifter 106 before being transmitted to the high frequency module 108. The phase shifter 106 can include any number of phase shifters, power dividers, transmission lines, and / or other components configured to shift the phase of the high frequency signal 154. In some cases, the phase shifter 106 can be referred to as a phase shift network.

When the antenna 102 is in transmit mode, the high frequency signal 154 may be transmitted from the high frequency module 108 to the antenna 102 through the plurality of transmission lines 156. Specifically, the high frequency signal 154 is received on one of a plurality of surface wave feeds 130 and then propagated along the corresponding waveguide of the array 122 of the radiating element. Can be converted to.

In this exemplary example, the relative phase difference between the plurality of surface wave feeds 130 can be modified to change the phi steering angle 118 of the transmitted or received radiation pattern 112. Therefore, by controlling the relative phase difference between the plurality of surface wave feeds 130 and the voltage applied to the tunable element of each waveguide of the array 122 of the radiating element, the phi steering angle 118 and theta The steering angle 120 can be controlled respectively. That is, the antenna 102 can be electronically steered in two dimensions.

Depending on the implementation, the radiating element 123 may be configured to emit linearly or circularly polarized radiation. When configured to emit linearly polarized radiation, the multiple metal strips used for each surface wave channel on the radiating element 123 may be tilted in the same direction as the X axis and along that X axis. Multiple metal strips are dispersed. Generally, only a single surface wave channel is required for each radiating element 123.

However, if the radiating element 123 is configured to generate circularly polarized radiation, the surface wave channel 125 may be the first surface wave channel and the second surface wave channel 145 may be the radiating element. It may be in 123. The surface wave channel 125 and the second surface wave channel 145 may be out of phase with each other by about 90 degrees. The interaction between the radiation from these two connected surface wave channels can generate circularly polarized radiation.

The plurality of impedance elements 126 forming the surface wave channel 125 may be the first plurality of impedance elements that radiate with polarized waves having an angle with respect to the polarization of the electric field of the surface wave. The second plurality of impedance elements forming the second surface wave channel 145 may radiate polarized waves at an angle offset by about 90 degrees compared to the surface wave channel 125.

For example, each impedance element of the first plurality of impedance elements of the surface wave channel 125 can have a tensor impedance associated with the principal angle, which is tilted at a first angle with respect to the X axis of the radiating element 123. ing. Also, each impedance element of the second plurality of impedance elements of the second surface wave channel 145 can have a tensor impedance, which is tilted at a second angle with respect to the X axis of the corresponding radiation element. is doing. The difference between the first angle and the second angle can be about 90 degrees.

The capacitance between the first plurality of impedance elements can be controlled by using the plurality of tunable elements 128 which can be the first plurality of tunable elements. The capacitance between the second plurality of impedance elements can be controlled by using the second plurality of tunable elements.

As a more specific example, the plurality of metal strips 132 on the surface wave channel 125 can form a positive angle of about 45 degrees with respect to the X axis, and the plurality of metal strips 132 along the X axis. It is distributed. However, the multiple metal strips used for the second surface wave channel 145 can form a negative angle of about 45 degrees with respect to the X axis, and the multiple metal strips are dispersed along the X axis. ing. This change in tilt angle produces different linearly polarized radiations, which can generate circularly polarized radiation when combined with a 90 degree phase shift.

The figure of the antenna system 100 of FIG. 1 does not imply any physical or structural limitation to the methods in which the exemplary embodiments can be implemented. Other components may be used in addition to or in place of those shown. Some components may be arbitrary. Blocks are also presented to illustrate some functional components. When implemented in an exemplary embodiment, one or more of these blocks may be combined, divided, or combined and then divided into different blocks.

For example, in another exemplary example, the phase shifter 106 may not be included in the antenna system 100. Instead, multiple transmission lines 156 are used to connect multiple surface wave feeds 130 to multiple power distributors and / or other types of components, and to connect these different components to the high frequency module 108. You may. In some examples, the plurality of transmission lines 156 can connect the plurality of surface wave feeds 130 directly to the high frequency module 108.

In some exemplary examples, one of the plurality of tunable elements 128 may be mounted as a pocket of variable material embedded in a dielectric substrate 124. As used herein, the "variable material" can be any material with a variable permittivity. The permittivity of the variable material can be varied, for example, to change the capacitance between the two impedance elements in which the variable material is placed. The variable material may be a voltage variable material or may be, but is not limited to, a liquid crystal material or any electrically variable material such as, for example, a liquid crystal material or barium strontium titanate (BST). ..

In another exemplary example, the tunable element of one of the plurality of tunable elements 128 may be part of the corresponding impedance element of the plurality of impedance elements 126. For example, a resonant structure with a tunable element can be used. The resonant structure may be, for example, a split ring resonator, an electrically connected resonator, or some other type of resonant structure, but is not limited thereto.

Next, with reference to FIG. 2, a diagram of the antenna system is shown according to an exemplary embodiment. The antenna system 200 can be an embodiment for the antenna system 100 of FIG. As shown, the antenna system 200 includes a tunable artificial impedance surface antenna (AISA) 201, which can be an embodiment for the artificial impedance surface antenna 110 of FIG. In addition, the antenna system 200 can also include a voltage controller 202 and a phase shifter 203. The voltage controller 202 and the phase shifter 203 can be examples of the voltage controller 104 and the phase shifter 106 of FIG. 1, respectively.

In this exemplary example, the tunable artificial impedance surface antenna 201 is a relatively low cost antenna that can be electronically steered in both theta θ and phi φ directions. When the tunable artificial impedance surface antenna 201 is operating in the XY plane, the theta direction can be the direction orthogonal to the Z axis orthogonal to the XY plane, while the phi direction is. The direction can be parallel to the XY plane.

As shown, the tunable artificial impedance surface antenna 201 includes a dielectric substrate 206, a metal strip 207, a varicap 209, and a high frequency (RF) surface wave feed 208. The metal strip 207 can be a periodic array of metal strips 207 disposed on one side of the dielectric substrate 206. The varicap 209 can be placed between the metal strips 207. The dielectric substrate 206 may or may not have a ground plane (not shown in this figure) on the surface of the dielectric substrate 206 opposite to the surface on which the metal strip 207 is located.

The steering of the main lobe of the tunable artificial impedance surface antenna 201 in theta direction is controlled by changing, or modulating, the surface wave impedance of the tunable artificial impedance surface antenna 201. For example, the impedance of the tunable artificial impedance surface antenna 201 can be varied, or modulated, by controlling the voltage applied to the metal strip 207 disposed on the surface of the dielectric substrate 206. Due to the presence of the varicap 209 between the metal strips 207, the voltage applied to the varicaps 209 can be controlled by using the metal strip 207. Each of the varicaps 209 is a type of diode with a capacitance that varies as a function of the voltage applied between the terminals of the diode.

The voltage applied to the metal strip 207 can, in turn, change the capacitance of the varicap 209 between the metal strips 207, which can change the impedance of the tunable artificial impedance surface antenna 201. That is, the capacitance of the varicap 209 can be changed by controlling the voltage applied to the metal strip 207. By varying the capacitance of the varicap 209, the capacitance coupling and impedance between the metal strips 207 can be varied or modulated in order to steer the beam produced by the antenna system 200 in theta direction. can.

In this exemplary example, the high frequency surface wave feed 208 can be a two-dimensional array of high frequency surface wave feeds. The steering of the main lobe of the tunable artificial impedance surface antenna 201 in the phi direction is controlled by changing the relative phase difference between the high frequency surface wave feeds 208.

The voltage controller 202 is used to apply a direct current (DC) voltage to the structural metal strip 207 of the tunable artificial impedance surface antenna 201. The voltage controller 202 can be controlled based on the command received via the control bus 205. Thus, the control bus 205 provides control for the voltage controller 202. Further, the control bus 204 can provide control for the phase shifter 203. Each of the control bus 204 and the control bus 205 may be a bus from a microprocessor, a central processing unit (CPU), one or more computers, or some other type of computer or processor.

In this exemplary example, the polarity of the varicap 209 can be aligned so that all varicap connections to any one of the metal strips 207 can be connected with the same polarity. One terminal of the varicap can be called an anode and the other terminal can be called a cathode. Thus, some of the metal strips 207 are only connected to the anode of the varicap 209, while the other metal strips 207 are only connected to the anode of the varicap 209. Also, as shown, adjacent metal strips 207 can alternate with respect to those connected to the anode of the varicap 209 and those connected to the cathode of the varicap 209.

The spacing of the metal strips 207 in one dimension of the tunable artificial impedance surface antenna 201 that can be in the X direction is that of the high frequency high frequency surface waves propagating from the high frequency surface wave feed 208 across the tunable artificial impedance surface antenna 201. It may be a fraction of the wavelength. In an exemplary example, the spacing between the metal strips 207 can be at most 2/5 of the wavelength of the high frequency high frequency surface waves. In another exemplary example, this fraction can be only about 2/10 of the wavelength of a high frequency high frequency surface wave. Depending on the mounting, the spacing of the varicaps 209 connected to the metal strip 207 in two dimensions of the tunable artificial impedance surface antenna 201, which can be in the Y direction, may be approximately the same as the spacing of the metal strip 207.

The high frequency surface wave feed 208 can form a phased array joint feed structure or can take the form of a homogeneous surface wave feed integrated into the tunable artificial impedance surface antenna 201. Surface wave feeds can be integrated into the tunable artificial impedance surface antenna 201, for example using microstrip. The spacing of the high frequency surface wave feed 208 in the Y direction can be based on selected rules indicating that the spacing is not too far from the free space wavelength for the highest frequency signal transmitted or received.

In this exemplary example, the thickness of the dielectric substrate 206 can be determined by the permittivity of the dielectric substrate 206 and the frequency of radiation transmitted or received. The higher the dielectric constant, the thinner the dielectric substrate 206 may be.

To obtain different angles of radiation, the capacitance value of the varicap 209 can be determined by the range required for the desired impedance modulation for the tunable artificial impedance surface antenna 201. Further, the specific substrate used for the dielectric substrate 206 can be selected based on the operating frequency of the tunable artificial impedance surface antenna 201, that is, the radio frequency.

For example, when the tunable artificial impedance surface antenna 201 is operating at about 20 GHz, the dielectric substrate 206 is mounted using a substrate with a thickness of about 50 mm (mm) available from Rogers. However, it is not limited to this. In this example, the dielectric substrate 206 can have a relative permittivity equal to about 12.2. The metal strip 207 can be separated from about 2 mm to about 3 mm on the dielectric substrate 206. Further, in this example, the high frequency surface wave feed 208 can be separated by about 2.5 cm and the varicap 209 can be separated by about 2 mm to about 3 mm. The varicap 209 can change the capacitance from about 0.2 picofarads (pF) to about 2.0 picofarads. Of course, other specifications may be used for the tunable artificial impedance surface antenna 201 for different radiation frequencies.

A transmit / receive module 210 is connected to the phase shifter 203 for transmitting or receiving high frequency signals using the tunable artificial impedance surface antenna 201. The phase shifter 203 can be a one-dimensional phase shifter in this exemplary example. The phase shifter 203 can be implemented using any type of commonly available phase shifter, including those used for phased array antennas.

In this exemplary example, the phase shifter 203 includes a transmit / receive module 210, a power distributor 212, and a high frequency transmission line 211 connected to the phase shifter 213. The phase shifter 213 is controlled by a voltage control line 216 connected to a digital-to-analog converter (DAC) 214. The digital / analog converter 214 receives a digital control signal from the control bus 204 in order to control the steering in the phi direction.

The main lobe of the tunable artificial impedance surface antenna 201 can be steered in the phi direction using a phase shifter 203 to perform a phase shift between each of the high frequency surface wave feeds 208. When the high frequency surface wave feeds 208 are uniformly spaced, the phase shift between adjacent high frequency surface wave feeds 208 can be substantially constant. The relationship between the steering angle of phi (φ) and the phase shift can be calculated using the standard phased array method according to the following equation.
φ ＝ sin ⁻¹ (λΔψ / 2πd) (1)
Where λ is the emission wavelength, d is the spacing of the high frequency surface wave feeds 208, and Δψ is the phase shift between these surface wave feeds. In some cases, these surface wave feeds may be non-uniformly spaced and the phase shift is adjusted accordingly.

As described above, the main lobe of the tunable artificial impedance surface antenna 201 is of theta (θ) by applying a voltage to the varactor 209 so that the tunable artificial impedance surface antenna 201 has a surface wave impedance Z _SW. Can be steered in a direction, this impedance Z _SW is cyclically modulated or varied at a distance (x) from the high frequency surface wave feed 208 according to the following equation:
Z _sw = X + Mcos (2πx / p) (2)
Here, X and M are the average impedance and amplitude of the tunable artificial impedance surface antenna 201, respectively, and p is the modulation period. Changes in the surface wave impedance Z _SW can be modulated in a sinusoidal manner.

Theta steering angle θ is related to impedance modulation by the following equation:
θ ＝ sin ⁻¹ (n _sw −λ / p) (3)
Here, λ is the wavelength of radiation, n _sw is as follows, and is the average surface wave index.

The beam is steered in theta direction by adjusting the voltage applied to the varicap 209 so that X, M, and p have the desired theta steer angle θ. The dependence of surface wave impedance on the varactor capacitance is calculated using the transcendental equation resulting from the resonance method on the horizontal axis or using full-wave numerical simulation.

A voltage can be applied to the varicap 209 by grounding the alternating metal strips 207 to the ground 220 via the voltage control line 218 and applying a tunable voltage to the remaining metal strips 207 via the voltage control line 219. can. The voltage applied to each voltage control line 219 may be a function of the desired theta steering angle or may be different for each voltage control line 219. The voltage may be applied from a digital-to-analog converter (DAC) 217 that receives digital control from control bus 205 by a controller for steering in theta direction. The controller may be a microprocessor, central processing unit (CPU), or any computer, processor, or controller.

One advantage of grounding half of the metal strip 207 is that only half of the voltage control line 219 is required for the presence of the metal strip 207. However, in some cases, the spatial resolution of the voltage control, and therefore the impedance modulation, can be limited to twice the spacing of the metal strips 207.

Next, with reference to FIG. 3, a partial side view of the tunable artificial impedance surface antenna 201 of FIG. 2 is shown according to an exemplary embodiment. In this exemplary example, the dielectric substrate 206 has a ground plane 300.

Next, with reference to FIG. 4, diagrams of different configurations of the antenna system are shown according to exemplary embodiments. The antenna system 400 can be an embodiment for the antenna system 100 of FIG. The antenna system 400 includes a tunable artificial impedance surface antenna (AISA) 401, which can be an embodiment for the artificial impedance surface antenna 110 of FIG.

The antenna system 400 and the tunable artificial impedance surface antenna 401 can be implemented in the same manner as the antenna system 200 and the tunable artificial impedance surface antenna 201 of FIG. 2, respectively. As shown, the antenna system 400 includes a tunable artificial impedance surface antenna 401, a voltage controller 402, and a phase shifter 403. The tunable artificial impedance surface antenna 401 includes a dielectric substrate 406, a metal strip 407, a varicap 409, and a high frequency surface wave feed 408. Further, the antenna system 400 can include a transmit / receive module 410.

However, in this exemplary example, the voltage controller 402 may be mounted differently than the voltage controller 202 is mounted in FIG. In FIG. 4, the voltage controller 402 can include a voltage line 411 that allows a voltage to be applied from the digital / analog converter 412 to each of the metal strips 407. By alternating the metal strips 407, they are not grounded as in Figure 2. The digital / analog converter 412 can receive digital control from the control bus 205 of FIG. 2 by means of, for example, a controller 414 for steering in theta direction. Controller 414 may be implemented using a microprocessor, central processing unit, or some other type of computer or processor. Steering in the phi direction can be performed using the phase shifter 403 in the same manner that the phase shifter 203 is used in FIG.

Using the voltage line 411, which applies a voltage to all of the metal strips 407, requires twice the control voltage as compared to the antenna system 200 of FIG. However, the spatial resolution of the impedance modulation of the tunable artificial impedance surface antenna 401 is doubled. In this exemplary example, the voltage applied to each voltage line 411 is a function of the desired theta steering angle and may be different for each voltage line 411.

Next, with reference to FIG. 5, a diagram of another configuration of the antenna system is shown according to an exemplary embodiment. The antenna system 500 can be an embodiment for the antenna system 100 of FIG. The antenna system 500 includes a tunable artificial impedance surface antenna (AISA) 501, which can be an embodiment for the artificial impedance surface antenna 110 of FIG.

The antenna system 500 and the tunable artificial impedance surface antenna 501 can be implemented in the same manner as the antenna system 200 and the tunable artificial impedance surface antenna 201 of FIG. 2, respectively. Further, the antenna system 500 and the tunable artificial impedance surface antenna 501 can be implemented in the same manner as the antenna system 400 and the tunable artificial impedance surface antenna 401 of FIG. 4, respectively.

As shown, the antenna system 500 includes a tunable artificial impedance surface antenna 501, a voltage controller 502, and a phase shifter 503. The tunable artificial impedance surface antenna 501 includes a dielectric substrate 506, a metal strip 507, a varicap 509, and a high frequency surface wave feed 508. Further, the antenna system 500 can include a transmit / receive module 510.

However, in this exemplary example, the voltage controller 502 is mounted differently from how the voltage controller 202 is mounted in FIG. 2 and how the voltage controller 402 is mounted in FIG. obtain. In FIG. 5, the digital / analog converters of FIGS. 2 and 4 are replaced by a variable voltage source 512.

As the voltage of the variable voltage source 512 changes, the emission angle of the beam generated by the tunable artificial impedance surface antenna 501 changes between the minimum theta steering angle and the maximum theta steering angle. This range for theta steering angle can be determined by the design configuration details of the tunable artificial impedance surface antenna 501.

The voltage is applied to the metal strip 507 via the voltage control line 514 and the voltage control line 516. The voltage control line 516 can provide grounding for the metal strip 507, while the voltage control line 514 can provide the metal strip 507 with a variable voltage. Over the X dimension, the metal strips 507 are alternately connected to voltage control lines 514 or voltage control lines 516. That is, they are grounded by alternating metal strips 507.

The metal strip 507 can have centers evenly spaced in the X dimension with the width of the metal strip 507 varying periodically in period (p) 518. The number of metal strips 507 in period 518 may be arbitrary. For example, the metal strip 507 can be 10 to 20 metal strips per cycle 518. The change in width for each period 518 may be configured to generate a surface wave impedance with periodic modulation in the X direction at period 518, for example the change in the sinusoidal curve of equation (3) above. It's a change.

Tunerable Artificial Impedance The surface wave impedance at each point on the surface antenna 501 is determined by the respective width of the metal strip 507 and the voltage applied to the varicap 509. The capacitance of the varicap 509 can change with varying applied voltages. When the voltage is about 0 volts, the capacitance of the _varicap can be the maximum of C max. As the voltage increases, the capacitance decreases until the capacitance reaches the minimum of _{C min.} As the capacitance changes, the impedance modulation parameters X and M change _{from the minimum values of X min} and M _min to the maximum values of X _max and M _max , respectively, as explained in the above equation (2). can do.

Further, the average surface wave index of the above equation 4 changes in the following range.

Further, as described in Equation 3 above, the range in which the radiation angle of the tunable artificial impedance surface antenna 501 can be scanned depends on the change of a single control voltage.
θ _min = sin ^-1 (n _min −λ / p) (5)
From the minimum value of θ _max = sin ^-1 (n _max −λ / p) (6)
Can vary up to the maximum value of.

Next, with reference to FIG. 6, a side view of the dielectric substrate is shown according to an exemplary embodiment. In this exemplary example, the dielectric substrate 601 can be used to mount the dielectric substrate 206 according to FIG. 2, the dielectric substrate 406 according to FIG. 4, and / or the dielectric substrate 506 according to FIG. The dielectric substrate 601 can have a dielectric constant that changes with the application of an electric field.

The metal strip 602 is shown arranged on one side of the dielectric substrate 601. As shown, the varicap is not used in this exemplary example. When a voltage is applied to the metal strip 602, an electric field is also generated between the adjacent metal strips 602 and between the metal strip 602 and the ground plane 603. The electric field changes the permittivity of the dielectric substrate 601 that results in a change in capacitance between adjacent metal strips 602. The capacitance between the adjacent metal strips 602 determines the surface wave impedance of the tunable artificial impedance surface antenna using the dielectric substrate 601.

Next, with reference to FIG. 7, a diagram of the dielectric substrate 601 of FIG. 6 having an embedded pocket of material is shown according to an exemplary embodiment. In this exemplary example, the dielectric substrate 601 can take the form of an inert substrate 700. A voltage difference can be applied to the adjacent metal strips 602, which can generate an electric field between the metal strips 602 and generate a change in permittivity in the pockets of the variable material 702 located between the metal strips 602. can.

The pocket of the variable material 702 can be an example of one way in which the plurality of tunable elements 128 of FIG. 1 can be mounted. The variable material in the pocket of the variable material 702 may be, but is not limited to, a liquid crystal material or any electrically variable material such as barium titanate strontium (BST). Specifically, the variable material 702 is embedded in a pocket within the dielectric substrate 601 between the metal strips 602.

Next, with reference to FIG. 8, a diagram of the antenna system is shown according to an exemplary embodiment. In this exemplary example, the antenna system 800 can be an embodiment for the antenna system 100 of FIG. The antenna system 800 includes an antenna 802, a voltage controller 803, a phase shifter 804, and a high frequency module 806. The antenna 802, the voltage controller 803, the phase shifter 804, and the high frequency module 806 can be examples of the antenna 102, the voltage controller 104, the phase shifter 106, and the high frequency module 108 of FIG. 1, respectively.

The antenna 802 is supplied with voltage by the voltage controller 803. The voltage controller 803 includes a digital-to-analog converter (DAC) 808 and a voltage line 811. The digital / analog converter 808 can be an embodiment for one voltage source in the plurality of voltage sources 146 of FIG. The voltage line 811 can be an embodiment for the plurality of voltage lines 150 of FIG.

A voltage can be applied from the digital / analog converter 808 to the antenna 802 via the voltage line 811. The controller 810 can be used to control the voltage signal transmitted from the digital / analog converter 808 to the antenna 802. The controller 810 can be an embodiment for the controller 151 of FIG. In this exemplary example, the controller 810 can be considered as part of the antenna system 800.

As shown, the antenna 802 can include a radiating structure 812 formed by an array of radiating elements 813. The radiating element array 813 can be an embodiment of the radiating element array 122 of FIG. In this exemplary example, each radiating element in the radiating element array 813 may be implemented as a surface wave waveguide on an artificial impedance surface.

The array of radiating elements 813 can include radiating elements 814, 815, 816, 818, 820, 822, 824, and 826. Each of these radiating elements can be mounted using a dielectric substrate. Also, each of these dielectric substrates will have multiple metal strips, multiple varactors, and surface wave feeds located on the surface of the dielectric substrate forming surface wave channels for the corresponding radiating elements. Can be done.

As an exemplary example, the radiating element 814 can be formed of a dielectric substrate 827. The plurality of metal strips 828 and the plurality of varicaps 830 may be placed on the surface of the dielectric substrate 827 to form the surface wave channel 831. Also, the surface wave feed 832 may be placed on the surface of the dielectric substrate 827. The plurality of metal strips 828 and the plurality of varicaps 830 can be examples of the plurality of metal strips 132 and the plurality of varicaps 134 in FIG. 1, respectively.

In transmit mode, the surface wave feed 832 sends a surface wave to the surface wave channel 831 of the radiating element 814. Surface wave channel 831 limits surface waves to propagate linearly along a limited path across multiple metal strips 828. Specifically, the surface wave channel 831 creates a region of high surface wave index surrounded by a region of low surface wave index to limit the surface wave to the configured path. The surface wave index is the ratio of the speed of light to the propagation speed of the surface wave.

The region of the high surface wave index is created by the metal strips 828 and the varicaps 830, while the region of the low surface wave index is created by the exposed surface of the dielectric substrate 827. The width of the region of the high surface wave index can be from 50% to about 100% with respect to the length of the surface wave wavelength. The wavelengths of surface waves are as follows.

Where λ _sw is the wavelength of the surface wave, f is the frequency of the surface wave, c is the velocity of light, and n _sw is the surface wave index.

Each of the plurality of metal strips 828 located on the dielectric substrate 827 can have the same width. Also, these metal strips can be evenly spaced along the dielectric substrate 827. In addition, the plurality of varicaps 830 can also be evenly spaced along the dielectric substrate 827. That is, the plurality of metal strips 828 and the plurality of varicaps 830 may be periodically dispersed on the dielectric substrate 827. Also, the plurality of varicaps 830 can be aligned so that all of the varicaps connections of the plurality of metal strips 828 have the same polarity.

The thickness of the dielectric substrate 827 can be determined by its permittivity and the frequency of radiation transmitted or received. The higher the dielectric constant, the thinner the dielectric substrate 827 may be.

Capacitance values for multiple varicaps 830 can be determined by the range required for the desired impedance modulation for different angles of radiation. The main lobe of the radiation pattern generated by the antenna 802 can be electronically steered in theta direction by applying a voltage to the various varicaps in the array 813 of the radiation element. A voltage can be applied to these varactors such that the antenna 802 has a surface wave impedance that varies in a sinusoidal manner at a distance x from the surface wave feeds on different dielectric substrates.

The voltage from the digital / analog converter 808 can be applied to the metal strip on the array 813 of the radiating element via the voltage line 811. In this exemplary example, the surface wave propagating across the array 813 of the radiating element may be connected to the phase shifter 804 by a surface wave feed on the array 813 of the radiating element. The phase shifter 804 includes a plurality of phase shift devices 834.

The main lobe of antenna 802 can be electronically steered in the phi direction by providing a phase shift between the respective surface wave feeds on the array 813 of the radiating element. When the surface wave feeds are evenly spaced, the phase shift between adjacent surface wave feeds can be substantially constant. The relationship between the phi steering angle and this phase shift can be calculated as follows.

In another exemplary example, the high frequency module, phase shifter, and multiple surface wave feeds may be on the opposite side of the antenna 802 with respect to the high frequency module 806. This configuration may be used to facilitate steering in the negative theta direction.

Next, with reference to FIG. 9, another figure of the antenna system is shown according to an exemplary embodiment. In this exemplary example, the antenna system 900 can be an embodiment for the antenna system 100 of FIG. The antenna system 900 includes an antenna 902, a voltage controller 903, a phase shifter 904, and a high frequency module 906.

The voltage controller 903 is configured to supply voltage to the antenna 902. The voltage controller 903 includes a variable voltage source 908. The voltage line 911 applies voltage to the antenna 902, while the voltage line 913 provides grounding for the antenna 902.

Antenna 902 can include an array of radiating elements 915, which may include radiating elements 912, 914, 916, 918, 920, 922, 924, and 926. Each of these radiating elements can be mounted using a dielectric substrate. Surface wave channels can be formed on each radiating element by a plurality of metal strips, a plurality of varicaps, and a dielectric substrate.

For example, the radiating element 912 can be formed using the dielectric substrate 927. A first plurality of metal strips 928, a second plurality of metal strips 930, and a plurality of varicaps 932 located on the surface of the dielectric substrate 927 can form a surface wave channel 931. Further, the surface wave feed 933 is arranged on the surface of the dielectric substrate 927, and connects the surface wave propagating along the surface wave channel 931 to the phase shifter 904.

Each of the first plurality of metal strips 928 located on the array of radiating elements 915 can have the same width. In addition, each of the second plurality of metal strips 930 located on the array 915 of the radiating element can also have the same width. The width of the metal strips in both the first plurality of metal strips 928 and the second plurality of metal strips 930 varies periodically along the dielectric substrate 927 with period p934. This period can be determined by the size of the metal strip, the radiation frequency, the theta steering angle, and the properties and thickness of the dielectric substrate 927.

Only two widths for metal strips are shown in one cycle, but any number of metal strips may be included in one cycle. Further, any number of different widths may be included in one cycle.

The voltage from the variable voltage source 908 may be applied to the first plurality of metal strips 928 via the voltage line 911. The second plurality of metal strips 930 may be grounded via the voltage line 913.

In this exemplary example, the surface wave propagating on the array 915 of the radiating element may be transmitted to the phase shifter 904 as a high frequency signal by the surface wave feed on the array 915 of the radiating element. As shown, the phase shifter 904 comprises a plurality of phase shift devices 936.

The transmission line 938 connects the surface wave feed to the plurality of phase shift devices 936 and the plurality of phase shift devices 936 to the high frequency module 906. The high frequency module 906 may be configured to function as a transmitter, receiver, or a combination thereof.

Next, with reference to FIG. 10, the figure of the antenna system 900 of FIG. 9 with different voltage controllers is shown according to an exemplary embodiment. In this exemplary example, the voltage controller 903 in FIG. 9 is replaced by the voltage controller 1000. The voltage controller 1000 includes a ground 1002, a digital / analog converter 1004, a voltage line 1006, and a voltage line 1008.

The voltage line 1006 allows the second plurality of metal strips 930 to be grounded to ground 1002. The voltage line 1008 supplies voltage from the digital / analog converter 1004 to the first plurality of metal strips 928. Controller 1010 is used to control the digital / analog converter 1004. In this exemplary example, different voltages are sent to each radiating element within the radiating element array 915.

Also, as shown, the phase shifter 904 is not included in this configuration for the antenna system 900. The transmission line 1012 connects the high frequency module 906 directly to the surface wave feed on the array 915 of the radiating elements.

In this exemplary example, the radiation pattern created by antenna 902 is steered towards theta by controlling the voltage applied to different varicaps in the array 915 of the radiation element. The radiation pattern created by antenna 902 is steered in the phi direction by a slight change in the surface wave index between adjacent radiation elements. This change results in a phase shift between surface waves propagating along these radiating elements that steer in the phi direction.

Then, with reference to FIGS. 11A and 11B, a diagram of yet another configuration of the antenna system 900 is shown according to an exemplary embodiment. In this exemplary example, the phase shifter 904 in FIG. 9 is replaced by the phase shifter 1100.

The phase shifter 1100 can be used to control the phi steering angle for the antenna system 900. The phase shifter 1100 includes waveguides 1102, 1104, 1106, 1108, 1110, 1112, 1114, and 1116. Each of these waveguides is a surface wave waveguide formed by a plurality of metal strips and a plurality of varicaps located on a dielectric substrate. To steer the radiation towards the phi steering angle, to control the phase of the surface waves propagating along these waveguides, apply a voltage to at least a portion of the metal strips on different dielectric substrates. Can be applied.

The phase of the surface wave can be controlled so that the phase shift of the surface wave at the end of the adjacent waveguide is Δψ. The phase of the surface wave at the end of each waveguide changes by controlling the propagation velocity of the surface wave. The surface wave propagation velocity can be controlled by controlling the voltage applied to the varicap on the dielectric substrate.

The voltage controller 1118 can be used to apply voltage to at least a portion of the metal strip of the dielectric substrate and thereby at least a portion of the varicaps on the dielectric substrate. The voltage controller 1118 includes a digital / analog converter 1120, voltage lines 1122, and ground 1121. Voltage can be applied from the digital / analog converter 1120 by voltage line 1122 to at least a portion of the metal strip on the dielectric substrate. Other parts of the metal strip may be grounded to ground 1121. Controller 1123 can be used to control the digital / analog converter 1120.

The phase of the surface wave at the end of the waveguide can be given by the following equation.
ψ (V) = 2πn _sw (V) f / c (9)
Here, n _sw (V) is the surface wave index and depends on the voltage. Each waveguide can be controlled by a different voltage from the voltage controller 1118 to generate a phase difference in the surface wave feed on the waveguide. The high frequency signal may be transmitted between the surface wave feed and the high frequency module 906 through transmission line 1124.

Next, with reference to FIG. 12, some diagrams of the antenna system are shown according to exemplary embodiments. This exemplary example shows a portion of the antenna system 1200. The antenna system 1200 is an embodiment for the antenna system 100 of FIG. As shown, the antenna system 1200 includes a radiating element 1201 and a high frequency assembly 1202.

Radiating element 1201 is an embodiment for radiating element 123 of FIG. Further, the radiating element 1201 is an embodiment of the radiating element array 122 of FIG. 1, which includes only a single radiating element. Only part of the radiating element 1201 is shown in this exemplary example. In this example, the radiation pattern produced by the antenna system 1200 can be electronically scanned in the XZ plane.

In this exemplary example, the high frequency assembly 1202 includes a high frequency module 1203, a phase shift device 1204, transmission lines 1206, transmission lines 1208, surface wave feed 1210, and surface wave feed 1211. The high frequency module 1203 may be configured to function as a transmitter, receiver, or a combination thereof. The phase shift device 1204 takes the form of a hybrid power splitter in this example. Specifically, the hybrid power splitter is configured to be used to change the phase difference between a high frequency signal traveling along transmission line 1206 and a high frequency signal traveling along transmission line 1208. .. In this exemplary example, a hybrid power splitter can be used to vary the phase difference between these two transmission lines between about 0 and about 90 degrees.

Of course, in other exemplary examples, the high frequency module 1203 and the phase shift device 1204 may be implemented in other ways. For example, the high frequency module 1203 may be configured to allow double polarization using a phase shift device 1204 in the form of a four port phase variable power splitter.

The radiating element 1201 is mounted using the dielectric substrate 1205. The surface wave channel 1212 and the surface wave channel 1213 are formed on the dielectric substrate 1205. The surface wave feed 1210 connects the transmission line 1206 to the surface wave channel 1212. Surface wave feed 1211 connects transmission line 1208 to surface wave channel 1213. The surface wave channel 1212 and the surface wave channel 1213 can be an embodiment for the surface wave channel 125 and the second surface wave channel 145 of FIG.

As shown, the surface wave channel 1212 is formed by a plurality of metal strips 1214 and a plurality of varicaps 1215. In this exemplary example, the plurality of metal strips 1214 are periodically arranged at an angle of about 45 degrees positive with respect to the X-axis 1216. The X-axis 1216 is a longitudinal axis along the radiating element 1201. The plurality of varicaps 1215 are electrically connected to the plurality of metal strips 1214. The voltage line 1218 is used to apply a voltage to a plurality of varicaps 1215. Pin 1220 can be used to connect the voltage line 1218 to one or more voltage sources and / or one or more grounds.

Also, as shown, the surface wave channel 1213 is formed by a plurality of metal strips 1224 and a plurality of varicaps 1226. As shown, the plurality of metal strips 1224 are periodically arranged at an angle of about 45 degrees negative with respect to the X-axis 1216. The voltage line 1228 is used to apply a voltage to a plurality of varicaps 1226. Pin 1230 is used to connect the voltage line 1228 to one or more voltage sources and / or one or more grounds.

The radiation pattern formed by the radiation element 1201 can be scanned in the X-Z plane by varying the voltage applied to the plurality of varicaps 1215, resulting in surface wave impedance at the desired radiation angle. Brings a modulation pattern. The surface wave channel 1212 and the surface wave channel 1213 are configured so that radiation from these two surface wave channels can be orthogonal to each other. The final radiation from the combination of these two surface wave channels is circularly polarized. When supplied by the phase shift device 1204 in the form of a 0 ° to 90 ° hybrid splitter, the surface wave channel 1212 and the surface wave channel 1213 are either right-polarized or left-polarized circles that receive or transmit. It is fixed to polarized radiation. Naturally, in another exemplary example, the phase shift device 1204 is in some other way such that radiation can be switched between left circularly polarized waves (LHCP) and right circularly polarized waves (RHCP). It may be implemented.

Radiations from surface wave channels 1212 and surface wave channels 1213 are polarized by the angle at which the metal strips 1214 and the metal strips 1224 are tilted with respect to the X-axis 1216, respectively. The plurality of metal strips 1214 and the plurality of metal strips 1224 are tensor impedance elements having a long spindle orthogonal to the long side of the metal strip and a short axis along this side. The local tensor admittance of each surface wave channel in the coordinate frame of this spindle can be given by the following equation.

Where Y _sw is a local tensor admittance, determined by the voltage applied to the metal strip at position x.

The surface wave currents along the long spindle are as follows.

Where J _sw is the surface wave current and E _sw is the surface wave electric field.

Radiation is driven by surface wave current according to the following equation.

Therefore, it is polarized in the direction across the gap between the metal strips. E _rad is the electric field of radiation.

Next, with reference to FIG. 13, the figure of the antenna system 1200 of FIG. 12 with two high frequency assemblies is shown according to an exemplary embodiment. In this exemplary example, the high frequency assembly 1202 is located at the end 1300 of the radiating element 1201, while the high frequency assembly 1301 is located at the end 1303 of the radiating element 1201.

The high frequency assembly 1301 includes a high frequency module 1302, a phase shift device 1304, a transmission line 1306, a transmission line 1308, a surface wave feed 1310, and a surface wave feed 1312. The surface wave feed 1310 flows into the surface wave channel 1212. The surface wave feed 1312 also flows into the surface wave channel 1213.

Either the high frequency assembly 1301 or the high frequency assembly 1202 can act as a sink for any undissipated surface wave energy. This allows surface waves to prevent reflections from the ends of the radiating element 1201 that can lead to unwanted distortion of the radiating pattern.

Also, by having two high frequency assemblies, the radiation pattern can be adjusted more effectively over a larger angular range. Therefore, if the radiation is tilted towards the positive part of the X-axis 1216, the high frequency assembly 1202 can be used to deliver the high frequency signal to the radiating element 1201. If the radiation is tilted towards the negative part of the X-axis 1216, the high frequency assembly 1301 can be used to deliver the high frequency signal to the radiating element 1201. Thus, since the high frequency beam formed by the radiation pattern is scanned at an angle, the beams directed at the positive and negative theta angles can be mirror images of each other.

Next, with reference to FIG. 14, a diagram of another antenna system is shown according to an exemplary embodiment. In this exemplary example, the antenna system 1400 is another embodiment for the antenna system 100 of FIG. The antenna system 1400 includes an antenna 1401, a phase shifter 1402, and a high frequency module 1404. The antenna system 1400 may also include a voltage controller (not shown in this example).

Antenna 1401 includes an array of radiating elements 1406 and multiple surface wave feeds 1407. The array of radiating elements 1406 includes radiating elements 1408, 1410, 1412, 1414, 1416, 1418, 1420, and 1422. Each of these radiating elements can be mounted in the same manner as the radiating element 1201 of FIG.

Multiple surface wave feeds 1407 connect an array of radiating elements 1406 to a phase shifter 1402. The phase shifter 1402 includes a plurality of phase shift devices 1424. The transmission line 1426 connects the surface wave feed 1407 to a plurality of phase shift devices 1424 and the plurality of phase shift devices 1424 to the high frequency module 1404. The high frequency module 1404 may be configured to function as a transmitter, receiver, or a combination thereof.

The plurality of phase shift devices 1424 are variable phase shifters in this example. In this exemplary example, multiple phase shift devices 1424 can be tuned such that the final phase shift in each of the plurality of surface wave feeds 1407 differs from the phase of adjacent surface wave feeds by a constant Δφ. .. As this constant changes, the resulting radiation pattern can be scanned in the YZ plane.

The figures in FIGS. 2-14 do not imply physical or structural limitations to the methods in which exemplary embodiments can be implemented. Other components may be used in addition to or in place of those shown. Some components may be arbitrary.

The different components shown in FIGS. 2 to 14 can be used as exemplary examples of how the components shown in block form in FIG. 1 can be implemented as physical structures. In addition, some of the components of FIGS. 2 to 14 may be combined with the components of FIG. 1, may be used together with the components of FIG. 1, or may be a combination of the two. good.

In some cases, it may be desirable to improve the gain of an antenna such as the artificial impedance surface antenna 110 in FIG. The gain of the artificial impedance surface antenna can be improved by improving the accuracy with which the artificial impedance surface antenna is electronically steered to reduce the drop in gain. An exemplary embodiment recognizes and considers a substantially radial arrangement of surface wave channels that may allow for more accurate electronic steering of artificial impedance surface antennas. Also, using this type of arrangement, impedance devices used to form surface wave channels can be separated by more than half a wavelength. In addition, this type of arrangement can be used to generate radiation of any polarization.

Next, with reference to FIG. 15, diagrams of different configurations of the artificial impedance surface antenna 110 in the antenna system 100 of FIG. 1 are shown in the form of an exemplary embodiment and thus in the form of a block diagram. The antenna system 100 of FIG. 1 is represented by an artificial impedance surface antenna 110 having a radial configuration 1500.

When the artificial impedance surface antenna 110 has a radial configuration 1500, the artificial impedance surface antenna 110 includes a dielectric substrate 1501, a plurality of radiating spokes 1502, and a plurality of surface wave feeds 1504. The dielectric substrate 1501 can be mounted in the same manner as the dielectric substrate 124 of FIG. However, in the radial configuration 1500, the dielectric substrate 1501 can be the only dielectric substrate used. The dielectric substrate 1501 can be composed of any number of layers of dielectric material.

In an exemplary example, the dielectric substrate 1501 may be composed of a material with adjustable electrical properties. For example, the dielectric substrate 1501 may be made of a liquid crystal material, but is not limited thereto.

In this exemplary example, the dielectric substrate 1501 has a circular 1506 with a center point 1508. That is, the dielectric substrate 1501 can be substantially symmetric with respect to the center point 1508. In another exemplary example, the dielectric substrate 1501 may have some other shape. For example, the dielectric substrate 1501 can have, but is not limited to, an ellipse, a quadrangle, a hexagon, an octagon, or some other type of shape. However, if the dielectric substrate 1501 is not substantially symmetric with respect to the center point 1508, the resulting radiation pattern 112 may not have the same gain at different steering angles.

Multiple radiating spokes 1502 can be mounted using the dielectric substrate 1501. Specifically, a plurality of radiating spokes 1502 can be formed on the dielectric substrate 1501.

The plurality of radiating spokes 1502 may be arranged radially with respect to the center point 1508 of the dielectric substrate 1501. In these exemplary examples, being radially located with respect to the center point 1508 means that each of the plurality of radiating spokes 1502 can extend from the center point 1508 towards the outer periphery of the dielectric substrate 1501. is doing. Each of the plurality of radiating spokes 1502 may be located approximately perpendicular to the central axis via the central point 1508 of the dielectric substrate 1501. In addition, each of the plurality of radiating spokes 1502 may be arranged such that each radiating spoke is substantially symmetrical with respect to the center point 1508.

Each of the plurality of radiating spokes 1502 can be mounted in the same manner as the radiating element 123 of FIG. The radiating spokes 1510 can be an embodiment of each radiating spoke of the plurality of radiating spokes 1502. The radiating spokes 1510 are configured to form surface wave channels 1512. Thus, the plurality of radiating spokes 1502 can form multiple surface wave channels. The surface wave channel 1512 is configured to limit the path of surface waves.

As shown, the radiating spokes 1510 can include a plurality of impedance elements 1514 and a plurality of tunable elements 1516. The plurality of impedance elements 1514 and the plurality of tunable elements 1516 can be mounted in the same manner as the plurality of impedance elements 126 and the plurality of tunable elements 128 in FIG. 1, respectively.

In this exemplary example, a plurality of impedance elements 1514 and a plurality of tunable elements 1516 can be arranged on the surface 1513 of the dielectric substrate 1501. Specifically, a plurality of impedance elements 1514 and a plurality of tunable elements 1516 can be arranged on the surface 1513 of the corresponding portion 1515 of the dielectric substrate 1501.

The plurality of impedance elements 1514, the plurality of tunable elements 1516, and the corresponding portion 1515 of the dielectric substrate 1501 can form an artificial impedance surface from which radiation can be generated. In this exemplary example, the corresponding portion 1515 of the dielectric substrate 1501 can be considered as part of the radiating spokes 1510. However, in another exemplary example, the dielectric substrate 1501 can be considered separate from the plurality of radiating spokes 1502.

One of a plurality of impedance elements 1514 can be mounted in a number of different ways. In an exemplary example, the impedance element may be mounted as a resonant element. In an exemplary example, the impedance device may be mounted as an element made of a conductive material. The conductive material may be, for example, a metallic material, but is not limited thereto. Depending on the mounting, the impedance element may be mounted as a metal strip, a patch of conductive paint, a metal mesh material, a metal film, a deposit of a metal substrate, or some other type of conductive element. In some cases, the impedance element may be, for example, a split ring resonator (SRR), an electrically connected resonator (ECR), a structure consisting of one or more metamaterials, or some other type of structure. It may be mounted as a resonance structure such as an element or an element.

Each of the plurality of tunable elements 1516 can be an element that can be controlled, i.e., adjusted to change the angle of the radiation pattern 112 produced by the radiation spokes 1510. In this exemplary example, each of the plurality of tunable elements 1516 can be an element having a capacitance that can be varied based on the voltage applied to the tunable element.

In an exemplary example, the plurality of impedance elements 1514 take the form of multiple metal strips 1518 and the plurality of tunable elements 1516 take the form of multiple varicaps 1520. Each of the plurality of varicaps 1520 may be a diode of the semiconductor device having a capacitance depending on the voltage applied to the diode of the semiconductor device.

The plurality of metal strips 1518 may be arranged in a row on the corresponding portion 1515 of the dielectric substrate 1501 substantially parallel to the plane substantially perpendicular to the central axis via the center point 1508 of the dielectric substrate 1501. For example, the plurality of metal strips 1518 may be periodically dispersed on the corresponding portion 1515 of the dielectric substrate 1501 along an axis that is substantially perpendicular to the central axis of the dielectric substrate 1501 and passes through this central axis.

In some exemplary examples, multiple metal strips 1518 may be printed on a dielectric substrate 1501. For example, multiple metal strips 1518 are printed on a dielectric substrate 1501 using any number of 3D printing techniques, additional deposition techniques, inkjet deposition techniques, or other types of printing techniques. obtain.

The plurality of varicaps 1520 may be electrically connected to a plurality of metal strips 1518 on the surface 1513 of the corresponding portion 1515 of the dielectric substrate 1501. As an exemplary example, at least one varicap of the plurality of varicaps 1520 can be placed between each metal strip of a pair of adjacent metal strips of the plurality of metal strips 1518. Also, a plurality of varicaps 1520 can be aligned so that all of the varicap connections on each metal strip have the same polarity.

By applying a voltage to a plurality of impedance elements 1514, a voltage can be applied to a plurality of tunable elements 1516. Specifically, the capacitance of the plurality of tunable elements 1516 is changed by changing the voltage applied to the plurality of impedance elements 1514. By changing the capacitance of the plurality of tunable elements 1516, the capacitance coupling and the impedance between the plurality of impedance elements 1514 can be changed, that is, modulated.

The corresponding portion 1515 of the dielectric substrate 1501, the plurality of impedance elements 1514, and the plurality of tunable elements 1516 may be configured for the selected design configuration 1522 for the surface wave channel 1512 formed by the radiating spokes 1510. .. Depending on the implementation, each radiating spoke of the plurality of radiating spokes 1502 may have the same or different selected design configurations.

As shown, the selected design configuration 1522 for the radiating spokes 1510 has multiple design parameters such as impedance element width 1524, impedance element spacing 1526, tunable element spacing 1528, and substrate thickness 1530. It may include, but is not limited to. The width 1524 of the impedance element can be the width of the impedance element in the plurality of impedance elements 1514. The width 1524 of the impedance element can be selected to be the same or different for each of the plurality of impedance elements 1514, depending on the implementation.

The impedance element spacing 1526 can be the spacing of the plurality of impedance elements 1514 along the surface 1513 of the corresponding portion 1515 of the dielectric substrate 1501. The spacing between the tunable elements 1528 can be the spacing between the plurality of tunable elements 1516 along the surface 1513 of the corresponding portion 1515 of the dielectric substrate 1501. Further, the thickness of the substrate 1530 can be set to the thickness of the corresponding portion 1515 of the dielectric substrate 1501. In this exemplary example, the entire dielectric substrate 1501 can have substantially the same thickness. However, in another exemplary example, different parts of the dielectric substrate 1501 corresponding to the different radiating spokes of the plurality of radiating spokes 1502 may have different thicknesses.

The values of the different parameters of the selected design configuration 1522 can be selected, for example, based on, but not limited to, the radiation frequency configured to operate the artificial impedance surface antenna 110. Other considerations include, for example, the desired impedance modulation for the artificial impedance surface antenna 110.

The surface wave propagated along each of the plurality of radiating spokes 1502 may be connected to the plurality of transmission lines 156 by the plurality of surface wave feeds 1504 arranged on the dielectric substrate 1501. Each of the plurality of surface wave feeds 1504 connects the corresponding radiating spokes of at least one of the plurality of radiating spokes 1502 to a transmission line carrying a high frequency signal, for example one of the plurality of transmission lines 156. ..

The surface wave feed of one of the plurality of surface wave feeds 1504 may be any device capable of converting the surface wave into a high frequency signal, the high frequency signal into a surface wave, or both. In an exemplary example, the surface wave feed of one of the plurality of surface wave feeds 1504 may be substantially located at the center point 1508 of the dielectric substrate 1501.

In an exemplary example, the plurality of surface wave feeds 1504 takes the form of a single surface wave feed located at the center point 1508 of the dielectric substrate 1501. This single surface wave feed, which can be called the central feed, can connect each of the plurality of radiating spokes 1502 to multiple transmission lines 156. In this example, the plurality of transmission lines 156 can take the form of a coaxial cable.

In another exemplary example, multiple surface wave feeds 1504 are located at or near center point 1508 and are configured to connect multiple radiating spokes 1502 to multiple transmission lines 156. It can take the form of a surface wave feed. In this example, the plurality of transmission lines 156 can take the form of a single transmission line or a plurality of transmission lines.

When the antenna 110 is in receive mode on the artificial impedance surface, the electromagnetic radiation received by the artificial impedance surface antenna 110 can be propagated as surface waves along a plurality of radiating spokes 1502. These surface waves are received by multiple surface wave feeds 1504 and converted into multiple high frequency signals 1532. The plurality of high frequency signals 1532 may be transmitted to the high frequency module 108 through one or more transmission lines 156. The high frequency module 108 can then process the plurality of high frequency signals 1532 accordingly.

When the antenna 110 is in transmit mode on the artificial impedance surface, the plurality of high frequency signals 1532 may be transmitted from the high frequency module 108 to the artificial impedance surface antenna 110 through the plurality of transmission lines 156. Specifically, the plurality of high frequency signals 1532 can be received by the plurality of surface wave feeds 1504 and converted into surface waves propagated along the plurality of radiated spokes 1502.

The radiation pattern 112 of the artificial impedance surface antenna 110 can be electronically steered in both theta and phi directions. The radiation pattern 112 can be formed by a plurality of radiation sub-patterns 1533. Multiple emission subpatterns 1533 can be generated by the corresponding parts of multiple emission spokes 1502. This corresponding part can be one or more radiating spokes 1502. In some cases, multiple emission subpatterns 1533 may be produced by all of the multiple emission spokes 1502.

For example, a plurality of radiated subpatterns 1533 can be generated by a plurality of radiated spokes out of a plurality of radiated spokes 1502. Each of the multiple radiation subpatterns 1533 is a radiation pattern produced by a particular radiation spoke. The plurality of radiation sub-patterns 1533 form the radiation pattern 112. For example, if a plurality of radiation subpatterns 1533 contains different radiation subpatterns corresponding to different radiation spokes, the combination and overlap of these different radiation subpatterns forms the radiation pattern 112.

In this exemplary example, each of the plurality of radiated spokes 1502 can be independently controlled so that each of the plurality of radiated subpatterns 1533 can be electronically steered. For example, radiation spokes 1510 may have, but are not limited to, radiation subpattern 1534. The radiation subpattern 1534 can be controlled independently of the other radiation subpatterns formed by the other radiation spokes of the plurality of radiation spokes 1502.

As an exemplary example, the voltage controller 104 is used to control the voltage applied to multiple tunable elements 1516 to control both theta and phi steering angles of the main lobe of radiation subpattern 1534. Can be done. Similarly, the voltage controller 104 has multiple radiating spokes 1502 on each of the plurality of radiating spokes 1502 in order to control both theta and phi steering angles of the main lobe of the radiating subpattern formed by each of the plurality of radiating spokes 1502. It may be configured to control the voltage applied to the tunable element.

Therefore, each of the plurality of emission subpatterns 1533 can be directed in a particular theta direction and a wide phi direction. For example, a particular radiation sub-pattern can be directed to a theta steering angle of about 45 degrees and spread over a wide range of phi angles. In this way, each radiation subpattern can form, for example, a fan beam.

The plurality of radiation sub-patterns 1533 overlap to form a radiation pattern 112 with a main lobe 116 oriented in a particular phi direction and a particular theta direction. The radiation pattern 112 can be formed to generate a beam of radiation. The beam can take, for example, the form of a pencil beam directed at a particular phi steering angle 118 and a particular theta steering angle 120. In this way, the artificial impedance surface antenna 110 can be electronically steered in two dimensions.

Depending on the implementation, the artificial impedance surface antenna 110 may be configured to emit linearly or circularly polarized radiation. That is, the artificial impedance surface antenna 110 can be used to generate a linearly or circularly polarized radiation pattern 112. Also, by adjusting the voltage applied to the plurality of tunable elements 1516, the radiation pattern 112 can be switched between linearly polarized waves and circularly polarized waves without changing the physical configuration of the artificial impedance surface antenna 110. be able to.

The impedance subpattern produced by the surface wave channels formed by the plurality of radiating spokes 1502 can be modulated to produce the entire linearly polarized radiation pattern 112. For example, the voltage applied to the tunable element at each corresponding portion of multiple radiating spokes 1502 can be set, so that the impedance subpatterns generated along the surface wave channels formed by each radiating spoke are as follows: Given in the formula.

In another example, the impedance subpattern of the surface wave channel formed by the plurality of radiation spokes 1502 can be modulated to produce the entire circularly polarized radiation pattern 112. Since the voltage applied to the tunable element of each corresponding part of the multiple radiated spokes 1502 can be set, the impedance subpattern generated along the surface wave channel formed by each radiated spoke is given by the following equation. Given.

Here, “+” of ± represents an impedance pattern that generates left circularly polarized waves, and “−” of ± represents an impedance pattern that generates right circularly polarized waves.

Equation (15) can be approximated as follows:
Z ＝ X ＋ Msin (γ ± φ) (19)

In another exemplary example, the impedance subpattern may be given by other types of expressions, including periodic functions. For example, the sine function sin (γ ± φ) in equation (19), the sine function sin (γ ± γ ₀ ) in equation (15), and the cosine function in equation (13).

Can be replaced with several other types of periodic functions, respectively.

Thus, the artificial impedance surface antenna 110 can be used to generate radiation of arbitrary polarization without the need to change the physical configuration of the artificial impedance surface antenna 110. The artificial impedance surface antenna 110 can be used to generate linearly or circularly polarized rays by varying the voltage applied to the tunable elements of the plurality of radiating spokes 1502.

Depending on the implementation, the artificial impedance surface antenna 110 can propagate surface waves towards or away from the center point 1508 of the dielectric substrate 1501. In some exemplary examples, the artificial impedance surface antenna 110 may include an absorbent material 1536 when the surface wave is propagated away from the center point 1508. Absorbent material 1536 can be placed on or around the edges of the dielectric substrate 1501. Absorbent material 1536 is configured to absorb excess energy from surface waves propagating radially outward from center point 1508 through multiple radiating spokes 1502.

In some exemplary examples, the dielectric substrate 1501 may be grounded using a grounding element 1538. Specifically, the grounding element 1538 can be arranged on the impedance surface of the dielectric substrate 1501.

The figure of the antenna system 100 of FIG. 1 does not imply any physical or structural limitation to the methods in which the exemplary embodiments can be implemented. Other components may be used in addition to or in place of those shown. Some components may be arbitrary. Blocks are also presented to illustrate some functional components. When implemented in an exemplary embodiment, one or more of these blocks may be combined, divided, or combined and then divided into different blocks.

In some exemplary examples, one of the plurality of tunable elements 1516 may be mounted as a pocket of variable material embedded in a dielectric substrate 1501. In another exemplary example, the tunable element of one of the plurality of tunable elements 1516 may be part of the corresponding impedance element of the plurality of impedance elements 1514. For example, a resonant structure with a tunable element can be used. The resonant structure may be, for example, a split ring resonator, an electrically connected resonator, or some other type of resonant structure, but is not limited thereto.

In another exemplary example, the center point 1508 may be the center point with multiple radiation spokes 1502 arranged around it, but it may not be the geometric center of the dielectric substrate 1501. For example, the center point 1508 may be offset from the geometric center of the dielectric substrate 1501.

In yet another exemplary example, each of the plurality of radiating spokes 1502 may have two independently controllable parts configured to form a surface wave channel. For example, the radiating spokes 1510 may have a first portion extending in one direction away from the center point 1508 and a second portion extending substantially in the opposite direction away from the center point 1508. These two parts may have the same or different design configurations, depending on the implementation. Further, in some cases, these two parts can be individually referred to as radiated spokes or radiated sub-spokes.

Next, with reference to FIG. 16, a diagram of an artificial impedance surface antenna is shown according to an exemplary embodiment. In this exemplary example, the artificial impedance surface antenna 1600 can be an embodiment for the artificial impedance surface antenna 110 having the radial configuration 1500 of FIG. The artificial impedance surface antenna 1600 has a radial configuration 1601 that can be an embodiment for the radial configuration 1500 of FIG.

As shown, the artificial impedance surface antenna 1600 includes a dielectric substrate 1602, a central surface wave feed 1604, and multiple radiating spokes 1606. The dielectric substrate 1602, the central surface wave feed 1604, and the plurality of radiating spokes 1606 can be used as examples of the dielectric substrate 1501, the plurality of surface wave feeds 1504, and the plurality of radiating spokes 1502, respectively, as shown in FIG. can.

In this exemplary example, the dielectric substrate 1602 has a circular shape with a center point 1605. The plurality of radiating spokes 1606 are arranged radially with respect to the center point 1605 so that the artificial impedance surface antenna 1600 is substantially radially symmetric. Radiation spokes 1608, radiation spokes 1610, radiation spokes 1612, and radiation spokes 1614 can be some examples of multiple radiation spokes 1606.

The plurality of radiating spokes 1606 are formed by an impedance element 1616 printed on a dielectric substrate 1602. The impedance element 1616 takes the form of a metal strip in this exemplary example. Also, the plurality of radiating spokes 1606 may include tunable elements (not shown in this figure) located between the impedance elements 1616.

The central surface wave feed 1604 can connect multiple radiating spokes 1606 to a transmission line (not shown in this figure). The transmission line may be configured to carry high frequencies to the central surface wave feed 1604 and / or from the central surface wave feed 1604.

The artificial impedance surface antenna 1600 can be electronically steered in theta and phi directions with the desired accuracy. Each of the multiple radiating spokes 1606 can be individually electronically steered in a particular theta direction and a wide phi direction to generate a fan beam. For example, radiated spokes 1608, radiated spokes 1612, and radiated spokes 1614 can be electronically steered to produce fan beam 1618, fan beam 1620, and fan beam 1622, respectively. The radiation patterns corresponding to the fan beam 1618, fan beam 1620, and fan beam 1622 can be overlapped to produce the pencil beam 1624. The pencil beam 1624 can be directed at a particular theta steering angle and a particular phi steering angle.

As shown, the absorbent material 1626 is located at and around the outer edge of the dielectric substrate 1602. The absorbent material 1626 can be an embodiment for the absorbent material 1536 of FIG. Absorbent material 1626 is configured to absorb excess energy due to surface waves propagating away from center point 1605.

Referring to FIG. 17, a cross-sectional side view of the artificial impedance surface antenna 1600 of FIG. 16 is shown according to an exemplary embodiment. In this exemplary example, a cross-sectional side view of the artificial impedance surface antenna 1600 of FIG. 16 is shown cut with respect to cutting lines 17-17 in FIG.

In this exemplary example, the grounding element 1700 can be seen along the surface of the dielectric substrate 1602. The grounding element 1700 can be an embodiment for the grounding element 1538 of FIG.

The transmission line 1702 is also shown in this figure. Transmission line 1702 can carry high frequencies to and from the central surface wave feed 1604, or both. In an exemplary example, the transmission line 1702 takes the form of a coaxial cable.

As shown, surface waves can propagate in the direction of arrow 1704, substantially parallel to the dielectric substrate 1602 and approximately perpendicular to the central axis 1706 passing through the center point 1605 of the dielectric substrate 1602. Multiple radiating spokes 1606 can be placed such that multiple radiating spokes 1606 (not shown in this figure) are substantially targeted with respect to the central axis 1706.

With reference to FIG. 18, diagrams of impedance patterns for the artificial impedance surface antenna 1600 of FIGS. 16 and 17 are shown according to exemplary embodiments. In this exemplary example, the artificial impedance surface antenna 1600 is linearly polarized to produce a radiation pattern with a theta steering angle of about 45 degrees and a main lobe directed to a phi steering angle of about 0 degrees. Impedance pattern 1800 can be generated when configured in.

Impedance pattern 1800 is shown for the first axis 1802 and the second axis 1804. The first axis 1802 and the second axis 1804 can represent two axes forming a plane substantially parallel to the dielectric substrate 1602 of FIG. Impedance pattern 1800 is composed of impedance subpatterns 1806 formed by the plurality of radiating spokes 1606 of FIG. Scale 1808 provides the correlation between the impedance subpattern 1806 and the impedance value. Impedance value is j

Can be a unit of j ohms equal to.

Next, with reference to FIG. 19, some figures of the artificial impedance surface antenna are shown according to an exemplary embodiment. In this exemplary example, the artificial impedance surface antenna 1900 can be another embodiment for the artificial impedance surface antenna 110 having the radial configuration 1500 of FIG. The artificial impedance surface antenna 1900 has a radial configuration 1901 that can be an embodiment for the radial configuration 1500 of FIG.

In this exemplary example, the artificial impedance surface antenna 1900 includes a dielectric substrate 1902, radiating spokes 1904, and a central surface wave feed 1906. Only a portion of the entire radiation spokes that form the artificial impedance surface antenna 1900 is shown in this figure.

Radiant spokes 1907 are an example of one of the radiant spokes 1904. Only part of the radiant spokes 1907 is shown. The radiating spokes 1907 are located in the corresponding portion 1908 of the dielectric substrate 1902. Radiant spokes 1907 include multiple metal strips 1909 and multiple varicaps 1910. The plurality of metal strips 1909 and the plurality of varicaps 1910 can be examples of the plurality of metal strips 1518 and the plurality of varicaps 1520 shown in FIG. 15, respectively.

As shown, a voltage can be applied to a plurality of metal strips 1909 and thereby a plurality of varicaps 1910 via conductive wires 1912 terminating at terminal 1914. Terminal 1914 can be connected to an electrical via (not shown in this figure), which passes through the thickness of the dielectric substrate 1902 and to control hardware such as a voltage controller. Passes a grounding element (not shown in this figure) to the connector that connects to.

Referring to FIG. 20, a cross-sectional side view of the artificial impedance surface antenna 1900 of FIG. 19 is shown according to an exemplary embodiment. In this exemplary example, the cross-sectional side view of the artificial impedance surface antenna 1900 of FIG. 19 is shown cut with respect to the cutting line 20-20 of FIG.

This exemplary example shows an electrical via 2000 that connects terminal 1914 in FIG. 19 to a voltage controller 2002. The voltage controller 2002 can vary the voltage applied to the metal strips of the plurality of radiating spokes 1904 in FIG.

An exemplary embodiment shows that different types of configurations for the artificial impedance surface antenna 110 in FIG. 1 may improve the efficiency of the artificial impedance surface antenna 110, thereby improving overall performance. Admit and consider. For example, an exemplary embodiment may optionally provide a square wave profile of surface impedance over each surface wave channel formed on each radiating element of the artificial impedance surface antenna 110 of FIG. I admit that there is and consider it.

An exemplary embodiment uses a switch element having only two possible states compared to a varicap that can be adjusted to have any different capacitance state over a range of capacitance values. By doing so, we acknowledge that it may be possible to achieve a square wave profile of surface impedance for surface wave channels. These switch elements can, for example, take the form of a PIN diode, but are not limited to this.

Referring to FIG. 21, the figure of the artificial impedance surface antenna 110 of FIG. 1 is shown in the form of a block diagram according to an exemplary embodiment. In this exemplary example, at least one surface wave channel on at least one radiating element of the artificial impedance surface antenna 110 of FIG. 21 can be implemented differently from the method described in FIG.

As shown, the surface wave channel 125 of FIG. 1 may not include the plurality of tunable elements 128 of FIG. On the contrary, in this exemplary example, the surface wave channel 125 includes a plurality of switch elements 2100 instead of the plurality of tunable elements 128 in FIG. Each of the plurality of switch elements 2100 can simply have two states 2102. The two states 2102 can include a first state 2104 and a second state 2106. In some cases, the first state 2104 can be called the on state and the second state 2106 can be called the off state.

In an exemplary example, the plurality of switch elements 2100 take the form of a plurality of PIN diodes 2108. In another exemplary example, the switch element of one of the multiple switch elements 2100 is selected from semiconductor switches, microelectromechanical system (MEMS) switches, high frequency diodes, Schottky diodes, and phase change material switches. May be good.

The switch element 2101 can be an example of one of a plurality of switch elements 2100. The switch element 2101 may be arranged in the gap between the first impedance element 2113 of the plurality of impedance elements 126 and the second impedance element 2115 of the plurality of impedance elements 126. Further, the switch element 2101 can electrically connect the first impedance element 2113 to the second impedance element 2115. The capacitance of the switch element 2101 and the capacitance of the gap between the first impedance element 2113 and the second impedance element 2115 are between the first impedance element 2113 and the second impedance element 2115. Contributes to the total capacitance of. In some cases, the capacitance of the gap between the first impedance element 2113 and the second impedance element 2115 can be ignored.

When the switch element 2101 takes the form of a PIN diode, the first state 2104 can take the form of an inductance state 2105 and the second state 2106 can take the form of a capacitance state 2107. By applying a first level voltage to the switch element 2101, the switch element 2101 can be placed in the inductance state 2105. By applying a second level voltage to the switch element 2101, the switch element 2101 can be placed in the capacitive state 2107.

Whether the switch element 2101 is in the inductance state 2105 or the capacitance state 2107 can be determined by the reactance of the switch element 2101. For example, the surface impedance associated with switch element 2101 can be defined as:
Z ＝ R ＋ jX (20)
Here, R is the real part of the resistance and surface impedance, and X is the imaginary part of the reactance and surface impedance. The resistance can also be called a surface resistance, and the reactance can also be called a surface reactance. If the reactance is positive, the reactance is described as inductive and the switch element 2101 can be thought of as an inductance state 2105. If the reactance is negative, the reactance is described as capacitive and the switch element 2101 can be considered as a capacitive state 2107. If the reactance is virtually zero, the surface impedance can be considered to be virtually completely resistant.

In the inductance state 2105, the switch element 2101 can have a substantially zero capacitance, but may have a parasitic inductance. That is, when the switch element 2101 is in the inductance state 2105, the capacitance of the switch element 2101 can be set to zero or can be ignored. Thus, in the inductance state 2105, the switch element 2101 can be modeled as a series resistor-inductor circuit. In the capacitance state 2107, the switch element 2101 can have some selected non-zero capacitance values. Thus, in the capacitance state 2107, the switch element 2101 can be modeled as a parallel resistor-capacitor circuit.

Since each of the plurality of switch elements 2100 can have only one of the two states 2102 at any given time in time, the voltage applied to the plurality of switch elements 2100 can be surfaced. It can be used to create a surface impedance profile 2114 for the wave channel 125. Specifically, one of the two levels of voltage can be applied to each of the plurality of switch elements 2100 to create the surface impedance profile 2114. The surface impedance profile 2114 can be created so that only a selected high surface impedance, a selected low surface impedance, or some combination of the two is formed.

For example, the voltage applied to the plurality of switch elements 2100 can be controlled so that the surface impedance profile 2114 takes the form of a square wave modulation 2110 with a high surface impedance and a low surface impedance. The square wave modulation 2110 can be a square wave type modulation. That is, in an exemplary example, the respective states of the plurality of switch elements 2100 may be controlled to modulate high and low surface impedances in the form of square waves as compared to sine waves. These two surface impedance levels are modulated on each surface wave channel of each radiating element of the artificial impedance surface antenna 110 to electronically steer the artificial impedance surface antenna 110 in theta direction, phi direction, or both. Can be done.

In an exemplary example, each of the plurality of impedance elements 126 can take the form of a rectangular metal strip. In some exemplary examples, each of the plurality of impedance elements 126 may have a shape with a repeating pattern 2112. The repeating pattern 2112 can be one pattern of shapes. For example, a particular impedance element in one of a plurality of impedance elements 126 has the same shape selected from a hexagonal shape, a diamond shape, or one of several other types of shapes. It can have a repeating pattern.

By using a plurality of switch elements 2100 for the surface wave channel 125, the gain of the artificial impedance surface antenna 110 can be improved. Also, by using a plurality of switch elements 2100, the artificial impedance surface antenna 110 may be able to operate at a frequency in the Ka band with a desired level of aperture ratio. In this way, power loss can be reduced by using a plurality of switch elements 2100. The Ka band can contain frequencies between about 26.5 GHz and about 40 GHz. As an exemplary example, the use of multiple PIN diodes 2108 may allow the artificial impedance surface antenna 110 to operate at frequencies of about 30 GHz with an aperture ratio higher than about 25%.

The figure of the artificial impedance surface antenna 110 in FIG. 21 does not imply any physical or structural limitation to the methods in which the exemplary embodiments can be implemented. Other components may be used in addition to or in place of those shown. Some components may be arbitrary. Blocks are also presented to illustrate some functional components. When implemented in an exemplary embodiment, one or more of these blocks may be combined, divided, or combined and then divided into different blocks.

Next, with reference to FIG. 22, a diagram of the radiating element is shown according to an exemplary embodiment. In this exemplary example, the radiating element 2200 can be an embodiment for the radiating element 123 of FIG.

As shown, the radiating element 2200 includes a dielectric substrate 2202. The surface wave channel 2204 is formed on the dielectric substrate 2202. The surface wave channel 2204 can be an embodiment for the surface wave channel 125 of FIG.

In this exemplary example, the surface wave channel 2204 comprises a plurality of impedance elements 2206 and a plurality of switch elements 2208. The plurality of switch elements 2208 can be an embodiment for the plurality of switch elements 2100 of FIG.

Each of the plurality of switch elements 2208 can have only one of the two states at any given time in time in this exemplary example. For example, when one of a plurality of switch elements 2208 is in the on state, the switch element can function like a circuit consisting of a resistor and an inductor in series. The on state corresponds to high surface impedance. The inductance provided can be important for the surface wave channel 2204 to allow the operation of an artificial surface impedance antenna that belongs within the Ka band of frequency. When the switch element is in the off state, the switch element can function like a circuit consisting of a resistor and a capacitor in parallel. The off state corresponds to low surface impedance.

Each state of the plurality of switch elements 2208 can be controlled to modulate between high and low surface impedances to create a surface impedance profile for the surface wave channel 2204. In this exemplary example, this surface impedance profile can resemble a square wave modulation. Part 2210 of surface wave channel 2204 is shown enlarged in FIG. 23 below.

Next, with reference to FIG. 23, an enlarged view of portion 2210 of surface wave channel 2204 of FIG. 22 is shown according to an exemplary embodiment. As shown in the figure, the plurality of impedance elements 2206 include an impedance element 2300 and an impedance element 2302. The impedance element 2300 and the impedance element 2302 can be examples for the first impedance element 2113 and the second impedance element 2115 in FIG. 21, respectively.

The plurality of switch elements 2208 includes a set of switch elements 2304 arranged in a gap between the impedance element 2300 and the impedance element 2302. Each of the set 2304 of switch elements has only two possible states and can be one of these two possible states at any given time in time. In an exemplary example, these two states can be an inductance state and a capacitance state.

As shown, the switch element set 2304 includes a switch element 2306, a switch element 2308, and a switch element 2310. The switch element 2306, the switch element 2308, and the switch element 2310 electrically connect the impedance element 2300 and the impedance element 2302.

Each of the plurality of impedance elements 2206 in FIG. 22 can have the shape of a repeating pattern. For example, the impedance element 2302 has a repeating pattern 2312. The repeating pattern 2312 is a series of the same shapes. In this exemplary example, the repeating pattern 2312 is a series of hexagonal shapes. As shown, the repeating pattern 2312 includes a hexagonal shape 2314, a hexagonal shape 2316, and a hexagonal shape 2318.

Next, with reference to FIG. 24, a diagram of another configuration of the radiating element is shown according to an exemplary embodiment. In this exemplary example, the radiating element 2400 can be an embodiment for the radiating element 123 of FIG.

As shown, the radiating element 2400 includes a dielectric substrate 2402. The surface wave channel 2404 is formed on the dielectric substrate 2402. The surface wave channel 2404 can be an embodiment for the surface wave channel 125 of FIG. The surface wave channel 2404 includes a plurality of impedance elements 2406 and a plurality of switch elements 2408.

The plurality of impedance elements 2406 can be an embodiment for the plurality of impedance elements 126 of FIG. In this exemplary example, each of the plurality of impedance elements 2406 can take the form of a rectangular metal strip.

The plurality of switch elements 2408 can be an embodiment for the plurality of switch elements 2100 of FIG. In this exemplary example, each of the plurality of switch elements 2408 can have only one of the two states at any given time in time. In an exemplary example, each of the plurality of switch elements 2408 may be implemented in the form of a PIN diode.

For example, when one of a plurality of switch elements 2408 is in the on state, the switch element can function like a circuit consisting of a resistor and an inductor in series. The on state corresponds to high surface impedance. The inductance provided can be important to allow operation within the Ka band of frequency. When the switch element is in the off state, the switch element can function like a circuit consisting of a resistor and a capacitor in parallel. The off state corresponds to low surface impedance.

The figures in FIGS. 22 to 24 do not imply physical or structural limitations to the methods in which exemplary embodiments can be implemented. Other components may be used in addition to or in place of those shown. Some components may be arbitrary.

The different components shown in FIGS. 22 to 24 can be exemplary examples of how the components shown in block form in FIGS. 1 and 2 can be implemented as physical structures. In addition, some of the components of FIGS. 22 to 24 may be combined with the components of FIGS. 1 and 2, used together with the components of FIGS. 1 and 2, or 2 thereof. It may be a combination of two.

Next, with reference to FIG. 25, a process for electronically manipulating the antenna system is shown in the form of a flow diagram according to an exemplary embodiment. The process shown in FIG. 25 can be implemented to electronically steer the antenna system 100 of FIG.

The process begins by propagating surface waves along each of the plurality of surface wave channels formed in each of the plurality of radiating elements in order to form a radiation pattern (operation 2500). Each surface wave channel of the plurality of surface wave channels formed in each radiation element of the plurality of radiation elements is a high frequency signal using the surface wave feed of one of the plurality of surface wave feeds associated with the plurality of radiation elements. Connected to a transmission line configured to carry (operation 2502).

The main lobe of the radiation pattern is then electronically steered in theta direction by controlling the voltage applied to the surface wave channels at each radiation element of the radiation element (operation 2504). In addition, the main lobe of the radiation pattern is electronically steered in the phi direction by controlling the relative phase difference between the plurality of surface wave feeds (operation 2506), after which the process ends.

Next, with reference to FIG. 26, a process for electronically manipulating the antenna system is shown in the form of a flow diagram according to an exemplary embodiment. The process shown in FIG. 26 can be implemented, for example, to electronically steer the artificial impedance surface antenna 110 having the radial configuration 1500 of FIG.

The process involves multiple surfaces formed by multiple radiating spokes on the antenna to generate multiple radiating subpatterns when multiple radiating spokes are arranged radially with respect to the center point of the dielectric substrate. It starts by propagating surface waves along the wave channel (operation 2600). The main lobe of the radiation pattern of the antenna is then electronically steered in two dimensions (operation 2602), after which the process ends.

Next, with reference to FIG. 27, a process for electronically manipulating the antenna system is shown in the form of a flow diagram according to an exemplary embodiment. The process shown in FIG. 27 can be realized, for example, to electronically steer the artificial impedance surface antenna 110 having the switch element as described in FIG.

The process begins by propagating surface waves along each of the plurality of surface wave channels formed in each of the plurality of radiating elements in order to form a radiation pattern (operation 2700). Next, each surface wave channel of the plurality of surface wave channels formed in each radiation element of the plurality of radiation elements uses the surface wave feed of one of the plurality of surface wave feeds associated with the plurality of radiation elements. , Can be connected to a transmission line configured to carry high frequency signals (operation 2702).

The main lobe of the radiation pattern can be electronically steered by controlling the voltage applied to multiple switch elements connecting multiple impedance elements in each of the multiple surface wave channels (Operation 2704). After that, the process ends.

Flow diagrams and block diagrams in different illustrated embodiments show the architecture, functionality, and operation of some possible implementations of the devices and methods in the exemplary embodiments. In this case, each block of the flow diagram or block diagram can represent a module, a segment, a function, and / or a part of an operation or a step.

In some alternative implementations of the exemplary embodiment, the functions, i.e., the functions shown in the block diagram, may occur out of the order shown in the drawings. For example, in some cases, two blocks shown in succession may be executed at substantially the same time, or the blocks may be executed in reverse order by the corresponding function. Also, other blocks may be added in addition to the blocks shown in the flow diagram or block diagram.

Further, the present disclosure includes embodiments according to the following provisions.
Item 1: A plurality of radiating elements in which each radiating element of a plurality of radiating elements includes a plurality of surface wave channels, and each surface wave channel of the plurality of surface wave channels is configured to limit the path of the surface wave. There are a plurality of radiating elements, including a plurality of switch elements and a plurality of impedance elements, and a surface wave feed of one of a plurality of surface wave feeds is a plurality of radiating elements of one of a plurality of radiating elements. A device with multiple surface wave feeds, configured to connect one of the surface wave channels of a surface wave channel to a transmission line configured to carry high frequency signals.
Item 2: The device according to item 1, wherein an artificial impedance surface antenna configured such that a plurality of radiating elements and a plurality of surface wave feeds are electronically steered in theta and phi directions.
Item 3: The device according to Item 2, wherein the artificial impedance surface antenna operates at a frequency between about 26.5 GHz and about 40 GHz.
Item 4: The device according to item 2, wherein the artificial impedance surface antenna has an aperture ratio higher than about 25% and operates at a frequency of about 30 GHz.
Item 5. Allowing multiple switch elements of each surface wave channel of multiple surface wave channels to create high surface impedance and low surface impedance surface impedance profiles for each surface wave channel, second. The device described in the section.
Item 6: The device according to item 5, wherein the surface impedance profile is square wave modulation.
Item 7. The device according to Item 5, wherein the high and low surface impedances are modulated to allow scanning in theta and phi directions.
Item 8. The apparatus according to Item 1, wherein each switch element of the plurality of switch elements is a PIN diode having an inductance state and a capacitance state.
Item 9. The device of item 1, wherein each switch element of the plurality of switch elements is simply a Schottky diode having two states.
Item 10. The apparatus according to Item 1, wherein each switch element of the plurality of switch elements is simply a semiconductor switch having two states.
Item 12. The device of item 1, wherein each switch element of the plurality of switch elements is simply a microelectromechanical system switch diode having two states.
Item 12. The device of item 1, wherein each switch element of the plurality of switch elements is simply a phase change material switch having two states.
Item 13. The device of item 1, wherein each switch element of the plurality of switch elements is simply a high frequency diode having two states.
Item 14: Impedance element of one of multiple impedance elements is a metal strip, a patch of conductive paint, a metal mesh material, a metal film, a deposit of a metal substrate, a resonance structure, a split ring resonator, electrically. The device according to paragraph 1, which is selected from a connected resonator and one of a structure consisting of one or more metal materials.
Item 15. The apparatus according to item 1, wherein one of a plurality of impedance elements has a pattern formed by a series of the same shapes.
Item 16. The device of item 15, wherein the same shape is selected from either a diamond-shaped shape or a hexagonal shape.
Item 17. Each radiating element of the plurality of radiating elements comprises a plurality of surface wave channels configured such that each surface wave channel of the plurality of surface wave channels restricts the path of the surface wave, and also includes a dielectric substrate. A plurality of impedance elements arranged on the surface of a dielectric substrate, and a plurality of switch elements arranged on the surface of a dielectric substrate in which each switch element of the plurality of switch elements has a first state and a second state. An artificial impedance surface antenna comprising a plurality of radiating elements and a plurality of surface wave feeds configured to connect multiple surface wave channels of each radiating element of the plurality of radiating elements to a plurality of transmission lines.
Section 18: A method for electronically manipulating an antenna system, in which each of the multiple surface wave channels formed on each of the multiple radiating elements to form a radiation pattern. A step of propagating a surface wave along a surface wave channel and a surface wave channel of a plurality of surface wave channels formed in each radiation element of a plurality of radiation elements, and a plurality of surface wave feeds related to the plurality of radiation elements. A step of connecting to a transmission line configured to carry a high frequency signal using one of the surface wave feeds, and a plurality of connecting multiple impedance elements of each surface wave channel of multiple surface wave channels. It includes a step of electronically manipulating the main lobe of the radiation pattern by controlling the voltage applied to the switch element.
Section 19: The step of electronically manipulating the main lobe applies a first level voltage or a second level voltage to create a surface impedance profile for each surface wave channel of multiple surface wave channels. The method of paragraph 18, comprising applying to each switch element of a plurality of switch elements.
Item 20: A first level voltage or a second level voltage of multiple switch elements so that the step of electronically manipulating the main lobe modulates between high and low surface impedances. 18. The method of paragraph 18, comprising applying to each switch element.

The description of another exemplary embodiment is presented for purposes of illustration and description and is not intended to cover or limit the embodiments in the disclosed embodiments. Many modifications and variations will be apparent to those skilled in the art. Also, another exemplary embodiment can provide different characteristics as compared to other desirable embodiments. The embodiments or selected embodiments are selected and described in order to best explain the intent and practical use of the embodiments so that those skilled in the art will be suitable for the particular application considered. The present disclosure for various embodiments with various modifications can be understood.

100 antenna system
102 antenna
104 Voltage controller
106 Phase shifter
108 High frequency module
110 Artificial impedance surface antenna
112 Radiation pattern
114 Desired direction
116 main robe
118 Phi steering angle
120 Theta steering angle
122 Radiant element array
123 Radiant element
124 Dielectric substrate
125 Surface wave channel
126 Multiple impedance elements
128 Multiple tunable elements
130 Multiple surface wave feeds
132 Multiple metal strips
134 Multiple varicaps
136 Selected design configuration
138 Impedance element width
140 Impedance element spacing
142 Tunerable element spacing
144 Board thickness
145 Second surface wave channel
146 Multiple voltage sources
148 Multiple grounds
150 Multiple voltage lines
151 controller
152 Surface wave
154 High frequency signal
156 Multiple transmission lines
158 Send / Receive Module
200 antenna system
201 Tunerable Artificial Impedance Surface Antenna
202 voltage controller
203 Phase shifter
204 Control bus
205 Control bus
206 Dielectric Substrate
207 metal strip
208 Surface wave feed
209 Varicap
210 Send / Receive Module
211 High frequency transmission line
212 Power distributor
213 Phase shifter
214 Digital / Analog Converter
216 Voltage control line
217 Digital / analog converter
218 Voltage control line
219 Voltage control line
220 grounding
300 Tread
400 antenna system
401 Tunerable Artificial Impedance Surface Antenna
402 Voltage controller
403 phase shifter
406 Dielectric Substrate
407 Metal strip
408 High Frequency Surface Wave Feed
409 Varicap
410 Transmit / receive module
411 voltage line
412 Digital / Analog Converter
414 controller
500 antenna system
501 Tunerable Artificial Impedance Surface Antenna
502 voltage controller
503 phase shifter
506 Dielectric substrate
507 metal strip
508 High frequency surface wave feed
509 Varicap
510 transmit / receive module
512 variable voltage source
514 Voltage control line
516 Voltage control line
518 cycle
601 Dielectric substrate
602 metal strip
603 Tread
700 Inactive substrate
702 variable material
800 antenna system
802 antenna
803 Voltage controller
804 Phase shifter
806 High frequency module
808 Digital / Analog Converter
810 controller
811 voltage line
812 Radiation structure
813 Radiant element array
814 Radiant element
815 Radiant element
816 Radiant element
818 Radiant element
820 Radiant element
822 Radiant element
824 Radiant element
826 Radiant element
827 Dielectric board
828 Multiple metal strips
830 Multiple varicaps
831 Surface wave channel
832 Surface wave feed
834 Phase shift device
900 antenna system
902 antenna
903 Voltage controller
904 Phase shifter
906 High frequency module
908 Variable voltage source
911 voltage line
912 Radiating element
913 Voltage line
914 Radiating element
915 Radiating element array
916 Radiating element
918 Radiant element
920 Radiating element
922 Radiating element
924 Radiating element
926 Radiant element
927 Dielectric board
928 First multiple metal strips
930 Second multiple metal strips
931 Surface wave channel
932 Multiple varicaps
933 Surface wave feed
936 Phase shift device
938 Transmission line
1000 voltage controller
1002 grounding
1004 Digital / Analog Converter
1006 voltage line
1008 voltage line
1010 controller
1012 transmission line
1100 phase shifter
1102 waveguide
1104 waveguide
1106 waveguide
1108 waveguide
1110 waveguide
1112 waveguide
1114 waveguide
1118 controller
1120 digital / analog converter
1121 grounding
1122 voltage line
1123 controller
1124 transmission line
1200 antenna system
1201 Radiating element
1202 high frequency assembly
1203 high frequency module
1204 phase shift device
1205 Dielectric board
1206 transmission line
1208 transmission line
1210 Surface wave feed
1211 Surface wave feed
1212 Surface wave channel
1213 Surface wave channel
1214 Multiple metal strips
1215 Multiple varicaps
1216 X axis
1218 voltage line
1220 pin
1224 Multiple metal strips
1226 Multiple varicaps
1228 voltage line
1230 pin
1300 end
1301 high frequency assembly
1302 high frequency module
1303 end
1304 phase shift device
1306 transmission line
1308 transmission line
1310 Surface wave feed
1312 Surface wave feed
1400 antenna system
1401 antenna
1402 phase shifter
1404 high frequency module
1406 Array of radiating elements
1407 Surface wave feed
1408 Radiant element
1410 Radiant element
1412 Radiant element
1414 Radiant element
1416 Radiant element
1418 Radiant element
1420 Radiant element
1424 Phase shift device
1426 Transmission line
1500 radial composition
1501 Dielectric substrate
1502 Multiple radiating spokes
1504 Multiple surface wave feeds
1506 circular
1508 center point
1510 radiant spokes
1512 Surface wave channel
1513 surface
1514 Multiple impedance elements
1515 Corresponding part
1516 Multiple tunable elements
1518 Multiple metal strips
1520 Multiple varicaps
1522 Selected design configuration
1524 Impedance element width
1526 Impedance element spacing
1528 Tunerable element spacing
1530 Substrate thickness
1532 Multiple high frequency signals
1533 Multiple radiation subpatterns
1534 Radiation subpattern
1536 Absorbent material
1538 Grounding element
1600 Artificial impedance surface antenna
1601 radial composition
1602 Dielectric substrate
1604 Central surface wave feed
1605 Center point
1606 radiant spokes
1608 radiant spokes
1610 Radiant spokes
1612 Radiant spokes
1614 Radiant spokes
1616 Impedance element
1618 fan beam
1620 fan beam
1622 fan beam
1624 pencil beam
1626 Absorbent material
1700 Grounding element
1702 transmission line
1704 arrow
1706 central axis
1800 impedance pattern
1802 First axis
1804 Second axis
1806 Impedance subpattern
1808 scale
1900 Artificial impedance surface antenna
1901 Radial composition
1902 Dielectric substrate
1904 radiant spokes
1906 Central surface wave feed
1907 radiant spokes
1908 Corresponding part
1909 Multiple metal strips
1910 Multiple varicaps
1912 Conductive wire
1914 terminal
2000 electric via
2002 voltage controller
2100 Multiple switch elements
2101 Switch element
2102 Two states
2104 First state
2105 Inductance state
2106 Second state
2107 Capacitance state
2108 Multiple PIN diodes
2110 Square wave modulation
2112 Repeat pattern
2113 First impedance element
2114 Surface impedance profile
2115 Second impedance element
2200 Radiant element
2202 Dielectric substrate
2204 Surface wave channel
2206 Multiple impedance elements
2208 Multiple switch elements
2210 Corresponding part
2300 impedance element
2302 Impedance element
2304 Switch element set
2306 Switch element
2308 Switch element
2310 Switch element
2312 Repeat pattern
2314 Hexagonal shape
2316 Hexagonal shape
2318 Hexagonal shape
2400 Radiant element
2402 Dielectric substrate
2404 Surface wave channel
2406 Multiple impedance elements
2408 Multiple switch elements

Claims (10)

Each radiating element (123) of the plurality of radiating elements comprises a plurality of surface wave channels, and each surface wave channel (125) of the plurality of surface wave channels is configured to limit the path of the surface wave. It ’s a radiant element,
Includes multiple switch elements (2100) and multiple impedance elements (126),
With multiple radiating elements
The surface wave feed of one of the plurality of surface wave feeds (130) is the surface wave channel (125) of the plurality of surface wave channels of the plurality of surface wave channels of the radiation element (123) of the plurality of radiation elements. ) With multiple surface wave feeds (130) configured to connect to transmission lines configured to carry the high frequency signal (154).
Equipped with
The plurality of switch elements (2100) have only an on state and an off state, and the plurality of switch elements (2100) have only an on state and an off state.
When the plurality of switch elements (2100) are in the ON state, the plurality of switch elements (2100) act as an RL series circuit at the operating frequency, corresponding to the high surface impedance of each surface wave channel (125).
When the plurality of switch elements (2100) are in the off state, the plurality of switch elements (2100) act as an RC parallel circuit at the operating frequency, corresponding to the low surface impedance of each surface wave channel (125).
The plurality of switch elements (2100) are configured to change the capacitance coupling between the impedance elements.
The plurality of impedance elements (126) of each radiating element (123) are arranged so that the distance between the adjacent impedance elements (126) is the smallest at the position where the switch element (2100) is arranged. ,
Device. Claim 1 wherein the plurality of radiating elements and the plurality of surface wave feeds (130) form an artificial impedance surface antenna (110) configured to be electronically steered in theta and phi directions. The device described. The plurality of switch elements (2100) of each surface wave channel (125) of the plurality of surface wave channels have a high surface impedance and a low surface impedance surface impedance profile (2114) for each surface wave channel (125). The device according to claim 2, which makes it possible to create. The apparatus according to claim 1 or 2, wherein each switch element (2101) of the plurality of switch elements (2100) is a PIN diode having an inductance state (2105) and a capacitance state (2107). Claimed that each switch element (2101) of the plurality of switch elements (2100) is simply a Schottky diode, a semiconductor switch, a microelectromechanical system switch diode, or a phase change material switch having two states (2102). The device according to item 1, 2 or 4. The device of claim 1, 2, 4 or 5, wherein each switch element (2101) of the plurality of switch elements (2100) is simply a high frequency diode having two states (2102). The apparatus according to claim 1, 2, 4, 5 or 6, wherein one of the plurality of impedance elements (126) has a pattern formed by a series of the same shapes. A method for electronically manipulating the antenna system (100), wherein the method is:
A step (2700) of propagating a surface wave along each surface wave channel of a plurality of surface wave channels formed in each radiation element of the plurality of radiation elements to form a radiation pattern (112).
Each surface wave channel (125) of the plurality of surface wave channels formed in each radiation element (123) of the plurality of radiation elements is set to a plurality of surface wave feeds (130) related to the plurality of radiation elements. Steps (2702) to connect to a transmission line configured to carry a high frequency signal (154) using one surface wave feed of
The radiation pattern (112) by controlling the voltage applied to the plurality of switch elements (2100) connected to the plurality of impedance elements (126) of each surface wave channel (125) of the plurality of surface wave channels. Step (2704) to electronically steer the main robe (116) of
Including
The plurality of switch elements (2100) have only an on state and an off state, and the plurality of switch elements (2100) have only an on state and an off state.
When the plurality of switch elements (2100) are in the ON state, the plurality of switch elements (2100) act as an RL series circuit at the operating frequency, corresponding to the high surface impedance of each surface wave channel (125).
When the plurality of switch elements (2100) are in the off state, the plurality of switch elements (2100) act as an RC parallel circuit at the operating frequency, corresponding to the low surface impedance of each surface wave channel (125).
The plurality of switch elements (2100) are configured to change the capacitance coupling between the impedance elements.
The plurality of impedance elements (126) of each radiating element (123) are arranged so that the distance between the adjacent impedance elements (126) is the smallest at the position where the switch element (2100) is arranged. ,
Method. The step of electronically manipulating the main lobe (116)
To create a surface impedance profile (2114) for each surface wave channel (125) of the plurality of surface wave channels, a first level voltage or a second level voltage is applied to the plurality of switch elements (2100). 8. The method of claim 8, comprising applying to each switch element of. The step of electronically manipulating the main lobe (116)
A claim comprising the step of applying a first level voltage or a second level voltage to each switch element of the plurality of switch elements (2100) so as to modulate between a high surface impedance and a low surface impedance. The method described in 8 or 9.

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