JPS624011B2 - - Google Patents
Info
- Publication number
- JPS624011B2 JPS624011B2 JP17820780A JP17820780A JPS624011B2 JP S624011 B2 JPS624011 B2 JP S624011B2 JP 17820780 A JP17820780 A JP 17820780A JP 17820780 A JP17820780 A JP 17820780A JP S624011 B2 JPS624011 B2 JP S624011B2
- Authority
- JP
- Japan
- Prior art keywords
- resonant
- signal
- signal path
- bridge
- tuning device
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
Links
- 230000037431 insertion Effects 0.000 description 8
- 238000003780 insertion Methods 0.000 description 8
- 230000008878 coupling Effects 0.000 description 6
- 238000010168 coupling process Methods 0.000 description 6
- 238000005859 coupling reaction Methods 0.000 description 6
- 239000003990 capacitor Substances 0.000 description 5
- 238000010586 diagram Methods 0.000 description 2
- 238000010521 absorption reaction Methods 0.000 description 1
- 238000006243 chemical reaction Methods 0.000 description 1
- 230000008054 signal transmission Effects 0.000 description 1
- 238000001228 spectrum Methods 0.000 description 1
- 238000010408 sweeping Methods 0.000 description 1
Classifications
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03J—TUNING RESONANT CIRCUITS; SELECTING RESONANT CIRCUITS
- H03J3/00—Continuous tuning
- H03J3/02—Details
- H03J3/16—Tuning without displacement of reactive element, e.g. by varying permeability
-
- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/20—Frequency-selective devices, e.g. filters
- H01P1/215—Frequency-selective devices, e.g. filters using ferromagnetic material
- H01P1/218—Frequency-selective devices, e.g. filters using ferromagnetic material the ferromagnetic material acting as a frequency selective coupling element, e.g. YIG-filters
-
- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03J—TUNING RESONANT CIRCUITS; SELECTING RESONANT CIRCUITS
- H03J3/00—Continuous tuning
- H03J3/02—Details
- H03J3/16—Tuning without displacement of reactive element, e.g. by varying permeability
- H03J3/18—Tuning without displacement of reactive element, e.g. by varying permeability by discharge tube or semiconductor device simulating variable reactance
- H03J3/185—Tuning without displacement of reactive element, e.g. by varying permeability by discharge tube or semiconductor device simulating variable reactance with varactors, i.e. voltage variable reactive diodes
Description
【発明の詳細な説明】
この発明は例えばスペクトラムアナライザ等の
同調装置として用いられる可変同調装置に関し、
特に広い周波数範囲にわたつて挿入損失が平坦な
特性を持つ可変同調装置を得ようとするものであ
る。DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a variable tuning device used as a tuning device for, for example, a spectrum analyzer.
In particular, the object is to obtain a variable tuning device that has characteristics with flat insertion loss over a wide frequency range.
主に500MHz以上の周波数領域において同調周
波数をスイープさせるような場合はYIG球とも呼
ばれる磁気共鳴素子を用いた可変同調装置が用い
られる。 A variable tuning device using a magnetic resonance element, also called a YIG sphere, is used mainly when sweeping the tuning frequency in a frequency range of 500 MHz or higher.
この発明は磁気共鳴素子を用いた可変同調装置
を使用することができない低周波域での使用に適
した可変同調装置を提案するものである。 The present invention proposes a variable tuning device suitable for use in a low frequency range where a variable tuning device using a magnetic resonance element cannot be used.
従来このような目的で使用される可変同調装置
はインダクタンスＬとコンデンサＣから成る同調
回路が用いられているが、LC同調回路は信号伝
送路に磁気結合回路及び共振回路が存在するた
め、磁気結合回路の結合度及び共振回路のＱの影
響を大きく受け、周波数によつて挿入損失が変化
する欠点がある。従つて広い周波数範囲にわたつ
て一度に同調周波数を変化させることができない
不都合が生じる。 Conventionally, the variable tuning device used for this purpose uses a tuning circuit consisting of an inductance L and a capacitor C, but since the LC tuning circuit has a magnetic coupling circuit and a resonant circuit in the signal transmission path, magnetic coupling is not possible. It has the disadvantage that it is greatly affected by the degree of coupling of the circuit and the Q of the resonant circuit, and the insertion loss changes depending on the frequency. Therefore, there arises the disadvantage that the tuning frequency cannot be changed at once over a wide frequency range.
この発明の目的は広い周波数範囲にわたつて挿
入損失が平坦な特性を持つ可変同調装置を提供す
るにある。 An object of the present invention is to provide a variable tuning device that has flat insertion loss characteristics over a wide frequency range.
以下にこの発明の一実施例を図面を用いて詳細
に説明する。 An embodiment of the present invention will be described in detail below with reference to the drawings.
第１図はこの発明の一実施例を示す。図中１は
入力端子であり、この入力端子１に特性インピー
ダンスZ0の信号路２の一端が接続される。信号路
２の他端側にブリツジ３が接続される。ブリツジ
３は一端が信号路２に共通接続された二つの抵抗
器４及び５と、この抵抗器４及び５の他端側に一
端がそれぞれ接続され信号路２と同一の特性イン
ピーダンスを持ち他端側に抵抗器６及び７が接続
されて無反射終端とされた一対の信号路８及び９
とにより構成される。抵抗器４，５及び６，７は
それぞれ等しい抵抗値R0とされる。またこの抵
抗値R0は信号路２及び８，９の特性インピーダ
ンスZ0に対しZ0＝R0の関係に選定される。 FIG. 1 shows an embodiment of the invention. In the figure, 1 is an input terminal, and one end of a signal path 2 having a characteristic impedance Z 0 is connected to this input terminal 1. A bridge 3 is connected to the other end of the signal path 2 . The bridge 3 has two resistors 4 and 5, one end of which is commonly connected to the signal path 2, and one end of which is connected to the other end of the resistors 4 and 5, each having the same characteristic impedance as the signal path 2. a pair of signal paths 8 and 9 with resistors 6 and 7 connected to the sides for reflection-free termination;
It is composed of Resistors 4, 5 and 6, 7 have the same resistance value R0 . Further, this resistance value R 0 is selected to have a relationship of Z 0 =R 0 with respect to the characteristic impedance Z 0 of the signal paths 2, 8, and 9.
このように選定することにより抵抗器４と５の
共通接続点Ａから各抵抗器４と５を見た抵抗値は
2R0となる。よつてその2R0の２辺が並列接続さ
れているからＡ点からブリツジ３の全体を見た抵
抗値はR0となり信号路２の特性インピーダンス
とマツチングがとられる。 By selecting in this way, the resistance value when looking at each resistor 4 and 5 from the common connection point A of resistors 4 and 5 is
2R becomes 0 . Therefore, since the two sides of 2R0 are connected in parallel, the resistance value when looking at the entire bridge 3 from point A becomes R0 , which matches the characteristic impedance of the signal path 2.
ブリツジ３の各一辺を構成する信号路８又は９
の何れか一方、この例では信号路８に共振素子１
１を結合する。この結合のために信号路８上に抵
抗器６の抵抗値R0に比べて充分無視できる程小
さいインダクタンスを持つコイル１２を直列に挿
入し、このコイル１２と共振素子１１を磁気的に
結合させる。共振素子１１はこの例ではコイルと
可変コンデンサとから成る並列共振回路を用いた
場合を示す。可変コンデンサは例えば可変容量ダ
イオード等を用いることができ、直流の制御信号
によつてその共振周波数が掃引されるように構成
されるものとする。 Signal path 8 or 9 forming each side of bridge 3
In this example, the resonant element 1 is connected to the signal path 8.
Combine 1. For this coupling, a coil 12 having an inductance sufficiently small to be ignored compared to the resistance value R 0 of the resistor 6 is inserted in series on the signal path 8, and this coil 12 and the resonant element 11 are magnetically coupled. . In this example, the resonant element 11 uses a parallel resonant circuit consisting of a coil and a variable capacitor. The variable capacitor can be, for example, a variable capacitance diode, and is configured so that its resonant frequency can be swept by a DC control signal.
ブリツジ３の抵抗器４及び５と信号路８及び９
の各接続点ＢとＣ間には平衡−不平衡変換トラン
ス、いわゆるバルーントランス１３の一次コイル
を接続し、二次コイルから出力端子１４を導出す
る。 Resistors 4 and 5 of bridge 3 and signal paths 8 and 9
A primary coil of a balanced-unbalanced conversion transformer, so-called balloon transformer 13, is connected between each connection point B and C, and an output terminal 14 is led out from the secondary coil.
上述の構成によれば共振素子１１の共振周波数
以外の周波数の信号に対してはＡ点からＢ及びＣ
点を見たインピーダンスは2R0となりブリツジ３
は平衡状態となる。よつてバルーントランス１３
の一次コイルには電流が流れることがなく、よつ
て出力端子１４には何等信号が出力されることは
ない。 According to the above configuration, for signals of frequencies other than the resonant frequency of the resonant element 11, from point A to B and C
The impedance when looking at the point is 2R 0 and bridge 3
is in equilibrium. Yotsutte Balloon Trance 13
No current flows through the primary coil, so no signal is output to the output terminal 14.
一方共振素子１１の共振周波数と同一の周波数
を持つ信号に対してはＡ点からＢ及びＣ点を見た
インピーダンスは共振素子１１の共振によりＢ点
側のインピーダンスが小さくなる。よつてブリツ
ジ３は不平衡状態となり出力端子１４に入力信号
が出力される。 On the other hand, for a signal having the same frequency as the resonant frequency of the resonant element 11, the impedance viewed from the point A to the points B and C becomes smaller on the B point side due to the resonance of the resonant element 11. Therefore, the bridge 3 is in an unbalanced state and the input signal is outputted to the output terminal 14.
ここでこの可変同調装置によれば入力端子１と
出力端子１４間の挿入損失は共振素子１１のエネ
ルギ吸収率で決定される。つまり共振素子１１が
信号路８を流れる信号のエネルギを吸収すると、
その吸収したエネルギの全部が反射されてＢ点に
戻され出力端子１４に取出される。つまり例えば
共振素子１１の共振インピーダンスが終端抵抗器
６の抵抗値R0に対し１／１００のインピーダンスになつ
たとすると終端抵抗器６には入力信号の１／１００のエ
ネルギが供給される。よつて共振素子１１の吸収
エネルギは１−１／１００＝0.99となる。よつて入力信
号はその99％が反射され出力端子１４に出力され
る。一方共振素子１１の共振インピーダンスが終
端抵抗R0に対し１／１０程度となつても共振素子１１
の吸収エネルギは１−１／１０＝0.9となり、入力信号
の90％は出力端子１４に出力される。 According to this variable tuning device, the insertion loss between the input terminal 1 and the output terminal 14 is determined by the energy absorption rate of the resonant element 11. In other words, when the resonant element 11 absorbs the energy of the signal flowing through the signal path 8,
All of the absorbed energy is reflected back to point B and taken out to the output terminal 14. That is, for example, if the resonant impedance of the resonant element 11 becomes 1/100 of the resistance value R 0 of the terminating resistor 6, the terminating resistor 6 is supplied with 1/100 of the energy of the input signal. Therefore, the absorbed energy of the resonant element 11 is 1-1/100=0.99. Therefore, 99% of the input signal is reflected and output to the output terminal 14. On the other hand, even if the resonant impedance of the resonant element 11 is about 1/10 of the terminal resistance R 0 , the absorbed energy of the resonant element 11 is 1-1/10 = 0.9, and 90% of the input signal is output to the output terminal 14. Ru.
結局この発明によれば共振素子１１の共振強度
に強弱があつても反射エネルギに大きく差が発生
しないため広帯域にわたつて平坦な挿入損失を得
ることができる。然も反射エネルギに比例して出
力が得られるものであるから挿入損失を小さくす
ることができる。 After all, according to the present invention, even if the resonance intensity of the resonant element 11 is strong or weak, a large difference does not occur in the reflected energy, so that a flat insertion loss can be obtained over a wide band. Moreover, since the output can be obtained in proportion to the reflected energy, the insertion loss can be reduced.
第２図及び第３図はこの発明の他の実施例を示
す。第２図の例では信号路８に直接小さい容量値
を持つ結合コンデンサ１５を通して直列共振回路
にエネルギを吸収するようにした場合を示す。こ
のように構成した場合には第１図の場合より高い
周波数の同調装置に適用して好適である。 FIGS. 2 and 3 show other embodiments of the invention. The example shown in FIG. 2 shows a case where energy is absorbed into a series resonant circuit through a coupling capacitor 15 having a small capacitance value directly in the signal path 8. This configuration is suitable for application to a higher frequency tuning device than the case of FIG. 1.
第３図は更に高い周波数の同調装置に適用して
好適な実施例を示す。この例では結合コンデンサ
１５を介してλ／４型線路１６を結合させ、このλ／４
型
線路１６を利用して共振回路を構成した場合を示
す。 FIG. 3 shows a preferred embodiment for application to a higher frequency tuning device. In this example, a λ/4 type line 16 is coupled via a coupling capacitor 15, and this λ/4
A case is shown in which a resonant circuit is constructed using the molded line 16.
以上説明したようにこの発明によれば共振回路
に吸収されるエネルギに比例した大きさの出力を
得ることができるため挿入損失が小さく、然も広
帯域にわたつて挿入損失が平坦な特性を持つ可変
同調装置を得ることができる。 As explained above, according to the present invention, it is possible to obtain an output proportional to the energy absorbed by the resonant circuit, so the insertion loss is small, and the insertion loss is variable over a wide band with flat characteristics. A tuning device can be obtained.
第１図はこの発明の一実施例を示す接続図、第
２図及び第３図はこの発明の他の実施例を示す接
続図である。
１…入力端子、２…信号路、３…ブリツジ、
４，５…一端が共通接続された２つの抵抗器、
６，７…終端抵抗器、８，９…一対の信号路、１
１…共振素子、１４…出力端子。
FIG. 1 is a connection diagram showing one embodiment of this invention, and FIGS. 2 and 3 are connection diagrams showing other embodiments of this invention. 1...Input terminal, 2...Signal path, 3...Bridge,
4, 5... Two resistors with one end commonly connected,
6, 7... Termination resistor, 8, 9... Pair of signal paths, 1
1... Resonant element, 14... Output terminal.
Claims (1)
抵抗器の他端側にそれぞれ接続されその各一端が
無反射終端とされた一対の信号路によつてブリツ
ジを構成し、そのブリツジの上記信号路の一方に
共振素子を結合させると共に上記抵抗器と信号路
の各接続点間にトランスを接続し、上記抵抗器の
共通接続点から入力端子を導出し、上記トランス
の二次コイルから出力端子を導出して成る可変同
調装置。1 A bridge is constituted by two resistors whose one ends are connected in common, and a pair of signal paths each connected to the other end of the resistor and each end of which is terminated with no reflection, and the bridge's A resonant element is coupled to one side of the signal path, and a transformer is connected between each connection point of the resistor and the signal path, an input terminal is derived from the common connection point of the resistor, and an output is output from the secondary coil of the transformer. A variable tuning device consisting of lead-out terminals.
Priority Applications (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP17820780A JPS57101416A (en) | 1980-12-17 | 1980-12-17 | Variable tuner |
| US06/327,473 US4460879A (en) | 1980-12-12 | 1981-12-04 | Variable tuning device |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP17820780A JPS57101416A (en) | 1980-12-17 | 1980-12-17 | Variable tuner |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS57101416A JPS57101416A (en) | 1982-06-24 |
| JPS624011B2 true JPS624011B2 (en) | 1987-01-28 |
Family
ID=16044446
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP17820780A Granted JPS57101416A (en) | 1980-12-12 | 1980-12-17 | Variable tuner |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS57101416A (en) |
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6438602U (en) * | 1987-09-02 | 1989-03-08 | ||
| JPH0257510U (en) * | 1988-10-19 | 1990-04-25 | ||
| JPH06235821A (en) * | 1993-02-09 | 1994-08-23 | Ina Koki Seisakusho:Kk | Optical fiber ring illuminator |
-
1980
- 1980-12-17 JP JP17820780A patent/JPS57101416A/en active Granted
Cited By (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| JPS6438602U (en) * | 1987-09-02 | 1989-03-08 | ||
| JPH0257510U (en) * | 1988-10-19 | 1990-04-25 | ||
| JPH06235821A (en) * | 1993-02-09 | 1994-08-23 | Ina Koki Seisakusho:Kk | Optical fiber ring illuminator |
Also Published As
| Publication number | Publication date |
|---|---|
| JPS57101416A (en) | 1982-06-24 |
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