JPS6255394B2 - - Google Patents
Info
- Publication number
- JPS6255394B2 JPS6255394B2 JP55060315A JP6031580A JPS6255394B2 JP S6255394 B2 JPS6255394 B2 JP S6255394B2 JP 55060315 A JP55060315 A JP 55060315A JP 6031580 A JP6031580 A JP 6031580A JP S6255394 B2 JPS6255394 B2 JP S6255394B2
- Authority
- JP
- Japan
- Prior art keywords
- output
- current
- reference signal
- level
- value setting
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired
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Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
- H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
- H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
- H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/145—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means
- H02M7/155—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a thyratron or thyristor type requiring extinguishing means using semiconductor devices only
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Rectifiers (AREA)
- Control Of Voltage And Current In General (AREA)
Description
【発明の詳細な説明】
〔産業上の利用分野〕
この発明は、プラズマアーク溶接、溶断用直流
電源などを構成するサイリスタ整流器の直流出力
電流を帰還制御するサイリスタ整流器の制御方法
に関する。DETAILED DESCRIPTION OF THE INVENTION [Industrial Application Field] The present invention relates to a method for controlling a thyristor rectifier that performs feedback control of the DC output current of a thyristor rectifier constituting a DC power source for plasma arc welding, fusing, and the like.
従来、プラズマアーク溶接、溶断用直流電源
は、出力電流特性が定電流特性であるものを使用
するのが良いとされ、そのため、一般に、サイリ
スタを用いたサイリスタ整流器によつて構成され
ている。
Conventionally, it has been said that it is best to use a DC power supply for plasma arc welding and fusing that has a constant current output characteristic, and for this reason, it is generally configured with a thyristor rectifier using a thyristor.
ところで、大電流によるトーチや被加工物の破
損を防止するため、プラズマ用電源の場合、起動
時の出力電流は、ソフトスタート特性の制御にも
とづき、徐々に定常値に増加させることが望まれ
る。 By the way, in order to prevent damage to the torch and workpiece due to large current, in the case of a plasma power supply, it is desirable that the output current at startup be gradually increased to a steady value based on control of the soft start characteristic.
また、プラズマ用直流電源は、連続使用される
ことが多く、しかも、大きい設備の治具を使用し
ているので、変動した出力電流を設定値に再調整
して戻すことが容易でないため、いわゆるフイー
ドバツク制御により、常時、出力電流を高い精度
で制御する必要がある。 In addition, since DC power supplies for plasma are often used continuously and use large equipment jigs, it is not easy to readjust the fluctuated output current back to the set value. It is necessary to constantly control the output current with high precision using feedback control.
そこで、従来のプラズマアーク溶接、溶断用直
流電源のサイリスタ整流器の制御方法では、第１
図に示すように、交流入力を入力端子１から、２
次側に所望の２次電圧が発生する変圧器２の１次
側に入力し、変圧器２の２次側に接続したサイリ
スタを含む制御整流部３により整流し、制御整流
部３の直流出力電流を、直流出力電流を検出する
電流検出部４、出力端子５を介して負荷（図示せ
ず）に供給する。 Therefore, in the conventional control method of the thyristor rectifier of the DC power supply for plasma arc welding and fusing, the first
As shown in the figure, AC input is input from input terminals 1 to 2.
A desired secondary voltage is input to the primary side of the transformer 2 which generates a desired secondary voltage, and is rectified by the control rectifier 3 including a thyristor connected to the secondary side of the transformer 2, and the DC output of the control rectifier 3 The current is supplied to a load (not shown) via a current detection section 4 that detects a DC output current and an output terminal 5.
また、電流検出部４の検出信号を、電流検出部
４に接続した比較増幅器６の反転入力端子に入力
するとともに、直流出力電流の起動値設定用の第
１出力電流調整用基準信号発生器Es1の起動値設
定レベルの第１出力調整用基準信号と、第２図に
示すように、時間的に零から徐々に増加し、ある
時点において第１出力調整用基準信号より高くな
り、その後、定常値設定レベルに保持される第２
出力電流調整用基準信号発生器Es2の第２出力調
整用基準信号とを、それぞれ第１、第２ダイオー
ドＤ１，Ｄ２を介して比較増幅器６の非反転端子
に入力する。 In addition, the detection signal of the current detection section 4 is inputted to the inverting input terminal of the comparator amplifier 6 connected to the current detection section 4, and the first output current adjustment reference signal generator Es is used for setting the starting value of the DC output current. As shown in FIG . 2 , the first output adjustment reference signal at the starting value setting level of 1 gradually increases from zero over time, becomes higher than the first output adjustment reference signal at a certain point, and then, The second value is maintained at the steady-state setting level.
The second output adjustment reference signal of the output current adjustment reference signal generator Es2 is input to the non-inverting terminal of the comparator amplifier 6 via the first and second diodes D1 and D2, respectively.
このとき、第１ダイオードＤ１と第２ダイオー
ドＤ２とがオア回路を構成し、第２出力調整用基
準信号が起動値設定レベルに達するまでの起動時
には第１出力調整用基準信号が比較増幅器６に入
力され、起動後には第２出力電流調整用基準信号
が比較増幅器６に入力される。 At this time, the first diode D1 and the second diode D2 constitute an OR circuit, and the first output adjustment reference signal is applied to the comparator amplifier 6 during startup until the second output adjustment reference signal reaches the startup value setting level. After startup, the second output current adjustment reference signal is input to the comparator amplifier 6.
また、比較増幅器６の出力信号は、検出信号の
レベルが上昇して反転入力端子のレベルが大きく
なると低下する。 Further, the output signal of the comparator amplifier 6 decreases as the level of the detection signal increases and the level of the inverting input terminal increases.
そして、比較増幅器６の出力信号を、入力端子
１の交流入力によつて動作する移相器７に入力
し、移相器７により、比較増幅器６の出力信号の
レベルの大、小に応じて制御整流部３のサイリス
タの導通角が大、小可変するように点弧位相を可
変制御する。 Then, the output signal of the comparison amplifier 6 is inputted to a phase shifter 7 operated by the AC input of the input terminal 1, and the phase shifter 7 adjusts the output signal according to the level of the output signal of the comparison amplifier 6. The ignition phase is variably controlled so that the conduction angle of the thyristor of the control rectifier 3 is varied.
したがつて、第１図の場合、制御整流部３の直
流出力電流が第３図の実線に示す特性に制御され
る。 Therefore, in the case of FIG. 1, the DC output current of the control rectifier 3 is controlled to have the characteristics shown by the solid line in FIG.
すなわち、起動時には、アークの発生を容易に
するため、第１出力調整用基準信号と検出信号の
誤差信号にもとづき、直流出力電流が、第１出力
調整用基準信号の起動値設定レベルの定電流に帰
還制御され、起動後には、第２出力調整用基準信
号と検出信号との誤差信号にもとづき、直流出力
電流が、徐々に第２出力調整用基準信号の定常値
設定レベルに増加してソフトスタート特性に制御
され、かつ、定常値設定レベルの電流に達する
と、定常値設定レベルの定電流になるように、帰
還制御される。 That is, at startup, in order to facilitate arc generation, the DC output current is set to a constant current of the starting value setting level of the first output adjustment reference signal based on the error signal between the first output adjustment reference signal and the detection signal. After startup, based on the error signal between the second output adjustment reference signal and the detection signal, the DC output current gradually increases to the steady value setting level of the second output adjustment reference signal, and the soft The current is controlled according to the start characteristic, and when the current reaches the steady-state value setting level, feedback control is performed so that the constant current becomes the steady-state value setting level.
ところで、第１図の場合、第１、第２出力調整
用基準信号を、オア回路を形成する第１、第２ダ
イオードＤ１，Ｄ２それぞれ介して比較増幅器６
に入力し、両調整用基準信号のレベルの高い方と
検出信号とを誤差増幅して直流出力電流を帰還制
御するため、サイリスタ整流器自身からの発熱に
よる温度上含む周囲温度の変化にもとづく第１、
第２ダイオードＤ１，Ｄ２のえん層電圧の変化
や、起動時からの経時ドリフトにより、直流出力
電流の制御基準となる両調整用基準信号のレベル
が変動し易く、しかも、両調整用基準信号のレベ
ル変動により、直流出力電流が大きな影響を受け
るため、直流出力電流の制御精度が低くなる問題
点がある。
By the way, in the case of FIG. 1, the first and second output adjustment reference signals are passed through the comparison amplifier 6 through the first and second diodes D1 and D2 forming an OR circuit, respectively.
In order to perform feedback control of the DC output current by error amplifying the higher level of both adjustment reference signals and the detection signal, the first control signal is input to ,
Due to changes in the layer voltages of the second diodes D1 and D2 and drift over time from startup, the levels of both adjustment reference signals, which serve as control standards for the DC output current, tend to fluctuate. Since the DC output current is greatly affected by level fluctuations, there is a problem in that the control accuracy of the DC output current becomes low.
この発明は、前記の点に留意してなされたもの
であり、交流入力を整流するサイリスタを含む制
御整流部の直流出力電流を検出する電流検出部を
設け、出力調整用基準信号と前記電流検出部の検
出信号との比較増幅により、前記サイリスタを点
弧制御し、前記直流出力電流を定電流特性に帰還
制御するサイリスタ整流器の制御方法において、
前記出力電流の起動値設定レベルの第１出力調
整用基準信号と前記検出信号との誤差信号を出力
する第１比較増幅器と、前記起動値設定レベルよ
り低レベルから徐々に前記起動値設定レベルより
高レベルの定常値設定レベルに上昇する第２出力
調整用基準信号と前記検出信号との誤差信号を出
力する第２比較増幅器と、前記両比較増幅器の出
力信号のレベルの高い方を移相器に出力するダイ
オード構成のオア回路とを備え、
前記移相器により前記オア回路の出力信号に応
じて前記サイリスタを点弧制御し、起動時の前記
出力電流を前記起動値設定レベルの定電流に帰還
制御し、前記第２出力調整用基準信号のレベルが
前記第１出力調整用基準信号より大きくなる起動
後の前記出力電流を、前記第２出力調整用基準信
号にもとづいて帰還制御し、前記定常値設定レベ
ルの定電流に徐々に増加することを特徴とするサ
イリスタ整流器の制御方法である。
The present invention has been made with the above points in mind, and includes a current detection section that detects a DC output current of a control rectification section including a thyristor that rectifies an AC input, and a reference signal for output adjustment and the current detection section that detects the current detection section. In the thyristor rectifier control method, the thyristor is controlled to fire by comparison and amplification with a detection signal of the section, and the DC output current is feedback-controlled to a constant current characteristic, comprising: a first output adjustment of a starting value setting level of the output current; a first comparator amplifier that outputs an error signal between the reference signal and the detection signal; and a second output that gradually increases from a level lower than the starting value setting level to a steady value setting level higher than the starting value setting level. a second comparison amplifier that outputs an error signal between the adjustment reference signal and the detection signal; and a diode-configured OR circuit that outputs the higher level of the output signals of both comparison amplifiers to the phase shifter; A phase shifter controls firing of the thyristor according to the output signal of the OR circuit, feedback controls the output current at startup to a constant current at the startup value setting level, and controls the output of the second output adjustment reference signal. Feedback control is performed based on the second output adjustment reference signal to gradually increase the output current after startup, the level of which becomes higher than the first output adjustment reference signal, to the constant current at the steady-state value setting level. This is a method for controlling a thyristor rectifier, characterized by:
したがつて、第１、第２出力調整用基準信号そ
れぞれは、第１、第２比較増幅器によつて別個に
検出信号と比較増幅され、このとき、第２出力調
整用基準信号が起動値設定レベルに達するまでの
起動時には、第１比較増幅器の出力信号がオア回
路を介して移相器に入力され、第１出力調整用基
準信号にもとづく帰還制御により、直流出力電流
が起動値設定レベルの定電流に制御され、第２出
力調整用基準信号が起動値設定レベルを超えて定
常時設定レベルに上昇する起動後には、第２比較
増幅器の出力信号がオア回路を介して移相器に入
力され、第２出力調整用基準信号にもとづく帰還
制御により、直流出力電流が起動値設定レベルの
電流から定常値設定レベルの電流に徐々に増加し
て常時値設定レベルの定電流に制御される。
Therefore, the first and second output adjustment reference signals are separately compared and amplified with the detection signal by the first and second comparison amplifiers, and at this time, the second output adjustment reference signal is set to the starting value. During startup, the output signal of the first comparator amplifier is input to the phase shifter via the OR circuit, and feedback control based on the first output adjustment reference signal causes the DC output current to reach the startup value setting level. After startup, which is controlled by a constant current and the second output adjustment reference signal exceeds the startup value setting level and rises to the steady state setting level, the output signal of the second comparator amplifier is input to the phase shifter via the OR circuit. Then, by feedback control based on the second output adjustment reference signal, the DC output current gradually increases from the current at the starting value setting level to the current at the steady value setting level, and is controlled to the constant current at the constant value setting level.
そして、オア回路が出力直流電流の帰還制御路
内に挿入されているため、オア回路のダイオード
が周囲温度変化、経時ドリフトなどの影響を受
け、オア回路の出力信号が変動しても、オア回路
の出力信号の変動を含む直流出力電流の第１、第
２出力調整用基準信号それぞれにもとづく電流か
らの変動が帰還制御され、直流出力電流が常時高
精度に帰還制御される。 Since the OR circuit is inserted in the feedback control path of the output DC current, even if the output signal of the OR circuit fluctuates due to the influence of ambient temperature changes, drift over time, etc., the OR circuit will The fluctuations in the DC output current from the current based on the first and second output adjustment reference signals, including fluctuations in the output signal of the DC output current, are feedback-controlled, and the DC output current is feedback-controlled with high accuracy at all times.
つぎに、この発明を、その実施例を示した第４
図および第５図とともに詳細に説明する。
Next, this invention will be described in the fourth section showing its embodiment.
This will be explained in detail with reference to FIG.
（１実施例）
まず、１実施例を示した第４図について説明す
る。(One Example) First, FIG. 4 showing one example will be described.
第４図において、第１図と同一記号は同一のも
のを示し、８は電流検出部４に反転入力端子が接
続された第１比較増幅器であり、非反転入力端子
に第１出力電流調整用基準信号発生器Es1が接続
されている。９は電流検出部４に反転入力端子が
接続された第２比較増幅器であり、非反転入力端
子に第２出力電流調整用基準信号発生器Es2が接
続されている。Ｄ３はアノードが第１比較増幅器
８の出力端子に接続された第３ダイオードであ
り、カソードが移相器７に接続されている。Ｄ４
はアノードが第２比較増幅器９の出力端子に接続
された第４ダイオードであり、カソードが移相器
７に接続された、第３ダイオードＤ３とともにオ
ア回路を構成する。 In FIG. 4, the same symbols as in FIG. 1 indicate the same things, and 8 is a first comparator amplifier whose inverting input terminal is connected to the current detection section 4, and the non-inverting input terminal is used for adjusting the first output current. A reference signal generator Es 1 is connected. Reference numeral 9 denotes a second comparator amplifier whose inverting input terminal is connected to the current detection section 4, and whose non-inverting input terminal is connected to a second output current adjustment reference signal generator Es2 . D3 is a third diode whose anode is connected to the output terminal of the first comparison amplifier 8, and whose cathode is connected to the phase shifter 7. D4
is a fourth diode whose anode is connected to the output terminal of the second comparator amplifier 9, and forms an OR circuit together with a third diode D3 whose cathode is connected to the phase shifter 7.
つぎに、第４図の動作について説明する。 Next, the operation shown in FIG. 4 will be explained.
交流入力を入力端子１から変圧器２の１次側に
入力し、変圧器２の２次側に接続された制御整流
部３により整流し、制御整流部３の直流出力電流
を、電流検出部４、出力端子５を介して負荷（図
示せず）に流し、電流検出部４の検出信号を、第
１、第２比較増幅器８，９のそれぞれの反転入力
端子に入力し、第１比較増幅器８により、第１出
力調整用基準信号と検出信号とを直接比較増幅し
て両信号のレベル差の誤差信号を形成するととも
に、第２比較増幅器９により、第２出力調整用基
準信号と検出信号とを直接比較増幅して両信号の
レベル差の誤差信号を形成し、第３、第４ダイオ
ードＤ３，Ｄ４が構成するオア回路により、第
１、第２比較増幅器８，９の出力信号のうち、レ
ベルの高い方を優先的に移相器７に入力し、移相
器７により制御整流部３のサイリスタを点弧制御
する。 AC input is input to the primary side of the transformer 2 from the input terminal 1, rectified by the control rectifier 3 connected to the secondary side of the transformer 2, and the DC output current of the control rectifier 3 is sent to the current detection unit. 4. The current is applied to a load (not shown) through the output terminal 5, and the detection signal of the current detection section 4 is inputted to the inverting input terminals of the first and second comparison amplifiers 8 and 9, and the first comparison amplifier 8 directly compares and amplifies the first output adjustment reference signal and the detection signal to form an error signal of the level difference between both signals, and the second comparison amplifier 9 compares and amplifies the second output adjustment reference signal and the detection signal. is directly compared and amplified to form an error signal of the level difference between both signals, and an OR circuit constituted by the third and fourth diodes D3 and D4 selects one of the output signals of the first and second comparison amplifiers 8 and 9. , the one with the higher level is preferentially input to the phase shifter 7, and the phase shifter 7 controls the ignition of the thyristor of the control rectifier 3.
ところで、両比較増幅器８，９の出力信号のレ
ベルは、周知の比較増幅器と同様に、反転入力端
子のレベルが非反転入力端子のレベルに上昇する
にしたがつて低下する。 Incidentally, the level of the output signals of both comparison amplifiers 8 and 9 decreases as the level of the inverting input terminal rises to the level of the non-inverting input terminal, similarly to the well-known comparison amplifier.
また、移相器７は、入力レベルが零のときに、
制御整流部３のサイリスタの導通角を現在の導通
角に保持するとともに、入力レベルが増、減変化
すると、入力レベルに応じて導電角を現在の導通
角より大、小それぞれに可変制御する。 Moreover, when the input level is zero, the phase shifter 7
The conduction angle of the thyristor of the control rectifier 3 is maintained at the current conduction angle, and when the input level increases or decreases, the conduction angle is variably controlled to be larger or smaller than the current conduction angle depending on the input level.
そして、起動によつて第２出力調整用基準信号
が、第１出力調整用基準信号の起動値設定レベル
より低いレベル（零）から徐々に定常値設定レベ
ルに上昇するため、第２出力調整用基準信号が第
１出力調整用基準信号の起動値設定レベルに上昇
するまでの起動時には、第１比較増幅器８の出力
信号のレベルが第２比較増幅器９の出力信号のレ
ベルより高くなり、オア回路を介して移相器７に
第１比較増幅器８の出力信号が優先的に入力さ
れ、直流出力電流が第１出力調整用基準信号の起
動値設定レベルの定電流に帰還制御される。 Then, due to activation, the second output adjustment reference signal gradually rises from a level (zero) lower than the starting value setting level of the first output adjustment reference signal to the steady value setting level. During startup until the reference signal rises to the startup value setting level of the first output adjustment reference signal, the level of the output signal of the first comparator amplifier 8 becomes higher than the level of the output signal of the second comparator amplifier 9, and the OR circuit is activated. The output signal of the first comparator amplifier 8 is preferentially inputted to the phase shifter 7 via the phase shifter 7, and the DC output current is feedback-controlled to a constant current at the activation value setting level of the first output adjustment reference signal.
また、第２出力調整用基準信号が起動値設定レ
ベルを超えて定常値設定レベルに上昇し始める
と、第２比較増幅器９の出力信号のレベルが第１
比較増幅器８の出力信号のレベルより高くなり、
オア回路を介して移相器７に入力される信号が第
１比較増幅器８の出力信号から第２比較増幅器９
の出力信号に切換わり、このとき、直流出力電流
は第２出力調整用基準信号のレベルの増加に比例
して増加するように帰還制御される。 Furthermore, when the second output adjustment reference signal exceeds the starting value setting level and begins to rise to the steady value setting level, the level of the output signal of the second comparison amplifier 9 changes to the first value setting level.
becomes higher than the level of the output signal of the comparison amplifier 8,
The signal input to the phase shifter 7 via the OR circuit is transferred from the output signal of the first comparator amplifier 8 to the second comparator amplifier 9.
At this time, the DC output current is feedback-controlled so as to increase in proportion to the increase in the level of the second output adjustment reference signal.
さらに、第２出力調整用基準信号が定常値設定
レベルに達すると、直流出力電流が定常値設定レ
ベルの定電流に帰還制御される。 Furthermore, when the second output adjustment reference signal reaches the steady-state value setting level, the DC output current is feedback-controlled to the constant current of the steady-state value setting level.
したがつて、起動時には、アークの発生を容易
にするため、第１出力調整用基準信号の比較増幅
にもとづき、直流出力電流が起動値設定レベルの
定電流に制御され、起動後には、第２出力調整用
基準信号と検出信号との比較増幅にもとづき、直
流出力電流がソフトスタート特性に制御されて
徐々に定常値設定レベルの電流に増加制御される
とともに、定常値設定レベルの電流に達した後は
当該設定レベルの定電流に制御され、直流出力電
流は第３図の実線に示す特性に帰還制御される。 Therefore, at startup, in order to facilitate arc generation, the DC output current is controlled to a constant current at the startup value setting level based on comparison and amplification of the first output adjustment reference signal, and after startup, the second Based on the comparison and amplification of the output adjustment reference signal and the detection signal, the DC output current is controlled by a soft start characteristic and gradually increases to the steady value setting level, and the current reaches the steady value setting level. Thereafter, the constant current is controlled to the set level, and the DC output current is feedback-controlled to the characteristic shown by the solid line in FIG.
そして、第４図の場合は、第１、第２比較増幅
器８，９により、第１、第２出力調用基準信号そ
れぞれと電流検出部４の検出信号とが、第１図の
第１、第２ダイオードＤ１，Ｄ２などを介在させ
ることなく直接比較され、第１、第２比較増幅器
８，９の出力信号が、第３、第４ダイオードＤ
３，Ｄ４のオア回路を介して移相器７に入力され
るため、周囲温度の変化による第３、第４ダイオ
ードＤ３，Ｄ４のえん層電圧の変化や、起動時か
らの経時ドリフトに対し、第１、第２比較増幅器
８，９に入力される第１、第２出力調整用基準信
号が変化することがなく、しかも、第３、第４ダ
イオードＤ３，Ｄ４のオア回路が直流出力電流の
帰還制御路内に挿入され、第３、第４ダイオード
Ｄ３，Ｄ４が周囲温度の変化、経時ドリフトの影
響を受けても、該影響にもとづく直流出力電流の
変動が、常に、電流検出部４の検出にもとづき、
移相器７によつて制御する帰還制御にしたがつて
補正制御され、直流出力電流が、第１、第２出力
調整用基準信号にもとづいて常時高精度に帰還制
御され、第３図に示す理想的な特性で起動設定レ
ベルの定電流から定常設定レベルの定電流に移行
し、良好なパルスアーク溶接、溶断などが行なえ
る。 In the case of FIG. 4, the first and second comparison amplifiers 8 and 9 convert the first and second output adjustment reference signals and the detection signal of the current detection unit 4 into the first and second comparison amplifiers 8 and 9, respectively, and The output signals of the first and second comparison amplifiers 8 and 9 are directly compared without intervening two diodes D1 and D2, and the output signals of the first and second comparison amplifiers 8 and 9 are directly compared without intervening diodes D1 and D2.
Since it is input to the phase shifter 7 through the OR circuit of 3 and D4, it is not affected by changes in the layer voltage of the 3rd and 4th diodes D3 and D4 due to changes in ambient temperature, and by drift over time from the time of startup. The first and second output adjustment reference signals input to the first and second comparison amplifiers 8 and 9 do not change, and the OR circuit of the third and fourth diodes D3 and D4 Even if the third and fourth diodes D3 and D4 are inserted in the feedback control path and are influenced by changes in ambient temperature or drift over time, fluctuations in the DC output current due to the influences will always cause the current detection unit 4 to Based on the detection
Correction control is performed according to the feedback control controlled by the phase shifter 7, and the DC output current is constantly feedback-controlled with high accuracy based on the first and second output adjustment reference signals, as shown in FIG. With ideal characteristics, the constant current at the start-up setting level shifts to the constant current at the steady-state setting level, allowing for good pulse arc welding, fusing, etc.
（他の実施例）
つぎに、他の実施例を示した第５図について説
明する。(Other Embodiments) Next, FIG. 5 showing another embodiment will be described.
第５図において、第４図と同一記号は同一のも
のを示し、IC１は第１演算増幅器であり、電流
検出部４の検出信号が第１抵抗Ｒ１を介して反転
入力端子（−）に入力され、非反転入力端子
（＋）に第１出力電流調整用基準信号発生器Es1
の第１出力調整用基準信号が第２抵抗Ｒ２を介し
て入力される。Ｒ３は第１演算増幅器IC１の反
転入力端子（−）と出力端子とに両端が接続され
た第３抵抗であり、第１演算増幅器IC１の利得
を決定する負帰還回路を構成し、第１演算増幅器
IC１と、第１、第２抵抗Ｒ１，Ｒ２とともに比
較増幅器１０を構成する。Ｃ１は第１位相補正用
コンデンサであり、一端が第４抵抗Ｒ４を介して
第１演算増幅器IC１の出力端子に接続され、他
端が第１演算増幅器IC１の反転入力端子（−）
に接続されている。 In FIG. 5, the same symbols as in FIG. 4 indicate the same things, IC1 is the first operational amplifier, and the detection signal of the current detection section 4 is input to the inverting input terminal (-) via the first resistor R1. The reference signal generator Es 1 for adjusting the first output current is connected to the non-inverting input terminal (+).
The first output adjustment reference signal is inputted via the second resistor R2. R3 is a third resistor whose both ends are connected to the inverting input terminal (-) and the output terminal of the first operational amplifier IC1, and constitutes a negative feedback circuit that determines the gain of the first operational amplifier IC1. amplifier
A comparison amplifier 10 is configured together with IC1 and first and second resistors R1 and R2. C1 is a first phase correction capacitor, one end of which is connected to the output terminal of the first operational amplifier IC1 via the fourth resistor R4, and the other end connected to the inverting input terminal (-) of the first operational amplifier IC1.
It is connected to the.
IC２は第２演算増幅器であり、電流検出部４
の検出信号が第５抵抗Ｒ５を介して反転入力端子
（−）に入力されるとともに、非反転入力端子
（＋）に第６抵抗Ｒ６を介した第２出力電流調整
用基準信号発生器Es2の第２出力調整用基準信号
が入力される。Ｒ７は第２演算増幅器IC２の反
転入力端子（−）と出力端子とに両端が接続され
た第７抵抗であり、第２演算増幅器IC２の利得
を決定する負帰還回路を構成し、第２演算増幅器
IC２と、第５、第６抵抗Ｒ５，Ｒ６とともに第
２比較増幅器１１を構成する。Ｃ２は第２位相補
正用コンデンサであり、一端が第２演算増幅器
IC２の出力端子に接続され、他端が第２演算増
幅器IC２の反転入力端子（−）に接続されてい
る。 IC2 is a second operational amplifier, and the current detection section 4
The detection signal is input to the inverting input terminal (-) via the fifth resistor R5, and the second output current adjustment reference signal generator Es2 is input to the non-inverting input terminal (+) via the sixth resistor R6. A second output adjustment reference signal is input. R7 is a seventh resistor whose both ends are connected to the inverting input terminal (-) and the output terminal of the second operational amplifier IC2, and constitutes a negative feedback circuit that determines the gain of the second operational amplifier IC2. amplifier
A second comparator amplifier 11 is configured together with IC2 and the fifth and sixth resistors R5 and R6. C2 is a second phase correction capacitor, one end of which is connected to the second operational amplifier.
It is connected to the output terminal of IC2, and the other end is connected to the inverting input terminal (-) of the second operational amplifier IC2.
Ｄ５はアノードが第２演算増幅器IC２の出力
端子に接続された第５ダイオードであり、カソー
ドが第１位相補正用コンデンサＣ１の一端に接続
されている。Ｄ６はアノードが第１位相補正用コ
ンデンサＣ１の一端に接続された第６ダイオード
であり、カソードが移相器７に接続され、第５ダ
イオードＤ５とともにオア回路を形成する。 D5 is a fifth diode whose anode is connected to the output terminal of the second operational amplifier IC2, and whose cathode is connected to one end of the first phase correction capacitor C1. D6 is a sixth diode whose anode is connected to one end of the first phase correction capacitor C1, whose cathode is connected to the phase shifter 7, and forms an OR circuit together with the fifth diode D5.
なお、第２位相補正用コンデンサＣ２は第１位
相補正用コンデンサＣ１より容量が大きく設定さ
れている。 Note that the second phase correction capacitor C2 is set to have a larger capacitance than the first phase correction capacitor C1.
つぎに、第５図の動作について説明する。 Next, the operation shown in FIG. 5 will be explained.
第４図の制御整流部３の直流出力電流が、電流
検出部４により検出され、電流検出部４の検出出
信号が第１、第２演算増幅器IC１，IC２の反転
入力端子（−）に入力され、第１、第２出力調整
用基準信号とそれぞれ比較増幅されるため、起動
時は第１比較増幅器１０の出力が移相器７に入力
され、起動後は第２比較増幅器１１の出力が移相
器７に入力され、起動の際には第４図とほぼ同様
にして制御整流部３のサイリスタが制御され、直
流出力電流がソフトスタート特性で第１出力調整
用基準信号の起動値設定レベルの定電流から第２
出力調整基準信号の定常設定レベルの定電流に移
行する。 The DC output current of the control rectifier 3 in FIG. 4 is detected by the current detector 4, and the detection output signal of the current detector 4 is input to the inverting input terminals (-) of the first and second operational amplifiers IC1 and IC2. and are compared and amplified with the first and second output adjustment reference signals, respectively. Therefore, at startup, the output of the first comparison amplifier 10 is input to the phase shifter 7, and after startup, the output of the second comparison amplifier 11 is input to the phase shifter 7. The input is input to the phase shifter 7, and at startup, the thyristor of the control rectifier 3 is controlled in substantially the same manner as shown in FIG. 2nd level constant current
Shifts to constant current at the steady setting level of the output adjustment reference signal.
ところで、第５図の場合は、パルスアーク溶
接、溶断を停止する際に、つぎに説明する滑らか
なダウンスロープ特性で直流出力電流を徐々に減
少、トーチなどを保護することができる利点も有
する。 By the way, the case shown in FIG. 5 also has the advantage that when stopping pulse arc welding or fusing, the DC output current can be gradually reduced due to the smooth down slope characteristic described below, and the torch etc. can be protected.
すなわち、第２出力調整用基準信号の定常値設
定レベルにもとづき、直流出力電流が定常値設定
レベルの定電流に制御されているときは、第１比
較増幅器１０の出力信号が零状態に保持されてい
る。 That is, when the DC output current is controlled to a constant current at the steady-state value setting level based on the steady-state value setting level of the second output adjustment reference signal, the output signal of the first comparator amplifier 10 is held at a zero state. ing.
そして、この状態で第２出力調整用基準信号の
レベルを徐々に低下すると、第２位相補正用コン
デンサＣ２の大容量にもとづき、第２比較増幅器
１１の出力信号のレベルが滑らかに低下し、直流
出力電流が滑らかに減少するとともに第１位相補
正用コンデンサＣ１の一端の電位も減少し、直流
出力電流が徐々に減少して滑らかなダウンスロー
プ特性で直流出力電流が遮断される。 Then, when the level of the second output adjustment reference signal is gradually lowered in this state, the level of the output signal of the second comparison amplifier 11 is smoothly lowered based on the large capacity of the second phase correction capacitor C2, and the DC As the output current decreases smoothly, the potential at one end of the first phase correction capacitor C1 also decreases, the DC output current gradually decreases, and the DC output current is cut off with a smooth down slope characteristic.
以上のように、この発明のサイリスタ整流器の
制御方法によると、第１、第２出力調整用基準信
号それぞれと電流検出部の検出信号とを第１、第
２比較増幅器それぞれで比較増幅し、両比較増幅
器の出力信号をオア回路を介して移相器に入力
し、制御整流部のサイリスタを点弧制御して直流
出力電流を帰還制御したことにより、オア回路の
ダイオードが周囲温度、経年ドリフトなどの影響
を受けても、直流出力電流の制御基準となる両調
整用基準信号が変動せず、しかも、周囲温度、経
年ドリフトなどの影響にもとづくオア回路の出力
信号の変動が帰還制御によつて補正されるため、
直流出力電流を高い精度で常時帰還制御し、起動
値設定レベルの定電流から定常値設定レベルの定
電流に徐々に増加させることができ、直流出力電
流の制御精度が著しく向上するものである。
As described above, according to the thyristor rectifier control method of the present invention, each of the first and second output adjustment reference signals and the detection signal of the current detection section are compared and amplified by the first and second comparison amplifiers, and both The output signal of the comparator amplifier is input to the phase shifter via the OR circuit, and the thyristor in the control rectifier is controlled to fire to feedback control the DC output current, so that the diode in the OR circuit is free from ambient temperature, aging drift, etc. Both adjustment reference signals, which serve as control standards for the DC output current, do not change even when influenced by Because it is corrected,
The DC output current can be continuously feedback-controlled with high accuracy and gradually increased from the constant current at the starting value setting level to the constant current at the steady value setting level, and the control accuracy of the DC output current is significantly improved.
第１図は従来のサイリスタ整流器の制御方法を
示すブロツク図、第２図は第２出力電流調整用基
準信号の時間と信号値との関係図、第３図はこの
発明が適応されるサイリスタ整流器の時間と直流
出力電流との関係図、第４図はこの発明のサイリ
スタ整流器の制御方法の１実施例のブロツク図、
第５図はこの発明の他の実施例の一部の回路図で
ある。
３……制御整流部、４……電流検出部、７……
移相器、８，１０……第１比較増幅器、９，１１
……第２比較増幅器、Ｄ３，Ｄ４，Ｄ５，Ｄ６…
…第３ないし第６ダイオード。
Fig. 1 is a block diagram showing a conventional control method for a thyristor rectifier, Fig. 2 is a diagram showing the relationship between the time and signal value of the reference signal for adjusting the second output current, and Fig. 3 is a thyristor rectifier to which the present invention is applied. FIG. 4 is a block diagram of an embodiment of the thyristor rectifier control method of the present invention.
FIG. 5 is a partial circuit diagram of another embodiment of the invention. 3... Control rectifier section, 4... Current detection section, 7...
Phase shifter, 8, 10...first comparison amplifier, 9, 11
...Second comparator amplifier, D3, D4, D5, D6...
...3rd to 6th diode.
Claims (1)
流部の直流出力電流を検出する電流検出部を設
け、出力調整用基準信号と前記電流検出部の検出
信号との比較増幅により、前記サイリスタを点弧
制御し、前記直流出力電流を定電流特性に帰還制
御するサイリスタ整流器の制御方法において、 前記出力電流の起動値設定レベルの第１出力調
整用基準信号と前記検出信号との誤差信号を出力
する第１比較増幅器と、前記起動値設定レベルよ
り低レベルから徐々に前記起動値設定レベルより
高レベルの定常値設定レベルに上昇する第２出力
調整用基準信号と前記検出信号との誤差信号を出
力する第２比較増幅器と、前記両比較増幅器の出
力信号のレベルの高い方を移相器に出力するダイ
オード構成のオア回路とを備え、 前記移相器により前記オア回路の出力信号に応
じて前記サイリスタを点弧制御し、起動時の前記
出力電流を前記起動値設定レベルの定電流に帰還
制御し、前記第２出力調整用基準信号のレベルが
前記第１出力調整用基準信号により大きくなる起
動後の前記出力電流を、前記第２出力調整用基準
信号にもとづいて帰還制御し、前記定常値設定レ
ベルの定電流に徐々に増加することを特徴とする
サイリスタ整流器の制御方法。[Scope of Claims] 1. A current detection unit is provided to detect a DC output current of a control rectification unit including a thyristor that rectifies an AC input, and by comparing and amplifying a reference signal for output adjustment and a detection signal of the current detection unit, In the thyristor rectifier control method, the thyristor rectifier is controlled to fire and the DC output current is feedback-controlled to a constant current characteristic, wherein the error between the first output adjustment reference signal and the detection signal at the starting value setting level of the output current is a first comparison amplifier that outputs a signal; a second output adjustment reference signal that gradually increases from a level lower than the starting value setting level to a steady value setting level higher than the starting value setting level; and the detection signal. a second comparison amplifier that outputs an error signal; and a diode-configured OR circuit that outputs the higher level of the output signals of both comparison amplifiers to a phase shifter; ignition control of the thyristor according to the starting value, and feedback control of the output current at startup to a constant current of the starting value setting level, so that the level of the second output adjustment reference signal becomes equal to the first output adjustment reference signal. A method for controlling a thyristor rectifier, characterized in that the output current, which increases after startup, is feedback-controlled based on the second output adjustment reference signal, and gradually increases to the constant current at the steady-state value setting level.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP6031580A JPS56157271A (en) | 1980-05-06 | 1980-05-06 | Controlling method for thyristor rectifier |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP6031580A JPS56157271A (en) | 1980-05-06 | 1980-05-06 | Controlling method for thyristor rectifier |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPS56157271A JPS56157271A (en) | 1981-12-04 |
| JPS6255394B2 true JPS6255394B2 (en) | 1987-11-19 |
Family
ID=13138612
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP6031580A Granted JPS56157271A (en) | 1980-05-06 | 1980-05-06 | Controlling method for thyristor rectifier |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JPS56157271A (en) |
Families Citing this family (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| RU2506625C1 (en) * | 2013-01-09 | 2014-02-10 | Федеральное государственное казенное военное образовательное учреждение высшего профессионального образования "ВОЕННАЯ АКАДЕМИЯ СВЯЗИ имени Маршала Советского Союза С.М. Буденного" Министерства обороны Российской Федерации | Device for automated control of semiconductor elements of bridge rectifier |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| SE376335B (en) * | 1974-07-10 | 1975-05-12 | Asea Ab |
-
1980
- 1980-05-06 JP JP6031580A patent/JPS56157271A/en active Granted
Also Published As
| Publication number | Publication date |
|---|---|
| JPS56157271A (en) | 1981-12-04 |
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