JPS628963B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention provides a method for reducing noise (and/or interference waves, interference noise) that exists or occurs within the occupied frequency band of the FM signal to be demodulated and/or in the frequency band adjacent thereto. A phase tracking loop (abbreviated as a phase tracking loop) is designed to effectively eliminate the noise generated in the FM demodulated signal and obtain a high-fidelity FM demodulated signal.
It has been made possible to expand the applicable frequency band and simplify the configuration of FM demodulation circuits based on the PTL (sometimes referred to as PTL) method.
The purpose is to obtain an FM demodulation circuit using the PTL method〓〓〓〓
It was done by

The FM demodulation circuit using the PTL method described above was initially influenced by noise and interference waves reproduced from a 4-channel stereophonic record using the so-called CD-4 method, which was researched and developed by the applicant's company and put into practical use. An FM demodulation circuit for obtaining a high-fidelity FM demodulated signal from which noise generated in the FM demodulated signal based on the presence of noise and interference waves is effectively removed from the FM signal. This was developed by the applicant company as FM demodulator 3, as shown in Figure 1.
A variable bandpass filter 2 is provided as a pre-stage circuit, and the center frequency of the variable bandpass filter 2 is set as follows.
If it can be controlled to always match the instantaneous frequency of the FM signal supplied to input terminal 1, even if noise or interference waves are present in the FM signal to be demodulated, the FM The starting point was the idea that it would be possible to send an FM demodulated signal of sufficiently high quality to the output terminal 4 from the demodulator 3, and it was completed as a result of repeated research to realize this idea. The basic configuration of this PTL type FM demodulation circuit is as shown in FIG. 2, and a patent application has already been filed by the applicant company.

That is, in Fig. 2, 1 is the input terminal for the FM signal to be demodulated, 4 is the output terminal for the FM demodulated signal, and 5 is the input terminal for the entire frequency band, with a phase difference of 90° between the output signals. 6 is a variable bandpass filter whose center frequency is variable according to the control signal; 7 is a phase comparator (multiplier); 8 is a loop filter; 9
is a loop amplifier, and the FM signal supplied to input terminal 1 is filtered by Hilbert filter 5 at 90
After being phase-shifted by .degree., the signal is supplied to the phase comparator 7 as one input signal, and is also supplied to the phase comparator 7 via the variable bandpass filter 6 as the other input signal.

Here, if the variable bandpass filter 6 is controlled by the control signal so that the center frequency of the variable bandpass filter 6 always has a frequency value that matches the instantaneous frequency of the input FM signal. That is, when the variable bandpass filter 6 is operated as a tracking filter 6 whose center frequency always matches the instantaneous frequency of the input FM signal,
It is clear that noise and interference waves in the input FM signal are effectively suppressed.

The state in which the tracking filter 6 has a center frequency that matches the instantaneous frequency of the input FM signal, in other words, the state in which the tracking filter 6 does not impart phase rotation to the FM signal, is the state in which the tracking filter 6 has a center frequency that matches the instantaneous frequency of the input FM signal. This can be realized by detecting the phase difference between the FM signals and applying feedback to the tracking filter 6 so that the phase difference becomes small. This is a circuit layout.

In the phase comparator 7 in the circuit arrangement shown in FIG. 2, the FM signal from the Hilbert filter 5 is used as a phase comparison reference signal, and the phase difference is obtained as a result of phase comparison between it and the FM signal from the tracking filter 6. The signal is given to loop filter 8. The loop filter 8 removes unnecessary signal components generated in the phase difference signal due to the phase comparison operation.

The output signal from the loop filter 8 is amplified by the loop amplifier 9 and given to the output terminal 4 as an FM demodulated signal, and also to the tracking filter 6.
It is fed back as a navel control signal.

Here, when the FM signal passes through the tracking filter 6, regardless of the control signal being fed back to the tracking filter 6, there is always some slight delay, so the phase comparator The output phase difference signal actually corresponds to the change in the instantaneous phase of the FM signal in a minute time, and this corresponds to the FM demodulated signal f.
(t) That is what it is.

Therefore, in the one-round phase tracking loop shown by the circuit arrangement shown in the second diagram, the tracking filter 6 has the function of tracking the FM signal and the function of outputting the FM demodulated signal at the same time. This is the FM shown in Figure 1.
The PTL corresponds to the content of the demodulation circuit and is shown by the circuit layout shown in this second diagram.
The FM demodulation circuit based on this system was able to obtain good demodulation performance when used in the FM signal demodulation circuit for the reproduced signal from a CD-4 system record.

However, the previously proposed FM demodulation circuit based on the PTL method shown in the circuit layout shown in the second diagram above (1) uses a Hilbert filter;
〓〓〓〓
(2) Due to the use of a variable bandpass filter as a tracking filter, the previously proposed FM demodulator using the PTL method is required to demodulate FM signals in a high frequency range. For example, it was difficult to use as an FM demodulation circuit for an FM tuner or a television receiver, and there were other problems such as the large number of parts required for the circuit configuration.

In other words, a Hilbert filter is constructed using a phase shifter, a differentiating circuit, an integrating circuit, a limiter, etc., but it is difficult to design a highly accurate Hilbert filter used in a high frequency region, and It is difficult to obtain a variable bandpass filter that operates as a good tracking filter in the frequency domain, and the FM demodulation circuit using the PTL method with the circuit layout shown in Figure 2 requires a large number of components. There were some problems, such as:

The present invention provides an FM demodulation circuit using the PTL method that satisfactorily eliminates the above-mentioned drawbacks of the FM demodulation circuit using the previously proposed PTL method. A detailed explanation will be given with reference to the following.

FIG. 3 is a block diagram of an embodiment of the FM demodulation circuit using the PTL method of the present invention. , the same drawing symbols as those used in FIG. 2 are used.

In Figure 3, 1 is the input terminal of the FM signal to be demodulated, 7 is the phase comparator, and 8 is the transfer function of G.
(S), 9 is a loop amplifier, 4 is an output terminal for an FM demodulated signal, and VHPF is a variable high-pass filter used as a tracking filter so that the use of a Hilbert filter can be omitted.

Note that 10 is a limiter provided as necessary.

The FM demodulation circuit using the phase tracking loop method of the present invention differs from the previously proposed FM demodulation circuit shown in FIG. 2 in that a variable high-pass filter VHPF is used as the tracking filter. , thereby eliminating the need for the Hilbert filter 5, which causes problems in the FM demodulation circuit using the phase tracking loop method of the present invention, which is a problem in the previously proposed FM demodulation circuit using the phase tracking loop method. However, in the present invention, the following points are solved:
Even if a variable high-pass filter VHPF is used instead of the variable bandpass filter used as a tracking filter in the previously proposed FM demodulation circuit arrangement, the previously proposed FM
FM demodulation effect similar to that of the demodulation circuit can be obtained;
Also, the reasons why the Hilbert filter 5, which was required in the previously proposed FM demodulation circuit arrangement, is no longer necessary in the FM demodulation circuit of the present invention will be explained in detail.

Figure 4 shows the phase tracking loop method of the present invention.
Variable high-pass filter used in FM demodulation circuit
This is a circuit diagram showing an example configuration of a VHPF, and the configuration of the variable high-pass filter VHPF shown in FIG. 4 is the same configuration as the variable high-pass filter VHPF shown in FIG. , which uses a variable capacitance element as the variable reactance element {In addition, the variable high-pass filter VHPF uses a variable inductance element as the variable reactance element, as shown in Figure Any format may also be used.

The variable high-pass filter VHPF shown in Fig. 4 is composed of a coil L, a resistor _R , a variable capacitor C ) As is clearer, 2
It has high-pass filtering characteristics of the following type.

And C≫Cx, R≫L/(C+Cx)≒L/
Under the condition C, the amplitude characteristics and phase characteristics derived from the transfer function T(S) shown by equation (1) are as shown by the curve diagram in FIG. In FIG. 5, the curves are amplitude characteristics, and the curves are phase characteristics.

Here, if ω _p is the resonant angular frequency (hereinafter referred to as resonant frequency ω _p ) and the increase in amplitude at the resonance point is H, then the resonant frequency ω _p and the increase in amplitude H are the following ( 2) and (3).

ω _p =1/√(+)≒1/√……(2) H=R√(+)≒R√……(3) 〓〓〓〓
Therefore, the resonant frequency ω shown in equation (2) above is
In _p , R shown in the above formula (3),
If the values of C and L are appropriately selected so that the value of H expressed by equation (3) becomes a sufficiently large value, the variable high-pass filter VHPF shown in Figure 4 can be adjusted to a value near the resonance frequency ω _p . This variable high-pass filter VHPF can be used in place of the variable bandpass filter because it exhibits sufficiently satisfactory frequency selection characteristics.

Furthermore, since the variable high-pass filter VHPF described above has a phase angle of +90° at the resonant frequency ω _p , the modulation signal μ(t) is now at the carrier frequency ω _c
Under the ^{condition of} giving a sufficiently ^{small frequency} deviation compared to The FM signal C(t) expressed by the above equation (4) is expressed by the variable high-pass filter VHPF.
and if the capacitance value of capacitor C _X does not change over time when the FM signal passes through the variable high-pass filter VHPF, then A signal C _p obtained by passing the output signal from the filter VHPF through the limiter 10
(t) is expressed by the following equation (5), C _p (t)=e ^j {〓〓 ^t+ ∫〓〓 ⁽ 〓 ^)d 〓 ^- 〓〓 ^(t)+ 〓}=+je ^j {〓〓 ^t+ ∫〓〓 ⁽ 〓 ^)d 〓 ^- 〓〓 ^(t) } ...(5) Also, when the above FM signal C(t) passes through the variable high-pass filter VHPF, the variable capacitance If the capacitance value of capacitor C _X changes over time as a function of f(t), the variable high-pass filter VHPF
The signal C' _p (t) obtained by passing the output signal from the limiter 10 is expressed by the following equation (6).

C′ _p (t)=+je ^j {〓〓 ^t+ ∫〓〓 ⁽ 〓 ^)d 〓 ^- 〓〓 ^(t)- 〓 ^f(t) } ...(6) In the above equation, τ is the variable high-pass filter VHPF
α is the group delay given to the FM signal by the variable capacitor _C The variable high-pass filter shown in Figure 4 is expressed by the following equation (7).

τ _{= 2C}
(t) and C' _p (t) are the output signals from the variable high-pass filter VHPF that have been passed through the limiter 10 to remove amplitude fluctuations, as mentioned above. As can be fully understood from the description, as mentioned above, when the frequency deviation of the FM signal is sufficiently small compared to the frequency ω _c of the carrier wave,
Since the amplitude fluctuation occurring in the output signal from the variable high-pass filter VHPF is negligibly small, in this case, the output signal from the variable high-pass filter VHPF is expressed by the above equations (5) and (6). Therefore, in such a case, the use of the limiter 10 may be omitted.

As is clear from equations (5) and (6) above, the output signal from the variable high-pass filter VHPF is phase-shifted by 90° with respect to the FM signal input thereto. Therefore, it is targeted for demodulation.
The FM signal is directly applied to the phase comparator 7 as one input signal, and the signal obtained by passing the FM signal to be demodulated through the variable high-pass filter VHPF is applied to the phase comparator 7 as the other input signal. Ba,
Since the phase comparator 7 can perform a phase comparison operation on the two input FM signals given to it, the variable high-pass filter VHPF
In the FM demodulation circuit using the phase tracking loop method of the present invention using as a tracking filter, the circuit layout is shown in the second diagram of the previously proposed circuit.
The Hilbert filter 5 required in the FM demodulation circuit is no longer necessary.

This point will be explained more specifically as follows. That is, according to the phase tracking loop system shown in the third figure of the present invention, which uses the variable high-pass filter VHPF having the functions as described above as a tracking filter.
The FM demodulation circuit can be expressed by a functional diagram shown by blocks P and Q as shown in FIG. 6a, and the above-mentioned FIG. However, in this Figure 6b, the part of the circuit layout on the right side from the position of the dashed-dotted line V-V in the drawing is substantially the same as the circuit layout shown in the already proposed second diagram. It is clear that they have the same function.
Even if the FM signal targeted for demodulation is e ^j Ω ^(t) , or the FM signal −je j Ω (t) obtained by shifting the phase of the above FM signal by −90°, the target for demodulation is e ^j Ω ^(t) . It goes without saying that the same FM demodulated signal can be obtained even if the

From the above explanation, it is clear that the FM demodulation circuit based on the PTL method of the present invention, which uses the variable high-pass filter VHPF as a tracking filter, does not contradict the basic configuration of PTL shown in previous proposals. Since it seems to be clear, the demodulation operation in the FM demodulation circuit of the present invention will be explained next.

First, it is necessary to find α in equation (6), which is the coefficient of phase modulation that occurs in the FM signal due to a change in the capacitance value of the variable capacitor C _X. The value of is calculated by considering the case where an unmodulated carrier wave is supplied as an input signal to the tracking filter while the tracking filter is being driven by the control signal f(t), and what happens to the output side of the tracking filter at that time. This can be determined by knowing whether an output signal appears, that is, by knowing what kind of modulation an unmodulated carrier wave given as an input signal undergoes to appear as an output signal.

_Therefore , now, the capacitance value C _{X of} the _variable capacitor C Variable high-pass filter when
Assume that the resonant frequency of the VHPF is ωc, which is equal to the frequency _ωc of the carrier wave of the FM signal, and the above-mentioned C≫Cx,
Under the condition of R≫L/(C+Cx)≒L/C, the above frequency _ωc is expressed as ωc=1/√(+)...(9) As shown by the above equation (9), the variable height If the transfer function T(jω, t) of the band pass filter is described, it is expressed as the following equation (10).

The above equation (10) is calculated by changing S to j in the above equation (1).
ω, and the numerator and denominator of equation (1) are respectively
Dividing by CL, we get the following formula (a), Next, Cx in equation (a) above is defined as Cx=Co+ΔCf
(t) as the following equation (b) and then the resonance condition ω of this variable high-pass filter
Using c=1/√(+), obtain formula (c), It can be obtained by inserting the condition C≫Co into the above equation (c).

Now, if the unmodulated carrier wave Cnm(t) applied to this variable high-pass filter VHPF is expressed by equation (11), then the output signal C'nm from the variable high-pass filter VHPF (t) is shown by equation (12).

Cnm(t)=e ^j 〓 ^ct ...(11) C′nm(t)=ej[ωct−tan−1{ΔCR・f(t)/L・〓〓〓}+(π/2)]… ...(12) Then, by appropriately selecting the values ΔC, R, Co, L, and C of each element constituting the variable high-pass filter VHPF, the following equation (13) is made to hold.
The value of α mentioned above is as shown in equation (14).

tan ^-1 {ΔCR・f(t)/L・√
} ≒ΔCR・f(t)/L・√ ...(13) α=ΔCR・f(t)/L・√ ...(14) Using the above study results, PTL shown in Figure 3
〓〓〓〓
For input terminal 1 of the FM demodulation circuit according to the method,
The demodulation operation of the FM demodulation circuit using the PTL method of the present invention when an FM signal as shown in equation (4) is supplied will be explained as follows.

That is, the FM signal e ^j {〓〓 ^t+ ∫〓〓 ⁽ 〓 ^)d 〓} supplied to the input terminal 1 and expressed by equation (4) is supplied as it is to the phase comparator 7 as one input signal, and It is given as an input FM signal to the variable high-pass filter VHPF.

Output signal C′ _p from variable high-pass filter VHPF
(t) is shown by the above-mentioned equation (6), but by substituting the value of α shown in the above-mentioned equation (14) for α in the above-mentioned equation (6), and The value of τ in formula (6) is set as τ=2C _X R=2C _p R {usually C _p
≫ΔC, so we can set C _X ≒ C _p ,
Therefore, it can be expressed as τ _{= 2C}
The FM signal C' _p (t) is expressed by the following equation (6a).

In the phase comparator 7, the FM signal C(t) shown by equation (4) and the FM signal C' _p shown by equation (6a)
(t) and the phase comparator 7
outputs a phase difference signal e _r (t) as shown by the following equation (15).

The nearly equal expression in equation (15) above focuses on the first term of the Taylor expansion of er(t) shown in the preceding line, and calculates sinX≒ when X is sufficiently small. This is obtained using the relationship of X.

The phase difference signal e _r output from the phase comparator 7
(t) is sent to the output terminal 4 as an FM demodulated signal f(t) via the loop filter 8 and the loop amplifier 9, and is also supplied as a control signal f(t) to the variable high-pass filter VHPF. be done.

Assuming that the characteristic of the loop filter 8 is G(S) and the amplification degree of the loop amplifier 9 is A, the phase difference signal and
Expressing the relationship of the FM demodulated signal f(s) using a Laplace transform type, the following equation (16) is obtained.

Solving the above equation (16), we get A demodulation equation as shown in equation (17) is obtained.

As is clear from this equation (17), the present invention
The FM demodulated signal obtained from the FM demodulation circuit using the PTL method is converted into a modulated signal μ(S). It is equivalent to applying a linear filter having a transfer function as shown in equation (18). Therefore, equation (17) shows that the FM demodulation circuit using the PTL method of the present invention has an FM demodulation function. It's proven.

Figure 7 shows an example in which a variable inductor _LX is used as a variable reactance element among the constituent elements of a variable high-pass filter VHPF.In this case, a capacitor _CX is replaced with a capacitor Connect C _a .

In addition, in implementing the present invention, a variable high-pass filter
The element whose reactance should be varied by the control signal in the VHPF is either a variable capacitance diode or a variable inductor, as in the embodiments shown in FIGS. 3 and 7. A variable high pass filter may be used so that both are used at the same time.
It goes without saying that a VHPF may be configured, and in any of the above cases, the
The FM demodulation operation can be performed successfully in the same manner as described in detail in the example.

As is clear from the detailed explanation above, in the FM demodulation circuit using the PTL method of the present invention,
By using the variable high-pass filter as a tracking filter, the Hilbert filter that was required in the conventional PTL-based FM demodulation circuit described above is not required, and the variable high-pass filter has a simple configuration. Moreover, it is extremely easy to design a circuit that can operate well in a high frequency region, so the FM demodulation circuit using the PTL method of the present invention satisfactorily solves all the problems of the previously proposed circuits. It can be done.

In addition, the FM demodulation circuit using the PTL method of the present invention can perform FM demodulation operation with excellent interference rejection characteristics against noise and interference waves.
Abnormal overmodulation noise that occurs in the case of FM detection using the PTL method does not occur, and furthermore,
When receiving FM broadcasts, the problem of worsening demodulation distortion when slightly detuned from the broadcast reception tuning point, which was common with conventional ratio detection and quadrature air detection, can be solved by the FM demodulation using the PTL method of the present invention. The circuit has various excellent features, such as the ability to expect significant improvements through the effects of negative feedback control.

[Brief explanation of the drawing]

Figure 1 is a block diagram explaining the principle of an FM demodulation circuit using the PTL system, Figure 2 is a block diagram of an FM demodulation circuit using the previously proposed PTL system, and Figures 3 and 7 are FM demodulation circuits using the PTL system of the present invention. A block diagram of each different embodiment of the demodulation circuit, FIG. 4 is a configuration example diagram of a variable high-pass filter, FIG. 5 is a curve diagram of frequency response characteristics and phase characteristics of the variable high-pass filter, and FIG. 6 a , b are equivalent circuit diagrams of the circuit arrangement shown in the third figure. 1...Input terminal, 3...FM demodulator, 4...Output terminal, 5...Hilbert filter, 2, 6...
Variable band filter, 7... Phase comparator, 8... Loop filter, 9... Loop amplifier, 10... Limiter, VHPF... Variable high-pass filter. 〓〓〓〓

Claims (1)

[Claims] 1. FM signal to be demodulated is input to one side.
means for applying an FM signal to the phase comparator; a high resonant peak with the cutoff frequency as the resonant frequency; and the resonant frequency is determined according to a control signal externally applied to the variable reactance element in the component. means for supplying an FM signal to be demodulated to a variable high-pass filter having a secondary characteristic that is configured to be changed;
The other input of the FM signal to the phase comparator mentioned above.
means for providing the FM signal as an FM signal; means for extracting the phase difference signal output from the phase comparator as an FM demodulated signal via a loop filter and loop amplifier; and sending the FM demodulated signal to the variable high-pass filter. An FM demodulation circuit using a phase tracking loop method and equipped with a means to provide it as a control signal. 2 Assuming that the amplitude of the output signal of the variable high-pass filter is constant, the other input FM is input to the phase comparator.
Claim 1 given as a signal
FM demodulation circuit using the phase tracking loop method described in . 3. Either a variable capacitance diode or a voltage-controlled variable inductor is used as a variable reactance element in the constituent elements of a variable high-pass filter with secondary characteristics whose resonant frequency is changed according to a control signal. An FM demodulation circuit using a phase tracking loop method according to claim 1, which uses one or both of the above.