JPH0251814B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION [Industrial Application Field] The present invention relates to an electromagnetic vibration type parts feeder, and particularly to a vibration control system suitable for controlling electromagnetic vibration of the parts feeder.

[Prior art]

Conventionally, in this type of vibration control system,
For example, as disclosed in Japanese Patent Application Laid-Open No. 57-27808, the gap between the movable iron core and the fixed iron core that changes according to the amplitude change of the vibration of the movable iron core of the electromagnet provided in the parts feeder is Some devices detect this as a change in the amount of light and control the current flowing into the electromagnet in a feedback phase based on a signal current corresponding to the change in the detected amount of light to keep the amplitude of the current flowing into the electromagnet constant.

[Problem that the invention seeks to solve]

However, in such a configuration, as mentioned above, the current flowing into the electromagnet is only subjected to feedback phase control, so for example, when the load on the parts feeder fluctuates, the vibration amplitude of the parts feeder becomes unstable. This causes a problem in that the parts feeder cannot properly vibrate and supply various parts, etc. Further, when the above-mentioned inflow current is not a sine wave but includes a high-order harmonic component, there is also a problem that the parts feeder generates vibration noise when it vibrates due to the harmonic component.

Therefore, in order to deal with the above-mentioned problems, the first invention provides an electromagnetic vibration type parts feeder that includes:
The present invention aims to provide a vibration control system that constantly maintains the vibration amplitude stably and appropriately.

In addition, in order to deal with the above-mentioned problems, the second invention is such that the vibration amplitude of the electromagnetic vibration parts feeder is always maintained stably and appropriately using a sine wave with sufficient power. The present invention aims to provide a vibration control system.

[Means for solving problems]

In order to solve this problem, the structural features of the first invention include an elastic mechanism placed on a base surface, a parts feeder main body supported by the elastic mechanism, and an electromagnetic coil. In an electromagnetic vibration type parts feeder comprising an electromagnet that mechanically vibrates the parts feeder main body under the repulsive action of the repulsive mechanism in response to excitation, the vibration state of the parts feeder main body is detected as a vibration detection signal. a converting means for converting the vibration detection signal into a displacement signal representing the displacement of the parts feeder main body; and a control means for controlling the frequency of the alternating current signal so that the phase difference between the phase of the alternating current signal and the phase of the displacement signal becomes a predetermined value.

In order to solve the above-mentioned problem, the structural features of the second invention include an elastic mechanism placed on the base, a parts feeder body supported by the elastic mechanism, and an electromagnetic coil. An electromagnetic vibrating parts feeder comprising an electromagnet that mechanically vibrates the parts feeder main body under the repelling action of the repulsive mechanism in response to excitation of an electromagnetic coil,
a detection means for detecting the vibration state of the parts feeder body and generating it as a vibration detection signal; a conversion means for converting the vibration detection signal into a displacement signal representing a displacement of the parts feeder body; and driving the electromagnet in accordance with the displacement signal. control means for generating an alternating current signal necessary for the purpose of the present invention and controlling the frequency of the alternating current signal so that a phase difference between the phase of the alternating signal and the phase of the displacement signal is a predetermined value; and a control means for generating a series of carrier wave pulse signals. a carrier wave pulse signal generating means for generating a modulated pulse signal by modulating the signal width of each of the carrier wave pulse signals with the alternating current signal and sequentially generating a modulated pulse signal; semiconductor switching means that performs a switching action in response to a change in signal level and sequentially generates a power amplification pulse signal having the same phase and the same waveform as each of the modulated pulse signals; The present invention is further provided with a sine wave signal generating means for extracting the signal, generating it as a sine wave signal, and applying it to the electromagnet.

[Effect]

By configuring the first invention as described above, when the resonant frequency of the parts feeder body fluctuates due to a change in the weight of the parts etc. accommodated in the parts feeder body or deterioration of the elastic mechanism, the control Means controls the frequency of the alternating current signal in order to change the phase of the alternating current signal so as to satisfy the predetermined value, following a change in the phase of the displacement signal generated by the converting means in cooperation with the detecting means. Therefore, this AC signal is applied to the electromagnet while maintaining a large amplitude and making its frequency match the fluctuating resonant frequency of the parts feeder main body.

Therefore, the parts feeder main body can always vibrate stably and appropriately at this fluctuating resonance frequency despite fluctuations in its resonance frequency, and as a result, the parts feeder can always vibrate and supply parts etc. It can be done properly. In such a case, as described above, the parts feeder main body always vibrates at this fluctuating resonant frequency despite fluctuations in its resonant frequency, so the strength and weight of the parts feeder main body, as well as the The strength of the repelling mechanism can be reduced to the necessary minimum, and as a result, it is possible to significantly improve the compactness, weight reduction, and cost reduction of this type of parts feeder, and to reduce the strength of the parts feeder body at the frequency of the alternating current signal. There is no need for adjustment to match the resonant frequency of.

Further, by configuring the second invention as described above, when the resonant frequency of the parts feeder body fluctuates due to a change in the weight of the parts etc. accommodated in the parts feeder body or deterioration of the elastic mechanism, the control means controls the frequency of the alternating current signal to change the phase of the alternating current signal so as to satisfy the predetermined value in accordance with a change in the phase of the displacement signal generated by the converting means in cooperation with the detecting means; The signal width modulating means generates a modulated pulse signal by modulating the signal width of each carrier wave pulse signal from the carrier wave pulse signal generating means using the frequency-controlled AC signal, and the semiconductor switching means modulates the signal width of each carrier wave pulse signal from the carrier wave pulse signal generating means, and the semiconductor switching means modulates the signal width of each carrier wave pulse signal from the carrier wave pulse signal generating means. The modulated pulse signal is power amplified to generate a power amplified pulse signal based on the power supplied from The wave signal is applied to the electromagnet while maintaining a large amplitude and a large power while matching its frequency to the fluctuating resonant frequency of the parts feeder main body. Therefore, the parts feeder main body can always vibrate stably and properly in a sinusoidal manner with sufficient power even at this fluctuating resonant frequency, despite fluctuations in its resonant frequency, and as a result, the first Not only can the same effects as the invention of the above invention be achieved, but also the parts feeder main body does not generate noise due to harmonics.

〔Example〕

Hereinafter, one embodiment of the present invention will be described with reference to the drawings. FIG. 1 shows that the vibration control system according to the present invention is
An example is shown in which the parts feeder 10 is applied to an electromagnetic vibration type parts feeder 10, in which the parts feeder body 13 is supported above the base 11 by a pair of leaf springs 12, 12 so as to be able to vibrate in the vertical direction. An electromagnet 14 is interposed between the parts feeder body 13 and the parts feeder main body 13. The electromagnet 14 has a fixed iron core 14a fixed on the base 11.
, a flat movable core 14b fixed to the bottom wall of the parts feeder body 13 from the outside so as to face each magnetic pole of the fixed core 14a, and this movable core 1.
4b and an electromagnetic coil 14c wound around the central magnetic pole of the fixed core 14a, and between each magnetic pole of the fixed core 14a and the movable core 14b, there is a predetermined gap necessary to ensure proper vibration of the parts feeder main body 3. It is formed. Further, in this embodiment, when the parts feeder 10 is in a steady state, the parts feeder main body 13 and the movable iron core 14b have resonance characteristics at a predetermined mechanical resonance frequency due to the relationship with the spring characteristics of each leaf spring 12, 12.

The vibration control system includes an acceleration sensor 20, an acceleration-displacement conversion circuit 30 connected to the acceleration sensor 20, and a phase-locked loop circuit 40 (hereinafter referred to as a PLL circuit 4) connected to the acceleration-displacement conversion circuit.
0), and the acceleration sensor 20 is
It is fixed to the opening of the parts feeder main body 13,
The vibration acceleration of the parts feeder main body 13 is detected and generated as an acceleration detection signal. The acceleration-displacement conversion circuit 30 is composed of an integrating circuit 31 connected to the acceleration sensor 20, an integrating circuit 32 connected to the integrating circuit 31, and a linear amplifier 33 connected to the integrating circuit 32. 31 integrates the value of the acceleration signal from the acceleration sensor 20 and generates this as a speed signal representing the vibration speed of the parts feeder main body 13. Integrating circuit 32
integrates the value of the speed signal from the integrating circuit 31 and generates this as a displacement signal representing the vibrational displacement of the parts feeder main body 13. The linear amplifier 33 phase inverts and amplifies the displacement signal from the integrating circuit 32 and generates it as an amplified displacement signal.

The PLL circuit 40 has a phase discrimination circuit 41, and this phase discrimination circuit 41 is connected to the linear amplifier 33.
The phase difference φ (=φ1−φ2) between the phase φ1 of the amplified displacement signal from the phase shifter 44 and the phase φ2 of the phase shift signal generated from the phase shifter 44 as described later is discriminated, and a duty ratio proportional to this phase difference φ is determined. Generates a square wave pulse signal. In such a case, the phase difference φ is zero degrees, -90 degrees and -
At 180 degrees, the duty ratio is 0%,
50% and 100%. The integration circuit 42 is a PLL
The circuit 40 functions as a so-called charge pump circuit, integrates the square wave pulse signal from the phase discrimination circuit 41, and generates an integrated voltage at a level corresponding to the result of this integration. In such a case, when the duty ratio of the square wave pulse signal is 50%, the level of the integrated voltage does not change, and when the duty ratio is larger (or smaller) than 50%, the level of the integrated voltage increases (or decreases). do. Also, 50
% duty ratio corresponds to phase difference φ = 0, 50%
The larger (or smaller) duty ratio is φ>0
(or φ<0).

Voltage controlled oscillator circuit 43 responds to the integrated voltage from integrating circuit 42 and generates an alternating current signal at a frequency proportional to the level of this integrated voltage. In such case,
Control is performed so that when the level of the integrated voltage does not change, the frequency of the AC signal does not change, and when the level of the integrated voltage increases (or decreases), the frequency of the AC signal increases (or decreases).
In response to the AC signal from the voltage controlled oscillation circuit 43, the phase shifter 44 shifts the phase of the AC signal by a predetermined phase (for example, 90 degrees) to the lag side and generates this as a phase shift signal. This means that the phase discrimination circuit 4
This means that the difference between the phase of the amplified displacement signal from the linear amplifier 33 and the phase shift signal from the phase shifter 44 applied to the phase shifter 44 is -90 degrees. In other words, this means that the phase of the amplified displacement signal from the linear amplifier 33 and the voltage controlled oscillation circuit 43
This means that the phases of the AC signals from

The vibration control system also includes a pulse signal generation circuit 50 and a pulse width modulation circuit 6 connected to the pulse signal generation circuit 50 and the voltage controlled oscillation circuit 43.
0, a distribution circuit 70 connected to this pulse width modulation circuit 60, a power supply circuit 80, and this current circuit 80.
and a power amplifier circuit 80 connected to the distribution circuit 70
The pulse signal generating circuit 50 generates a series of pulse signals at a predetermined frequency higher than the audible frequency.

The pulse width modulation circuit 60 modulates the signal width of each pulse signal from the pulse signal generation circuit 50 using the AC signal from the voltage controlled oscillation circuit 43, and generates the result of this modulation as a pulse width modulation signal. In such a case, the degree of modulation in the signal width of this pulse width modulated signal changes depending on the alternating current signal. Distribution circuit 7
0 generates the first distribution signal and simultaneously eliminates the second distribution signal when the pulse width modulation signal from the pulse width modulation circuit 60 is at low level, and eliminates the first distribution signal when the pulse width modulation signal is at high level. At the same time, a second distribution signal is generated.

The power supply circuit 80 rectifies and smoothes an alternating current voltage from a commercial power source, and generates a direct current voltage between its output terminals 81 and 82. The power amplification circuit 90 includes field effect transistors 91 to 94 (hereinafter referred to as FETs 91 to 9).
4), diodes 95 to 98, and a capacitor 99, both FETs 91 and 94 are connected to the distribution circuit 70 at their respective gate terminals to receive the first distribution signal from the distribution circuit 70, and
The FETs 92 and 93 are connected to the distribution circuit 70 at their respective gate terminals to receive the second distribution signal from the distribution circuit 70. Also, both FET91,9
3 are connected to the output terminal 81 of the power supply circuit 80 at their respective source terminals, while both FETs 92,
94 connects each FET 91, 93 at each source terminal.
and are connected to the output terminal 82 of the power supply circuit 80 at each drain terminal.

Therefore, both FETs 91 and 94 are connected to the distribution circuit 70.
When both become conductive in response to the first distribution signal from
The drain terminal of the FET 91 has approximately the same potential as the output terminal 81 of the power supply circuit 80, and the source terminal of the FET 94 has approximately the same potential as the output terminal 82 of the power supply circuit 80. On the other hand, both FETs 92 and 93 are connected to the distribution circuit 70.
When both become conductive in response to the second distribution signal from
The drain terminal of the FET 93 has approximately the same potential as the output terminal 81 of the power supply circuit 80, and the source terminal of the FET 92 has approximately the same potential as the output terminal 82 of the power supply circuit 80. In other words, the first and second distribution signals from the distribution circuit 70 are generated alternately in relation to the low level and high level of the pulse width modulation signal from the pulse width modulation circuit 60, so that both FETs 91, 94 and Since both FETs 92 and 93 are made conductive alternately, both
The signal generated between FETs 92 and 94 is transmitted to the power supply circuit 80.
The pulse width modulated signal from the pulse width modulation circuit 60 is power amplified using the DC voltage and DC power from the pulse width modulation circuit 60, resulting in a power amplified pulse signal having the same phase and the same waveform as the same pulse width modulation signal.

Both diodes 95 and 96 have their cathodes connected to the source terminals of FETs 91 and 92, respectively, and the anodes of these diodes 95 and 96 are connected to the drain terminals of FETs 91 and 92, respectively. Also, both diodes 9
7 and 98 are each FET93 and 9 at each cathode.
The anodes of both diodes 93 and 94 are connected to the source terminals of diodes 93 and 94, respectively.
Connected to the drain terminals of FETs 93 and 94, respectively. Therefore, both diodes 95 and 98
The coil 101 and electromagnetic coil 14 of the low-pass filter 100 are electrically conductive in response to each conduction of the FETs 92 and 93 to protect both FETs 91 and 94.
Capacitor 99 receives each back electromotive force generated at c.
(connected between both output terminals 81 and 82 of power supply circuit 80). Also, both diodes 9
FETs 2 and 93 are made conductive in response to the conduction of both FETs 91 and 94, respectively, and charge the capacitor 99 by receiving the counter electromotive force of the coil 101 and the electromagnetic coil 14c while protecting both FETs 92 and 93. This means that each of the diodes 95 to 98 has a power regeneration function in cooperation with the capacitor 99.

The low-pass filter 100 filters out components other than the low frequency components (for example, frequency components of 500 Hz or more) of the power amplification pulse signal from the power amplification circuit 90 based on the cooperative filter function of the coil 101 and the capacitor 102. A sine wave filter signal is generated based on the frequency component and applied to the electromagnetic coil 14c via the diode 110. This means that the electromagnetic coil 14c is excited under the half-wave rectification effect of the diode 110 in response to a sinusoidal change in the filter signal from the low-pass filter 100, thereby attracting the movable iron core 14b to the fixed iron core 14a. The coil 101 generates a back electromotive force in response to a power amplification pulse signal from the power amplification circuit 90, and the electromagnetic coil 14c generates a back electromotive force in response to a filter signal from the low-pass filter 100.

In this embodiment configured as described above, the parts feeder main body 13 housing various parts receives the action of the electromagnet 14 while the power supply circuit 80 is generating DC voltage in cooperation with the commercial power supply. If it is assumed that the parts feeder main body 13 is vibrating in a steady state, the acceleration sensor 20 detects the vibration acceleration of the parts feeder main body 13 and generates an acceleration detection signal (symbol a1 in FIG. 2).
), the integrating circuit 31 integrates the value of the acceleration detection signal and generates it as a speed signal, the integrating circuit 32 integrates the value of the same speed signal and generates it as a displacement signal, and the linear amplifier 33 integrates the value of the acceleration detection signal and generates it as a displacement signal. The signal is phase inverted and amplified to produce an amplified displacement signal (sign b1 in Figure 2).
(see) occurs.

When the phase shifter 44 generates a phase shift signal (see symbol c1 in FIG. 2) in such a state, the phase discrimination circuit 41 generates an amplified displacement signal from the linear amplifier 33 and a phase shift signal from the phase shifter. Accordingly, a square wave pulse signal (see reference numeral d1 in FIG. 2) is generated at a duty ratio proportional to the phase difference between these two signals. In this case, since the parts feeder 10 is in a steady state, the duty ratio of the square wave pulse signal from the phase discrimination circuit 41 is 50%. Next, the integrator circuit 42 integrates the square wave pulse signal from the phase discrimination circuit 41 and obtains a level corresponding to the result of this integration (at present, it is a zero level as shown by symbol e1 in FIG. 2). An integrated voltage is generated at .

When an integrated voltage is generated from the integrating circuit 42 in this way, the voltage controlled oscillator circuit 43 generates an AC signal (symbol f1 in FIGS. 2 and 3) at the same frequency as the amplified displacement signal from the linear amplifier 33 at the current stage. The pulse width modulation circuit 60 modulates the signal width of each pulse signal from the pulse signal generation circuit 50 with the AC signal from the voltage controlled oscillation circuit 60, and generates a pulse width modulation signal (sign g1 in FIG. 3). ), the distribution circuit 70 generates a first distribution signal when the pulse width modulation signal from the pulse width modulation circuit 60 is at a low level, and generates a second distribution signal when the pulse width modulation signal is at a high level. do.

Therefore, both FETs 91 of the power amplifier circuit 90,
94 are turned on in response to the first distribution signal from the distribution circuit 70 while both FETs 92 and 93 are non-conducting, while both FETs 92 and 93 are turned on when both FETs 91 and 9 are turned off.
In response to the second distribution signal from the distribution circuit 70, both of the circuits 4 and 4 become conductive. In other words, the power amplifier circuit 90 performs pulse width modulation from the pulse width modulation circuit 60 based on the DC voltage and DC power from the power supply circuit 80 by alternately conducting both FETs 91 and 94 and both FETs 92 and 93 as described above. A power amplified pulse signal (see reference numeral h1 in FIG. 3) having the same waveform and phase as the signal is generated from between each drain terminal of both FETs 91 and 93. Then, the low-pass filter 100 generates a sine wave filter signal (see reference numeral i1 in FIG. 2) in response to the power amplification signal from the power amplification circuit 90.

When a filter signal is generated from the low-pass filter 100 in this way, the electromagnetic coil 14c is excited by the filter signal in cooperation with the diode 110, and the movable iron core 14b and the parts feeder main body 13 are moved to the fixed iron core in response to the excitation of the electromagnetic coil 14c. Each leaf spring 12, 12 by cooperation with 14a
It vibrates in the vertical direction in relation to the spring characteristics of. In such a case, as described above, the voltage controlled oscillation circuit 43
Since the phase of the AC signal from the linear amplifier 33 and the phase of the amplified displacement signal from the linear amplifier 33 match each other,
When the frequency of the alternating current signal matches the mechanical resonance frequency, the vibration amplitude of the parts feeder body 13 reaches its maximum as shown in FIG. 4.

Further, as described above, the pulse width modulation circuit 60 forms a pulse width modulation signal based on the AC signal from the voltage controlled oscillation circuit 43, and the DC voltage and DC power from the power supply circuit 80 are controlled based on this pulse width modulation signal. In addition, the power amplification circuit 90 forms a power amplification pulse signal, and the low-pass filter 100 forms a filter signal based on this power amplification pulse signal. It has electric power and a sine wave. Therefore,
Since the electromagnetic coil 14c is excited by a filter signal having the same frequency as the resonant frequency, large power, and a sine wave, the parts feeder body 13 always has a high power maximum amplitude under the resonant frequency. It will perform sine wave vibration,
As a result, the parts feeder of this type can vibrate and supply parts appropriately and smoothly without any noise caused by high frequency waves.

Further, as described above, when the low-pass filter 100 is given a power amplification pulse signal from the power amplification circuit 90 and the electromagnetic coil 14c is given a filter signal from the low-pass filter 100 via the diode 110, the coil 101 and the electromagnetic coil Each back electromotive force generated in 14c is connected to both diodes 9
5, 98 or both diodes 96, 97 to provide regeneration to the capacitor 99.
to charge. As a result, the charging energy of this capacitor 99 is donated to the generation of a power amplification signal in the power amplification circuit 90 while improving the power factor, and as a result, it is possible to achieve power saving in this type of vibration control system.

In addition, in such a state, time t = T1 (second
When the weight of various parts accommodated in the parts feeder main body 13 increases, the mechanical resonance frequency decreases, and the value of the acceleration signal from the acceleration sensor 20 (see symbol a2 in FIG. 2) decreases. The value of the amplified displacement signal from the acceleration-displacement conversion circuit 30 (see reference numeral b2 in FIG. 2) decreases, and the phase shift of the amplified displacement signal from the linear amplifier 33 becomes the phase shift signal from the phase shifter 44. (See code c2 in Figure 2)
, the duty ratio of the square wave pulse signal from the phase discriminator circuit 41 (see symbol d2 in FIG. 2) decreases, and the value of the integral signal from the integrating circuit 42 (see symbol e2 in FIG. 2) decreases. decreases, and the AC signal from the voltage controlled oscillation circuit 43 (signed f in FIG. 2)
2) decreases, and the pulse width modulation circuit 6
The degree of modulation of the pulse width modulated signal from 0 (that is, the power amplified pulse signal from the power amplifier circuit 90) decreases, and the frequency of the filter signal from the low-pass filter 100 (see symbol i2 in FIG. 2) decreases. do.

However, since the phase of the phase shift signal from the phase shifter 44 is delayed so as to approach the phase of the amplified displacement signal from the linear amplifier 33 in accordance with the decrease in the frequency of the AC signal from the voltage controlled oscillation circuit 43, the phase discrimination circuit 4
A square wave pulse signal from 1 (sign d3 in Fig. 2)
) increases, the level of the integral signal from the integrating circuit 42 (see symbol e3 in FIG. 2) increases, and the level of the AC signal from the voltage controlled oscillation circuit 43 (see symbol f3 in FIG. 2) increases. ) increases, and the frequency of the filter signal from the low-pass filter 100 (see reference numeral i3 in FIG. 2) increases.

As described above, even if the mechanical resonance frequency temporarily decreases due to an increase in the weight of parts accommodated in the parts feeder main body 13, the phases of the amplified displacement signal and phase shift signal to the phase discrimination circuit 41 are The phase difference is controlled to decrease and approach -90 degrees, and the frequency of the filter signal to the electromagnetic coil 14c is made to match the above-mentioned reduced resonance frequency of the parts feeder body 13, so that the parts feeder body 13 is controlled to reduce its resonance. Despite the decrease in frequency, sinusoidal vibration is performed at the maximum amplitude of high power as described above under this decreased resonance frequency,
As a result, the vibration supply of parts by this type of parts feeder can be performed appropriately and smoothly without noise caused by harmonics, by automatically adjusting the excitation frequency of the electromagnet 14 to the reduced resonance frequency of the parts feeder. It can be done. Furthermore, the automatic frequency matching function described above greatly improves the compactness, weight, and cost of the parts feeder.

In addition, in the above-mentioned action, the case where the resonant frequency of the parts feeder main body 13 decreases is described, but this is not limited to this, and the above-mentioned action and effect description is substantially the same even when the resonant frequency of the parts feeder main body 13 increases. can achieve the following effects. Further, the factor of variation in the resonant frequency of the parts feeder body 13 is not limited to variation in the weight of parts accommodated in the parts feeder body 13, but also
Even in the case of elastic fatigue, etc., the same effects as described above can be achieved.

Next, a modification of the above embodiment will be described with reference to FIG. 5. In this modification, a rectifier circuit 120 connected to a linear amplifier 33, a potentiometer 130, a rectifier circuit 120 and a potentiometer a comparison circuit 140 connected to 130;
Integrating circuit 150 connected to this comparison circuit 140
The structure is characterized by the fact that it further employs a multiplier 160 connected to the integrating circuit 150 and between the voltage controlled oscillation circuit 43 and the pulse width modulation circuit 60.

The rectifier circuit 120 rectifies the amplified displacement signal from the linear amplifier 33 to generate a rectified signal. The potentiometer 130 is operated to generate a setting signal when setting the vibration amplitude of the parts feeder body 13 to a desired value. The comparator circuit 140 determines that the level of the setting signal from the potentiometer 130 is equal to the level of the rectifier circuit 12.
Higher (or lower) than the level of the rectified signal from 0
A comparison signal is generated at high level (or low level). Integrating circuit 150 integrates in response to the rise (or fall) of the comparison signal from comparator circuit 140 and generates an integrated signal. The multiplier 160 has a variable gain K (0<K<1) that changes in proportion to the level of the integrated signal from the integrating circuit 150.
This multiplier 160 multiplies the amplitude of the AC signal from the voltage controlled oscillation circuit 43 by the level of the integral signal from the integrating circuit 150 in accordance with a variable gain K, and generates the multiplication result as a multiplication signal.
be granted to

Therefore, in this modified example configured in this way, if the level of the setting signal from the potentiometer 130 is adjusted to a desired value in advance, the rectification generated by the rectification circuit 120 in cooperation with the linear amplifier 33 can be adjusted. The comparison circuit 140 generates a comparison signal according to the signal and the setting signal from the potentiometer 130, the integration circuit 150 generates an integral signal in relation to the comparison signal, and the multiplier 160 generates an integral signal from the voltage controlled oscillation circuit 43. AC signal and integration circuit 150
A multiplication signal is generated based on the integral signal from. In this case, the phase of the multiplication signal from the multiplier 160 is the same as the phase of the AC signal from the voltage controlled oscillation circuit 43, and the amplitude of the multiplication signal causes the vibration amplitude of the parts feeder main body 13 to match the desired value. The value has become such that

Based on the multiplied signal from the multiplier 160, a pulse width modulation signal from the pulse width modulation circuit 60, a power amplification signal from the power amplification circuit 90, and a filter signal from the low pass filter 100 are substantially different from those in the previous embodiment. When similarly occurring, the parts feeder main body 13 is subjected to a large electric power at the mechanical resonance frequency as in the previous embodiment in cooperation with the electromagnet 14 which responds to the filter signal from the low-pass filter 100 via the diode 110. Of course, this parts feeder body 13 vibrates in normal waves.
The vibration amplification of can be constantly adjusted to a value corresponding to the level of the set signal from potentiometer 130.
This means that the vibrational supply of parts by the parts feeder 10 not only has the same effects as in the embodiment described above, but also can be done properly and smoothly at all times with just the right vibration amplitude of the parts feeder 10. means.

In the above embodiment, an example was explained in which the frequency of the pulse signal from the pulse signal generation circuit 50 was specified, but this pulse signal generation circuit 5
By variably adjusting the frequency of the pulse signal from 0, the vibration characteristics of the parts feeder main body 13 can be adjusted appropriately by changing the frequency of the filter signal from the low-pass filter 100 as necessary.

Further, in the above embodiment, an example was explained in which the delay phase value by the phase shifter 44 was 90 degrees, but
Without being limited to this, the parts feeder main body 1 can be modified by appropriately changing the delay phase value as necessary.
The vibration amplitude of 3 may be changed.

Further, in the above embodiment, an example was explained in which the system of the present invention is used for half-wave drive, but instead, when the system of the present invention is used for full-wave drive, the diode 110 is deleted and the linear A frequency dividing circuit (having a 1/2 frequency dividing function) may be connected between the amplifier 33 and the phase discrimination circuit 41.

[Brief explanation of drawings]

FIG. 1 is a block diagram showing one embodiment of the present invention;
Figure 2 is an input/output waveform diagram of each element in Figure 1,
FIG. 3 is a partially enlarged view of the same, FIG. 4 is a characteristic diagram showing the phase of the output of the PLL circuit and the vibration amplitude of the parts feeder, and FIG. 5 is a block diagram showing a modification of the above embodiment. Explanation of symbols, 10...Parts feeder, 11...
... Base, 12 ... Leaf spring, 13 ... Parts feeder main body, 14 ... Electromagnet, 14c ... Electromagnetic coil, 30 ... Acceleration-displacement conversion circuit, 40 ...
PLL circuit, 50...Pulse signal generation circuit, 60
... Pulse width modulation circuit, 70 ... Distribution circuit, 80
...Power supply circuit, 90...Power amplifier circuit, 100...
...Low pass filter, 110...diode.

Claims (1)

[Scope of Claims] 1. A repellent mechanism placed on a base surface, a parts feeder main body supported by the repulsive mechanism, and an electromagnetic coil, and in response to excitation of the electromagnetic coil, the parts feeder main body An electromagnetic vibrating parts feeder comprising an electromagnet that mechanically vibrates under the repulsive action of an elastic mechanism, a detection means for detecting the vibration state of the parts feeder body and generating a vibration detection signal, and the vibration detection signal. converting means for converting the signal into a displacement signal representing the displacement of the parts feeder main body, and generating an alternating current signal to be applied to the electromagnet according to the displacement signal, and a phase difference between the phase of the alternating current signal and the phase of the displacement signal. 1. A vibration control system for an electromagnetic vibration type parts feeder, characterized in that a control means is provided for controlling the frequency of the alternating current signal so that the frequency of the alternating current signal is set to a predetermined value. 2. A repellent mechanism placed on a base surface, a parts feeder main body supported by the repulsive mechanism, and an electromagnetic coil, and in response to the excitation of the electromagnetic coil, the parts feeder main body is moved by the elastic repulsion of the elastic mechanism. In an electromagnetic vibrating parts feeder equipped with an electromagnet that mechanically vibrates under action, a detection means detects the vibration state of the parts feeder body and generates a vibration detection signal, and a detection means that detects the vibration state of the parts feeder body and generates a vibration detection signal; converting means for converting into a displacement signal representing a displacement signal, and generating an alternating current signal necessary for driving the electromagnet according to the displacement signal, and setting a phase difference between the phase of the alternating current signal and the phase of the displacement signal to a predetermined value. a control means for controlling the frequency of the alternating current signal, a carrier wave pulse signal generating means for generating a series of carrier wave pulse signals, and a signal width of each of the carrier wave pulse signals is modulated by the alternating current signal to sequentially generate a modulated pulse signal. and a signal width modulation means that performs a switching action in response to level changes of each of the modulated pulse signals under the power supplied from the DC power source, and generates a power amplified pulse signal having the same phase and the same waveform as each of the modulated pulse signals. The invention is characterized in that it includes a semiconductor switching means that sequentially generates signals, and a sinusoidal signal generating means that extracts a low frequency component from the frequency components of each power amplification pulse signal, generates it as a sinusoidal signal, and applies it to the electromagnet. Vibration control system for electromagnetic vibration type parts feeder.