JPH0566071B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention relates to a television synchronization receiver that can be used in television receivers and VTR video tuners.

Conventional configurations and their problems In recent years, so-called electronic tuners, which use variable capacitance diodes and inductors as tuning elements, have been widely used in television receivers and VTR video tuners. Electronic tuners have advantages such as being non-contact, so there is no problem of contact failure, and being electronically controllable, making it convenient for multi-functionality such as remote control. However, because the characteristics of the variable capacitance diodes are not uniform and because an inductor is required for tuning, the characteristics as designed cannot be obtained, and it is difficult to make adjustments and automate manufacturing.

Therefore, the inventor of the present application has already invented a television synchronization receiver to which the Costas loop is applied, as an alternative to a receiver using a tuning circuit using a variable capacitance diode and an inductor.

This conventional television synchronization receiver will be explained below with reference to the drawings. FIG. 1 is a main part block diagram showing the configuration of a conventional television synchronization receiver. 1 is a high frequency input section, 2 is a first synchronous detector, 3 is a second synchronous detector, 4 is a first low-pass filter, 5 is a second low-pass filter, 6 is a first signal amplifier, 7 is a second signal amplifier, 3 is a phase comparator, 9 is a third low-pass filter, 10 is a voltage adder, 11 is a voltage controlled oscillator, 12 is a 90° phase shifter,
13 is a channel selection voltage generator, and 14 is a video signal filter.

The operation of the television synchronized receiver configured in this manner will be described below. Let vi(t) be the video carrier signal of the desired channel input to the high frequency input section 1. Since vi(t) is modulated by residual sideband, vi(t)=Re{[I(t)+jQ(t)]expj[ωit+i]} =I(t)cos(ωit+ψi)− Q(t)sin(ωit+i)...(1) Here, Re indicates the real part of the expression in { }.
I(t) is a signal having an in-phase component with respect to the carrier wave, and includes a video signal. Q(t) is a signal of a component orthogonal to the carrier wave, ωi is the angular frequency of the video carrier wave, and i is the phase of the video carrier wave. This vi(t) is applied to one terminal of the first synchronous detector 2 via the high frequency input section 1.

The output of the voltage controlled oscillator 11 is vo(t)=Ao cos(ωot+o)...(2) When this is applied to the other terminal of the first synchronous detector 2 consisting of a voltage multiplier, the output v〓 (t)
is v _I (t)=vi(t)・vo(t) =AoI(t)/2 {cos[ωi+ωo]t+i+o] +cos[(ωi−ωo)t+i−o]} −AoQ(t)/2 {sin [(ωi+ωo)]t+i+o
] +sin [(ωi−ωo)t+i−o]}……(3). When the voltage controlled oscillator output is synchronized with the video carrier wave, ωo = ωi, so v _I (t) = AoI (t)/2{cos (2ωit + ψi + ψo
) +cos(i−o)}−AoQ(t)/2{sin(2ω
it+i+o)+sin(i-o)}...(4) When the 2ωi signal is removed by low-pass filter 4, v _I (t)=AoI(t)/2cos-AoQ(t)/2sin...
…(5) becomes. Here, io is the phase difference between the video carrier and the voltage controlled oscillator output. If = 0
Then, v _I (t) = AoI (t)/2 ... (6). That is, a signal I(t) having an in-phase component with respect to the video carrier wave is obtained as a detection output. However, orthogonal components are not detected. This detection output is applied to a video signal filter 14 via a low-pass filter 4 and a signal amplifier 6.

When a television signal is received using the superherodyne reception method, the overall baseband frequency characteristic can be considered flat due to the Nyquist slope characteristic of the intermediate frequency amplifier, but when it is received using the synchronous reception method, The situation is as shown in Figure 2 a. In other words, the voltage gain in the low frequency range is two parts that of the high frequency range. Therefore, in the conventional example shown in FIG. 1, the frequency characteristics of the video receiving filter 14 are corrected as shown in FIG. 2b.

The conventional television synchronous receiver whose configuration and operation have been explained so far uses the Costas loop (Costas loop), which is a type of synchronous carrier regeneration method.
loop), it is possible to easily synchronize the local oscillator output with the incoming television signal even if the conventional television signal is weak. However, in the above configuration, there is a problem in that the carrier color signal, part of the luminance signal, and the carrier audio signal of the channel adjacent to the channel to be received are mixed into the baseband video signal of the channel to be received as interference signals. have.

That is, the following interference signal, which will be explained using FIG. 3, is mixed. The carrier television signal is comprised of signals having a frequency relationship as shown in FIG. 3a. The desired channel to receive is shown on the right, and the lower adjacent channel is shown on the left. The television signal of the desired channel is synchronously detected by the synchronous detector 2 and converted into a baseband video signal, a carrier color signal and a carrier audio signal as shown in FIG. 3b.
The television signal of the lower adjacent channel is also converted by the synchronous detector 2 into an adjacent carrier video signal, an adjacent carrier color signal and an adjacent carrier audio signal as shown in FIG. 3c. Of these, the hatched portion in FIG. 3c is removed when the output of the synchronous detector 2 passes through the low-pass filter 4. This portion contains most of the energy of the adjacent carrier video signal. but,
The other parts of FIG. 3c, mainly the adjacent carrier color signal and the adjacent carrier audio signal, are mixed into the baseband video signal of FIG. 3b.

OBJECTS OF THE INVENTION It is an object of the present invention to provide a television synchronization receiver that significantly reduces the mixing of the carrier color signal, residual luminance signal, and carrier audio signal of the lower adjacent channel into the baseband video signal of the desired channel. There is a particular thing.

Configuration of the Invention The television synchronous receiver of the present invention includes a voltage controlled oscillator, a 90° phase shifter that shifts the output of the voltage controlled oscillator by 90°, and an output of the voltage controlled oscillator and the 90° phase shifter. first and second synchronous detectors that synchronously detect the in-phase and quadrature components of the video carrier signal using the outputs of the synchronous carrier as synchronous carrier waves, respectively; and a second low-pass filter, a phase detector for detecting a phase difference between the video carrier signal and the output of the voltage-controlled oscillator from the outputs of the first and second low-pass filters, and an output of the phase detector. an A-D converter for converting the baseband video signal contained in the output of the first low-pass filter from analog to digital; a vertical filter that filters the video signal spectrum of the channel desired to be received; and a D-A converter that converts the output of the vertical filter from digital to analog; This consists of an adaptive vertical filter that changes the passband width according to level changes between channels. It is possible to select the color signal spectrum and the residual video signal spectrum separately, and at the same time reduce the mixing of the carrier audio signal of the lower adjacent channel.

DESCRIPTION OF EMBODIMENTS An embodiment of the present invention will be described below with reference to the drawings.

FIG. 4 is a block diagram of a main part of a television synchronization receiver according to an embodiment of the present invention. In FIG. 4, 15 is a high frequency input section, 14 is a first synchronous detector, 17 is a second synchronous detector, 18 is a first low-pass filter, 19 is a second low-pass filter, 20
is a first signal amplifier, 21 is a second signal amplifier,
22 is a phase detector, 23 is a third low-pass filter,
24 is a voltage adder, 25 is a voltage controlled oscillator, 26
is a 90° phase shifter, 27 is a tuning voltage generator,
These correspond to the blocks with the same names in FIG. 1, and the operation of the parts consisting of these blocks is the same as that already explained for the conventional example. 28 is a clock generator, 29 is an A-D converter, 30 is a video signal filter, 31 is a vertical filter controller, 3
2 is a filter control delay compensator, 33 is a vertical filter, 34 is a horizontal filter, 35 is a horizontal delay compensator, 36 is a first DA converter, 37
38A is a carrier color signal C output terminal, and 38B is a luminance signal Y output terminal.

The operation of the television synchronous receiver of this embodiment configured as described above will be explained below. This television synchronized receiver performs digital signal processing of television signals. Of the outputs of the first signal amplifier 20, which are the outputs of the synchronous detection circuit, the television synchronization signal or color burst signal is separated to control the clock generator 28. The output of this clock generator 28 is a clock for digital signal processing. The television signal output from the first signal amplifier 20 is converted into a digital signal by an A-D converter 29, and is applied to a video signal filter 30 composed of a digital filter. The frequency characteristics of the video signal filter 30 are as follows:
This is the same as the characteristic shown in FIG. 2b already shown for the conventional example.

Consider a two-dimensional frequency in which the horizontal frequency of a television signal is μ and the vertical frequency is v. The unit delay operators in the horizontal and vertical directions are then represented by complex numbers Z ^-1 and W ^-1 . That is, Z ^-1 = e ^-j2 〓〓〓 ^o ……(11) W ^-1 = e ^-j2 〓〓〓 ^o ……(12). where ζo and ηo are the horizontal and vertical sampling periods.

Desired frequency response Fdv of vertical filter 33
(ν) is expressed as Fdv(ν)= _∞ 〓 ^n=∞ fdv(n)e ^-j3 〓〓〓 ^on ……(13). Here fdv(n) is the corresponding impulse response. That is, fdv(n)=1/νo∫ ^vo/2 _-vp/2 Fdv(ν)e ^-j2 〓〓〓
^on dν...(14) Here, νo is the sampling frequency, and νo=1/ηo.

Assume now that the desired frequency response Fdv(ν) is an ideal low-pass filter as shown in FIG. That is, −νo/2<ν<νo/2, Fdv(ν)=1,1ν1ν _C 0,ν _C <1ν1νo/2...(15) Since Fdv(ν) is periodic, Equation (15) Define the frequency response for all ν. The impulse response fdv(n) is calculated from equations (14) and (15) as fdv(n)=1/νo∫〓 ^C _- 〓 _C e ^-j2 〓〓〓 ^on dν=sin
(2πν _C ηon)/nπ (16) Since fdv(n) is an infinite interval sequence, n is truncated at an appropriate point to make it a causal impulse response of finite length. That is, let the impulse response fv(n) of the vertical filter 33 be fv(n)=fdv(n), 00nN-1 and other n...(17). In general, fv(n) can be expressed as the product of the desired impulse response fdv(n) and a finite width window g(n). That is, fv(n) is a finite number sequence and can be expressed as fv(n)=fdv(n)g(n)...(18). In the example of equation (17), it becomes as follows.

g(n)=1, 0,0nN-1 For any other n...(19) Equation (19) indicates a rectangular window, but other windows such as a Hamming window may be used as the window g(n). It's okay.

In addition, as the desired frequency response Fdv (ν), equation (15)
In this example, an ideal low-pass filter was used, but the impulse response fv(n) is the frequency response Fv(ν) shown by the following equation.
It is also possible to use That is, fv(n)=1, 0,0nN-1 For other n...(20) Fv(ν)= _N-1 〓 〓 ^N-0 e ^-j2 〓〓〓 ^on =1−e ^-j2 〓〓 〓 ^oN ／１−e ^-j2 〓〓〓 ^o
= sin(πνη _p N)/sin(πνη _p )−e ^-j2 〓〓〓 ^o (
N-1)...(21) Fv(ν) when N=2 in equation (21)
is 2 horizontal synchronization (2H) used to separate the luminance signal and color signal (YC separation) of color television signals.
It is nothing but a comb filter.

Further, it is assumed that Fdv(v-vo/2) is the frequency response of FIG. 5 shifted by vo/2 as shown in FIG. That is, 1,−νo/2ννc−νo/2 and Fdv(ν−νo/2)=−νc+νo/2ννo/
2 0, νc−νo/2<ν<−νo+νc/
2. At this time, the impulse response fdv(n) is expressed by the formula (2
From 1), fdv(n) = sin {2π(ν _c −νo/2)η _p n}/nπ = sin(2πν _c η _p n−nπ)/nπ = sin(2πv _c η _p n)/nπ , n is 0 or an even number −sin(2πν _c η _p n)/nπ, n is an odd number ……(21).

Finite sequence fv(n) obtained as above
A transversal filter as shown in FIG. 7 is constructed by setting the tap gain to . The output x _o of the video signal filter 30 shown in FIG. 4 is applied to the terminal 39 as an input. 40-1, 40-2,...40
-N is IH (1 horizontal period) delay element, 41-0,4
1-1...41-N is a multiplier having a gain of fv(n), 42, 43 and 41 are adders, and 45 is a subtracter. Here, multipliers 41-0, 41-
1,...41-N are connected to the terminal 39 and the output ends of the IH delay elements 40-1, 40-2,...40-N, and the adder 42 is connected to the taps 41-0, 41-N.
2, 41-4, ...41-N, and the adder 43 adds the outputs of the multipliers 41-1, 41-3, ...41.
-(N-1), the adder 44 adds the outputs of adders 42 and 43, and the subtracter 45 subtracts the outputs of adders 42 and 43. The output terminal 46 is connected to the horizontal delay compensator 36 in FIG.
7 outputs the luminance signal y _oY and the carrier color signal y _oC of the desired channel to be received, respectively, to the horizontal filter 34 .

The frequency response _H (μ) of the horizontal filter 34 is
As shown in FIG. 8b, it has a pass band of ±0.5 MHz centered on the color subcarrier frequency of 3.58 MHz of the channel desired to receive. This horizontal filter 34 allows the conveyed color signal y _oC from the vertical filter 33 to be
is band-limited. On the other hand, the vertical filter 33
The luminance signal y _oY (FIG. 8a) outputted from the horizontal delay compensator 35 is compensated for the delay caused by the horizontal filter 34 . The carrier color signal y _oC is sent to the first DA converter 36, and the luminance signal y _oY is sent to the second DA converter 36.
The signals are digital-to-analog converted by the D-A converter 37 and output as analog signals C and Y from the terminals 38A and 38B.

FIG. 9 shows the frequency relationship between the spectrum of the carrier chrominance signal and residual luminance signal of the lower adjacent channel and the spectrum of the luminance signal and carrier chrominance signal of the channel desired to be received. The video signal carrier wave of the lower adjacent channel is 6MHz (based on NTSC system.
This will be explained using the NTSC system. ), but the horizontal scanning frequency _H of the desired channel (4.5MHz÷286)
The closest integer multiple of half the frequency to 6MHz is _fH /2×768=6.00262 (MHz). This is the frequency of the spectrum of the carrier color signal of the channel desired to be received that is closest to the frequency of the video signal carrier of the lower adjacent channel. The difference between these frequencies is 2.62KHz. Therefore, the frequency difference between the luminance signal spectrum of the lower adjacent channel and the spectrum of the carrier color signal of the channel desired to receive is 2.62 KHz. Furthermore, the spectrum of the carrier color signal of the lower adjacent channel is H/2 with respect to the spectrum of the luminance signal of the lower adjacent channel, and the spectrum of the luminance signal of the desired reception channel is _H /2 with respect to the spectrum of the carrier color signal of the desired reception channel.
Therefore, the spectrum of the carrier color signal of the lower adjacent channel has a frequency difference of 2.62 KHz with respect to the spectrum of the luminance signal of the desired channel.

FIG. 9 also shows that the spectrum of each signal has a certain frequency width for each peak.
Actually, the spectrum of the frame frequency interval is _H
It has a structure with a peak for each. If the level of the vertical signal changes rapidly, this frequency width will expand, and if the change is slow, this frequency width will decrease. Here, the vertical signal is a signal in which one frame of a television signal is set as a two-dimensional image and whose axis is in the vertical direction. That is, it is a signal whose axis is perpendicular to the scanning lines and sampled at scanning line intervals on that axis. Therefore, the passband width νc of the vertical filter 33 is made variable, and when the level change between scanning lines of the received television signal is rapid, νc is widened, and when the level change is slow, νc is narrowed. do. By doing so, it is possible to remove most of the carrier color signal spectrum of the lower adjacent channel and the remaining video signal spectrum, while preventing deterioration of the television signal of the desired channel. At the same time, the carrier audio signal of the lower adjacent channel has most of its spectrum removed. This is because the carrier audio signal is frequency modulated, so its spectrum is spread within a certain band.

In order to make the passband width νc of the vertical filter 33 variable, the vertical filter 33 is an adaptive vertical filter. This adaptive vertical filter is obtained by making the impulse response fv(n) of the vertical filter 33, which has already been described, variable. A vertical filter controller 31 is provided to provide the value of fv(n) to the vertical filter 33 to control it.

FIG. 10 is a block diagram of a filter used in the vertical filter controller 31, and FIG. 11 is a diagram showing its frequency response. This filter is for separating and selecting only the signal spectrum of the channel desired to be received. The output of the video signal filter 30 shown in FIG. 4 is applied to the terminal 48. The passband width of the vertical filter 49 is set narrower than the previously determined frequency difference of 2.62 KHz in order to remove the spectrum of the lower adjacent channel signal. The output of this vertical filter 49 is applied to a horizontal bandpass filter 50. The pass band of the horizontal band filter 50 is set from 1.4 MHz to 4.5 MHz. This lower limit of 1.4 MHz is calculated from the frequency 1.5 MHz converted by the synchronous detector 16 of the audio carrier of the lower adjacent channel to 0.1 MHz, which is half the bandwidth of the sideband due to the frequency modulation of the audio carrier. This is the value after subtracting it. By doing so, the vertical filter 49 works effectively only in the frequency band where the spectrum of the lower adjacent channel signal exists. The frequency response when the vertical filter 49 and the horizontal bandpass filter 50 are connected in cascade is shown in FIG. 11a. The signal applied to terminal 48 is also applied to horizontal low pass filter 52 via vertical delay compensator 51. The frequency response of horizontal low pass filter 52 is shown in FIG. 11b. The passband is set to 1.4 MHz because, in a frequency range that is not interfered with by the lower adjacent channel signal, there is no need to remove the spectrum of the lower adjacent channel from the desired reception channel signal using a horizontal filter. The output of the horizontal filter 50 and the output of the horizontal low-pass filter 52 are added by an adder 53 and output to a terminal level detector 55 through a terminal level detector 54 . As a result, the filter configuration shown in FIG. 10 has a frequency response as shown in FIG. 11c. Note that the vertical filter 49 and the vertical delay compensator 51 require
1H delay element W ^-1 is 41-1,4 shown in Figure 7.
1-2, . . . 41-N.

In this way, the output of the horizontal band filter 50 and the output of the horizontal low pass filter 52 are connected to the adder 53.
This added signal is added to one input terminal of the level detector 54, and the output of the vertical delay compensator 51 is added to the other input terminal of the level detector 54. At this time, the vertical delay compensator 51
Since it has a delay element, it also functions as a delay memory for one scanning line, so that the level detector 54 generates a signal corresponding to the level change of the vertical signal of the received television signal, and this signal is sent to the terminal 55. is output from. The output of this detector 54 is used as the output of the vertical filter controller 31, and the tap gain fv(n) of the vertical filter 33 is determined by this output.

In this way, according to the present embodiment, the signal of the channel desired to be received obtained by synchronously detecting the television signal is filtered by the vertical filter 33, so that the interference caused by the signal of the lower adjacent channel can be removed. It has been realized. Furthermore, by making the vertical filter 33 an adaptive filter, it is possible to prevent the vertical filter 33 from deteriorating the quality of the signal of the channel desired to be received.

Effects of the Invention As is clear from the above description, the present invention provides a synchronous detector that synchronously detects a television signal by applying a Costas loop, a low-pass filter that low-pass filters the output of the synchronous detector, and a low-pass filter that performs low-pass filtering of the output of the synchronous detector. Analog converts the baseband video signal included in the low-pass filter output.
A-D converter for digital conversion and this A-D
A vertical filter that filters the output video signal spectrum of the converter, and digital-to-analog conversion of the output of this vertical filter to obtain a video signal D.
- A converter, even though the television broadcast wave has a lower adjacent channel, the converted luminance signal of the lower adjacent channel generated in the synchronous detection circuit; Prevents the mixing of carrier color signals and carrier audio signals, and also selects the baseband video signal spectrum and carrier color signal spectrum of the desired channel to be received separately from the carrier color signal spectrum and residual video signal spectrum of the lower adjacent channel. At the same time, it is possible to reduce the mixing of the carrier audio signal of the lower adjacent channel.

Furthermore, by configuring the above vertical filter with an adaptive vertical filter that varies the passband width according to level changes between scanning lines of the received television signal, the quality of the signal of the channel desired to be received by the vertical filter is degraded. The effect is that the converted signals of the lower adjacent channels can be separated and removed without causing any interference.

Furthermore, the adaptive vertical filter is connected to a first adder that adds a weighted sum of the signal input terminal and the output of each tap of the even-numbered one-horizontal period delay element, and an output of each tap of the odd-numbered one-horizontal period delay element. a second adder that performs a weighted sum of the first adder and a third adder that further adds the output of the first adder and the second adder; By constructing a transversal filter in which a carrier color signal is obtained from a subtracter that subtracts the output of the second adder from the output of the adder, video signals can be processed using the frequency interlace method like a television signal. Even if the signal and the carrier color signal share a band, the adaptive vertical filter can separate and select the baseband video signal of the desired channel from the converted signal of the lower adjacent channel. Effects can be obtained.

Furthermore, one of the above transversal filters
By making the loads on each tap of the horizontal period delay element equal, the frequency characteristics of the pass band will not become the characteristics of an ideal filter, but the effect of simplifying the structure of the filter can be obtained.

Additionally, a vertical filter controller is coupled to a horizontal low pass filter having a passband equal to the channel spacing frequency minus the audio intermediate frequency, and a horizontal low pass filter for filtering out the carrier color signal spectrum of the lower adjacent channel. a vertical filter with a sufficiently narrow band, a horizontal filter that passes the output of this vertical filter in a band whose lower limit is the frequency obtained by subtracting the audio intermediate frequency from the channel interval frequency and whose upper limit is the audio intermediate frequency, and this horizontal band. means for superimposing the output of the filter and the output of the vertical filter; means for adding the superimposing means and the output of the horizontal low-pass filter; and a difference between the scan lines of the means level of the adding means. By using a level detector that detects the signal, it is possible to detect the level difference between the scanning lines of the channel desired to be received without being affected by the converted signal of the lower adjacent channel.

[Brief explanation of the drawing]

Figure 1 is a block diagram of the main parts of a conventional television synchronous receiver, Figure 2a is a baseband frequency characteristic diagram of a video signal, Figure 2b is a frequency characteristic of a video signal filter, and Figure 3a is a diagram of a television synchronous receiver. FIG. 3B is a diagram showing the frequency conversion relationship of the desired reception channel and the lower adjacent channel; FIG. 3C is a diagram showing the frequency displacement function of the lower adjacent channel; FIG. 4 is a block diagram of the main part of an embodiment of the present invention, FIG. 5 is a diagram showing the frequency response of an ideal low-pass filter, and FIG. 6 is a diagram showing the frequency response of the ideal low-pass filter shifted by νo/2. 7 is a diagram showing the configuration of the transversal filter, FIG. 8a is a diagram showing the frequency response of the vertical filter, FIG. 8b is a diagram showing the frequency response of the horizontal filter, and FIG. The figure shows the frequency relationship between the spectrum of the carrier chrominance signal and residual luminance signal of the lower adjacent channel and the spectrum of the luminance signal and carrier chrominance signal of the channel desired to be received. Fig. 11a is a frequency response diagram when a vertical filter and a horizontal filter in a filter used in a vertical filter controller are connected in cascade, and Fig. 11b is a frequency response diagram similarly used in a vertical filter controller. FIG. 11c is a frequency response diagram of a filter used in a vertical filter controller. 16...first synchronous detector, 17...second synchronous detector, 18...first low-pass filter, 19...
...Second low-pass filter, 22...Phase detector, 2
5...Voltage controlled oscillator, 26...90° phase shifter, 2
9... A-D converter, 31... Vertical filter controller, 33... Vertical filter, 34... Horizontal filter, 36... First D-A converter,
37...Second DA converter.

Claims (1)

[Claims] 1. A voltage controlled oscillator, a 90° phase shifter for shifting the output of the voltage controlled oscillator by 90°, and synchronizing the output of the voltage controlled oscillator and the output of the 90° phase shifter, respectively. first and second synchronous detectors that synchronously detect in-phase and quadrature components of a video carrier signal as carrier waves, and first and second low-pass filters that low-pass filter the outputs of the first and second synchronous detectors. filter and
a phase detector for detecting the phase difference between the video carrier signal and the output of the voltage-controlled oscillator from the outputs of the first and second low-pass filters; and means for feeding back the output of the phase detector to the voltage-controlled oscillator. and A- which converts the baseband video signal included in the output of the first low-pass filter from analog to digital.
It has a D converter, a vertical filter that filters the video signal spectrum of the channel desired to be received in the output of the A-D converter, and a D-A converter that converts the output of the vertical filter from digital to analog. A television synchronization receiver characterized in that the vertical filter is an adaptive vertical filter that varies a passband width according to a level change between scanning lines of a received television signal. 2 The adaptive vertical filter is connected to a signal input terminal and a first adder that adds the weighted outputs of each tap of the even-numbered one-horizontal period delay element, and a first adder that adds the output of each tap of the odd-numbered one-horizontal period delay element. The second sum of weights
a third adder that further adds the output of the first adder and the output of the second adder, obtains the luminance signal from the output of the first adder, and obtains the luminance signal from the output of the first adder. 2. A television synchronization receiver according to claim 1, comprising a transversal filter that obtains a carrier color signal from a subtracter that subtracts the output of the second adder. 3. The television synchronization receiver according to claim 2, wherein the loads on each tap of the one horizontal period delay element of the transversal filter are equal. 4. The vertical filter controller is combined with a horizontal low-pass filter whose passband is the channel spacing frequency minus the audio intermediate frequency, and a passband whose passband is such that the carrier color signal spectrum of the lower adjacent channel can be removed. a vertical filter that is sufficiently narrow; a horizontal band filter that passes the output of this vertical filter in a band whose lower limit is a frequency obtained by subtracting the audio intermediate frequency from the channel interval frequency and whose upper limit is the audio intermediate frequency; and this horizontal band filter. and a level detector for detecting a difference in the output level of the adding means between scanning lines. Television synchronization receiver as described.