JPH0720143B2 - Clock synchronization method - Google Patents

Description

The present invention relates to a clock synchronization for obtaining demodulation samples synchronized with a modulation clock in a receiver of a digital communication system using amplitude phase shift (APSK) modulation. Regarding the scheme.

(Prior Art) Conventionally, a phase-locked loop (PLL) as shown in FIG. 2 has been widely used as a clock synchronization method for an amplitude phase shift (APSK) signal. The operation will be briefly described below with reference to the drawings. In the figure, the thin line shows an actual signal and the thick line shows an orthogonal signal.

In order to sample the APSK signal at the timing synchronized with the modulation clock, the A / D converter 13 inputs the signal obtained by quasi-synchronous quadrature demodulation of the APSK signal and modulates the input signal based on the sample clock. N samples are taken every cycle. The clock phase error detecting means 14 inputs the digital time series signal quantized by the A / D converter 13 into the bit number l (l is a positive integer), and detects the phase error between the sample clock and the modulation clock. To do. For the clock phase error detecting means 14, a method of comparing the phases of the sample clock and the extracted clock component, a method of calculating the clock phase error from the sample of the signal point and the zero crossing point, or the like is used. The loop filter 15 averages the phase errors detected by the clock phase error detecting means 14. The digital VCO 16 is phase-controlled by the output of the loop filter 15 and regenerates a clock synchronized with the modulated clock. This becomes the sample clock of the A / D converter 13.

(Problems to be Solved by the Invention) The above is the outline of the conventional clock synchronization system. Since this method basically uses the PLL, there is a synchronization problem peculiar to the PLL. That is, it takes a long time to synchronize, and the synchronization time greatly varies depending on the phase of the initial sample. Also, a hang-up occurs due to the π phase shift. Furthermore, the delay of the channel filter or the like existing in the loop affects the characteristics.

Therefore, it is an object of the present invention to provide a pseudo open loop type clock synchronization system which realizes a constant and short synchronization time.

(Means for Solving the Problem) A clock synchronization system of the present invention is a clock synchronization system for sampling an amplitude phase shift (APSK) signal at a timing synchronized with a modulation clock, and is almost N (N) of the modulation clock.
Is a positive integer) an oscillator that outputs a clock having a frequency, and an A / D converter that performs quasi-synchronous quadrature demodulation on the APSK signal to sample the demodulated signal at the output clock of the oscillator,
Envelope detecting means for calculating the envelope of the digital time series signal by inputting the digital time series signal quantized by the A / D converter to the bit number 1 (1 is a positive integer), and the output clock of the oscillator. Of the sine wave generating means for inputting the sine wave generating means for outputting a quadrature signal which is a sine wave having a frequency of 1 / N of the output clock and being orthogonal to each other, the phase of the output signal of the envelope detecting means and the sine wave generating means Phase correlation detection means for detecting the correlation with the phase of the output signal, a low-pass filter for averaging the output of the phase correlation detection means, and an orthogonal signal consisting of mutually orthogonal signals output from the low-pass filter An arctangent calculating means for calculating arctangent, a frequency divider for dividing the output clock of the oscillator by 1 / N, and a unit for comparing the phase of the output signal of the frequency divider with the phase of the synchronous clock. An output signal based on a comparator, a subtractor that takes the difference between the phase of the output signal of the phase comparator and the phase of the output signal of the arctangent calculation means, and the clock phase error that is the output of the subtractor. An output of the A / D converter using a digital phase control oscillator (VCO) that controls the phase of the synchronous clock in a cycle step of the output clock of the oscillator, and the timing of the synchronous clock that is the output signal of the digital VCO. And a sample for extracting a sample of the modulation clock timing from the sample.

(Example) Next, this invention is demonstrated with reference to drawings. FIG. 1 is a diagram showing an embodiment of the present invention. In the figure, the thin line shows an actual signal and the thick line shows an orthogonal signal.

In the clock synchronization method shown in FIG. 1, the amplitude phase shift (AP
In order to sample the (SK) signal at a timing synchronized with the modulation clock, a clock synchronized with the modulation clock is generated. The oscillator 1 outputs a clock having a frequency approximately N (N is a positive integer) times the modulation clock. A / D converter 2
Samples a signal obtained by quasi-synchronous quadrature demodulation of the APSK signal with the output clock of the oscillator 1. Envelope detecting means 3
Inputs a digital time series signal quantized by the A / D converter 2 into the number of bits l (l is a positive integer), and calculates the envelope of the digital time series signal. The sine wave generating means 4 outputs a quadrature signal having a frequency of 1 / N of the output clock of the oscillator 1 and being sine waves orthogonal to each other.
The sine wave generating means 4 is accessed by using a counter that counts the output clock of the oscillator 1 and the output of the counter as an address, and the sine wave value is written in advance.
Can be easily realized with the M table. Phase correlation detection means 5
Detects the correlation between the phase of the output signal of the envelope detecting means 3 and the phase of the output signal of the sine wave generating means 4. Here, the frequency of the output clock of the oscillator 1 is f _s and the period is T
_s (= 1 / f _a ), the output of the envelope detecting means 3 is x (
_n T _s ), the output Y ( _n T _s ) of the phase correlation detection means 5 is Y ( _n T _s ) = x ( _n T _s ) exp {−j 2 π (f _s / N) _n T _s } (n = 0,1,2, ...). The low-pass filter 6 averages the outputs of the phase correlation detecting means 5. The arctangent calculating means 7 inputs the quadrature signal which is the output of the low-pass filter 6, calculates the tangent thereof, and outputs the phase difference between the modulation clock and the sine wave of the frequency f _s . On the other hand, the frequency divider 8 divides the output clock of the oscillator 1 by 1 / N. The phase comparator 9 compares the phase of the output signal of the frequency divider 8 with the phase of the synchronous clock. Frequency divider 8
2 and the original clock of the synchronous clock that is the output of the digital VCO 11 are both the output clocks of the oscillator 1, and therefore the phase of the output signal of the phase comparator 9 is an integral multiple of 2π / N. The subtractor 10 calculates the difference between the phase of the output signal of the phase comparator 9 and the phase of the output signal of the arctangent calculation means 7. The digital VCO 11 controls the phase of the synchronous clock to be output at the cycle step of the output clock of the oscillator 1 based on the clock phase error output from the subtractor 10. The sampler 12 extracts the sample of the modulation clock timing from the output samples of the A / D converter 2 by using the synchronous clock timing which is the output of the digital VCO 11.

In the first half of FIG. 1, the first half of the envelope detection means 3, the sine wave generation means 4, the phase correlation detection means 5, the low-pass filter 6 and the arctangent calculation means 7 estimates the phase of the modulation clock by open loop. ing. In general, the deviation of the frequency of the modulation clock in the transmitter / receiver is very small, so in a short packet communication system, etc., the phase of the modulation clock is estimated only once for initial synchronization, etc., and estimated over the entire packet section. It is possible to adopt a method of judging data by using the phase of the modulated clock. However, in a communication system that handles continuous signals, a slow clock phase fluctuation occurs due to a shift in the frequency of the modulated clock in the transceiver, and it is necessary to handle it. Therefore, in the present invention, a PLL including a phase comparator 9, a subtractor 10 and a digital VCO 11 is added to follow the clock phase fluctuation. However, since this PLL has a high gain, its noise bandwidth is sufficiently wider than the bandwidth of the low-pass filter 6. Therefore, the SN ratio of the reproduced clock depends only on the bandwidth of the low-pass filter 6, and the entire system can be regarded as an open loop when equivalent.

In the present invention, since the clock for A / D converting the input signal and the sample clock of the sampler are asynchronous, asynchronous connection is required. In FIG. 1, the A / D converter 2, the envelope detecting means 3, the sine wave generating means 4, the phase correlation detecting means 5 and the low pass filter 6 repeatedly perform processing at the cycle T _s of the output clock of the oscillator 1. , Arctangent calculating means 7, phase comparator 9, subtractor 10, digital VCO 1
1. The sampler 12 repeatedly performs processing at the cycle T _c of the synchronous clock which is the output of the digital VCO 11. Here, an asynchronous connection is made between the low-pass filter 6 and the arctangent calculation means 7, but since the cycle T _C is an integral multiple of the cycle T _s , it does not pose a problem.

(Effects of the Invention) As described above, in the present invention, a constant and short synchronization time can be realized by adopting the pseudo open loop type clock synchronization method in which the clock phase estimator and the wideband PLL are combined. Further, it is possible to continuously follow the phase with respect to the clock frequency error. Further, since it is all digital, it is expected to be advantageous in that it can be integrated into an IC without adjustment, and software processing using a digital signal processor (DSP) can be performed.

[Brief description of drawings]

FIG. 1 is a diagram showing an embodiment of the present invention, and FIG. 2 is a diagram showing a conventional clock synchronization system. 1 ... Oscillator, 2, 13 ... A / D converter, 3 ... Envelope detecting means, 4 ... Sine wave generating means, 5 ... Phase correlation detecting means, 6 ... Low-pass filter, 7 ... Arc tangent Calculation means, 8 ... Divider, 9 ... Phase comparator, 10 ... Subtractor,
11, 16 ... Digital VCO, 12 ... Sampler, 14 ... Clock phase error detection means, 15 ... Loop filter.

Claims (1)

[Claims] 1. A clock synchronization system for sampling an amplitude phase shift signal at a timing synchronized with a modulation clock, and an oscillator for outputting a clock having a frequency approximately N (N is a positive integer) times the modulation clock, and the amplitude. An A / D converter that performs quasi-synchronous quadrature demodulation of the phase shift signal and samples the demodulated signal at the output clock of the oscillator, and the A / D converter quantizes the number of bits to 1 / Envelope detecting means for inputting the digitized digital time-series signal and calculating the envelope of the digital time-series signal, and inputting the output clock of the oscillator and having a frequency of 1 / N of the output clock and orthogonal to each other. Sine wave generating means for outputting a quadrature signal consisting of a sine wave, and phase correlation for detecting the correlation between the phase of the output signal of the envelope detecting means and the phase of the output signal of the sine wave generating means. Output means, a low-pass filter for averaging the outputs of the phase correlation detection means, and an arctangent calculation means for inputting an orthogonal signal composed of mutually orthogonal signals output from the low-pass filter and calculating an arctangent thereof, A frequency divider that divides the output clock of the oscillator by 1 / N, a phase comparator that compares the phase of the output signal of the frequency divider with the phase of the synchronization clock, and the phase of the output signal of the phase comparator and A subtracter that takes the difference from the phase of the output signal of the arctangent calculation means, and the phase of the synchronous clock that is the output signal based on the clock phase error that is the output of the subtractor, in a periodic step of the output clock of the oscillator. The digital phase control oscillator to be controlled, and the A /
A clock synchronization method comprising: a sampler for extracting a sample of a modulation clock timing from output samples of a D converter.