JPH081445B2 - Drive for an analog indicating instrument for a cross-coil vehicle - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a cross-coil type analog indicator, and more particularly to a driving device suitable for driving the analog indicator.

[0002]

2. Description of the Related Art Conventionally, in a drive device of this type, pulse signals are sequentially generated at a frequency proportional to the vehicle speed, as shown in, for example, Japanese Patent Application Laid-Open No. 2-222840, and these pulse signals are generated. These pulse signals are converted into analog voltage proportional to the frequency, and in accordance with this analog voltage, a current is made to flow into a pair of crossing coils of the crossing coil type analog indicating instrument to generate an electromagnetic force from each crossing coil. There is one in which the vehicle speed is indicated by a pointer at a deflection angle corresponding to a combined value of these electromagnetic forces.

[0003]

By the way, in such a structure, normally, the above-mentioned smoothing of the analog voltage is realized by a filter composed of a resistor and a capacitor. However, when the frequency of the pulse signal is low, the ripple of the analog voltage increases as the time constant given by the resistor and capacitor of the filter decreases, and as a result, the needle deflection phenomenon of the pointer is caused. Defect occurs. On the other hand, when the frequency of the above-mentioned pulse signal is high, the longer the above-mentioned time constant, the worse the response of the above-mentioned analog voltage, and as a result, the problem that the followability of the pointer deteriorates occurs.

For this, for example, Japanese Patent Laid-Open No. 1-11
As shown in Japanese Patent No. 8772, a pair of frequencies-
It is conceivable to adopt a voltage converter to solve the above-mentioned problem, but in such a case, a pair of frequency-voltage converters are required as described above, which causes a problem that the circuit scale becomes large.

In view of the above, the present invention provides a driving device for a cross-coil type analog indicating instrument over the entire range of frequencies corresponding to analog input without increasing the scale. This is intended to ensure good followability of the pointer while eliminating the needle wobbling phenomenon of the pointer.

[0006]

Means for Solving the Problems A pair of crossing coils which are arranged substantially concentrically with each other and generate respective electromagnetic forces corresponding to analog inputs according to respective inflow currents, and a combined value of the respective electromagnetic forces. In response to the composite value, an analog indicating instrument equipped with a pointer for instructing the analog input at a deflection angle, pulse signal generating means for sequentially generating pulse signals at a frequency proportional to the analog input,
Frequency-voltage conversion means for converting each of the pulse signals into an analog voltage proportional to the frequency of each of the pulse signals;
Of the analog switch corresponding to the increase of the analog voltage
With decreasing stepwise resistance value in response to the switching operation
Of the analog switch corresponding to the decrease of the analog voltage
A variable resistance circuit and a capacitor that gradually increase the resistance value according to the switching operation are provided, and the analog voltage is filtered according to the resistance value and the electrostatic capacitance by the variable resistance circuit and the capacitor to generate a filter voltage. And a current inflow means for respectively inflowing each of the inflow currents into each of the crossing coils according to the filter voltage.

[0007]

By configuring the present invention as described above, if the pulse signal generating means sequentially generates pulse signals at a frequency proportional to the analog input, the frequency-voltage converting means outputs the pulse signals to the respective pulse signals. Switching operation of an analog switch that converts into an analog voltage proportional to each frequency and the filter means responds to an increase or decrease in the analog voltage.
The basis of the resistance value of the variable resistance circuit, the filter voltage generates the analog voltage by the variable resistor circuit and the capacitor and filtered, the current inlet means is the filter voltage stepwise increase reduced in accordance with the Accordingly, each inflow current is caused to flow into each of the cross coils to generate each electromagnetic force corresponding to the analog input from each of the cross coils, and the pointer has a deflection angle corresponding to a combined value of the electromagnetic forces. Instruct the analog input.

[0008]

As described above, the inflow current to each of the crossing coils is specified in relation to the filter voltage generated by the filter means under the filtering effect of the filter means on the output of the frequency-voltage converting means. Therefore, even if a ripple component is included in the output of the frequency-voltage conversion means, the ripple component corresponds to the increase or decrease of the analog input so as to eliminate the needle wobbling phenomenon of the pointer and the deterioration of followability. Each inflow current is specified on the premise of the output of the filter means after being smoothed according to the switching operation of the analog switch .

Therefore, for vehicles with a small analog input
In the case of the frequency range of several Hz peculiar to analog indicating instruments,
For example, if the vehicle speed is 5 km / h, the circumference is around 3.5 Hz.
A pulse signal wave number, but Ru can reliably eliminated <br/> needle deflection phenomenon by the above-mentioned ripple component of the pointer even if such. Further, when the analog input is large, it is possible to secure good followability of the pointer. Further, since the filter means may be a single filter means, it is possible to reduce the size and cost of this type of device without using an extra filter.

[0010]

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS An embodiment of the present invention will now be described with reference to the drawings. FIGS. 1 and 2 show an example in which a drive device D according to the present invention is applied to a vehicle cross-coil type analog indicating instrument 10. . The analog indicating instrument 10 has a pair of crossing coils 11 and 12, and these crossing coils 11 and 1 are provided.
The two are wound so as to cross each other in a cross shape. The cross coil 11 generates an electromagnetic force as a vector quantity in the axial direction according to the inflow current, while the cross coil 12
Generates an electromagnetic force as a vector quantity in the axial direction (that is, the direction orthogonal to the axis of the cross coil 11) according to the inflow current.

A disk 13 made of a permanent magnet is provided in each of the two crossing coils 11 and 12 about its axis 13a.
It is rotatably instructed so as to be orthogonal to the axes of 1 and 12, and the disk 13 is magnetized to the N pole and the S pole at each outer peripheral portion on one diameter line thereof, A predetermined magnetic force is generated in a vector amount in a direction determined by the magnetic poleability. Then, the disk 13 rotates in the clockwise direction (or counterclockwise direction) shown in FIG. 2 according to the vector sum of the electromagnetic forces from the two crossing coils 11 and 12 under the predetermined magnetic force. As shown in FIG. 2, the pointer 14 is axially supported orthogonally to the axis 13a of the disk 13, and the pointer 1
The deflection angle S of 4 changes according to the rotation of the disk 13.

The drive unit D has a constant voltage generator 20 as shown in FIGS. 1 and 3, and the constant voltage generator 20 is driven by a DC power source in response to a constant current from a constant current source Ic. The constant voltages V _c1 , V _c2 and V _c3 are generated in relation to the DC voltage Vd. Further, as shown in FIG. 1, the drive device D includes a vehicle speed sensor 30 and a waveform shaper 40 connected to the vehicle speed sensor 30, and the vehicle speed sensor 30 detects the actual vehicle speed V of the vehicle and detects it. Proportional frequency f (H
At z), vehicle speed pulses (see FIG. 9A) are sequentially generated.

The waveform shaper 40, as shown in FIG. 4, includes both diodes 41, 41, a charging / discharging capacitor 42, a constant current source Ic, both zener diodes 43, 43, and resistors 4 respectively.
4 to 44, comparator 45, both inverters 46a, 4
6b and a transistor 47, each vehicle speed pulse (see FIG. 9A) from the vehicle speed sensor 30 is waveform-shaped and sequentially generated as a shaping pulse (see FIGS. 9B and 9C) from the inverter 46a.

The drive device D is shown in FIGS. 1, 4 and 5.
As shown in FIG. 5, a frequency-voltage converter 50 (hereinafter, referred to as an FV converter 50) connected to the waveform shaper 40 and a filter circuit 60 connected to the FV converter 50 and constituting a main part of the present invention. And the F-V converter 50 has
Both OR gates 51, 51, transistors 52 to 52,
Each resistor 53, 54, 54, both transistors 55, 55,
F-V conversion one-shot capacitor 56, both diodes 57, 57, resistor 58, F-V conversion output smoothing capacitor 59a, current-voltage conversion variable resistor 59b connected in parallel to this capacitor 59a, and constant current. An analog voltage Vfv constituted by a source Ic and proportional to each shaped pulse from the waveform shaper 40 to its frequency f (Hz).
(See FIG. 9D), and this analog voltage Vfv is generated from the common output terminal of the variable resistor 59b and the capacitor 59a.

In such a case, the capacitor 59a smoothes the analog voltage Vfv together with the variable resistor 59b. As shown in FIG. 5, the filter circuit 60 has a voltage divider 61, and the voltage divider 61 is composed of resistors 61a, 61b, 61c, and 61d connected in series with each other. Then, the voltage divider 61 is used in the constant voltage generator 20.
The constant voltage V _c1 from V is divided by the resistors 61a to 61d, and the two resistors 61a, 61b; 61b, 61c; 61 are divided.
The divided voltage Vref1, Vref2 from each common terminal of c, 61d
And Vref3, respectively. However, the divided voltage Vref1
Corresponds to the analog voltage Vfv corresponding to the vehicle speed V = 22.5 (Km / h), and the divided voltage Vref2 is the vehicle speed V = 45.
It corresponds to the analog voltage Vfv corresponding to (Km / h), and the dividing piezoelectric Vref3 corresponds to the analog voltage Vfv corresponding to the vehicle speed V = 90 (Km / h).

The filter circuit 60 has comparators 62a, 62b and 62c, and the comparator 62a has an analog voltage Vfv from the FV converter 50.
Is compared with the divided voltage Vref1 from the voltage divider 61, and Vfv>
A comparison signal is generated at a high level when Vref1 and Vfv <
A comparison signal is generated at a low level when Vref1. The comparator 62b compares the analog voltage Vfv from the FV converter 50 with the divided voltage Vref2 from the voltage divider 61,
When Vfv> Vref2, a comparison signal is generated at a high level,
When Vfv <Vref2, a comparison signal is generated at a low level. The comparator 62c also divides the analog voltage Vfv from the FV converter 50 into the divided voltage Vre from the voltage divider 61.
Compared with f3, a comparison signal is generated at a high level when Vfv> Vref3, and a comparison signal is generated at a low level when Vfv <Vref3.

The analog switch 63a is a comparator 6
It closes in response to the high level comparison signal from 2a ,
In response to the low level comparison signal from the comparator 62a,
To open . The analog switch 63b is the comparator 6
It closes in response to the high level comparison signal from 2b ,
In response to the low level comparison signal from the comparator 62b,
To open . The analog switch 63c is closed in response to a high level comparison signal from the comparator 62c.
To the low level comparison signal from the comparator 62c.
Respond and open . Resistors 64a connected in series with each other,
The resistor circuit 64 including 64b, 64c and 64d constitutes a filter together with the capacitor 65, and the resistors 64a, 64b and 64c correspond to the analog switches 6 respectively.
3a, 63b and 63c are short-circuited only under their respective closures.

In such a case, the resistors 64a, 64b, 64
The resistance values of c and 64d are R1, R2, R3 and R4, respectively.
If so, each analog switch 63a, 63b, 63c
When both are open, the combined resistance value R of the resistance circuit 64 is the sum of the resistance values R1, R2, R3 and R4 (see FIG. 10). When only the analog switch 63a is closed, the combined resistance value R is the sum of the resistance values R2, R3 and R4. When only both analog switches 63a and 63b are closed, the combined resistance value R is the sum of the resistance values R3 and R4. When each of the analog switches 63a, 63b, 63c is closed, the combined resistance value R becomes the resistance value R4.

However, (R1 + R2 + R3 + R4) is the vehicle speed V =
Analog voltage Vfv corresponding to 0 to 22.5 (Km / h)
Corresponding to, (R2 + R3 + R4) is the vehicle speed V = 22.5 ~ 4
Corresponding to the analog voltage Vfv corresponding to 5 (Km / h),
(R3 + R4) corresponds to the analog voltage Vfv corresponding to the vehicle speed V = 45 to 90 (Km / h), and R4 is the vehicle speed V ≧.
It corresponds to the analog voltage Vfv corresponding to 90 (Km / h). The capacitor 65 has a capacitance C and a resistance circuit 64.
F-V according to the time constant τ determined by the combined resistance value R of
The analog voltage Vfv from the converter 50 is further filtered and smoothed to generate a filter voltage VF.

The reference voltage generator 70 divides the constant voltage Vc1 by the resistors 71 to 77 directly connected to each other and generates the first to sixth reference voltages from the respective common terminals 71a to 76a. In such a case, the first to sixth reference voltages are 0.5
(V), 0.75 (V), 1 (V), 1.25 (V),
These correspond to 1.5 (V) and 1.75 (V ), respectively. In addition, the range of the deflection angle S of the pointer 14 from 0 ° to 360 ° is 0.
(V) to 2 (V), and 0.5 (V), 1
(V) and 1.5 (V) correspond to 90 °, 180 °, and 270 °, respectively. The comparison circuit 80 has a plurality of comparators 81 to 85, and the comparator 81 compares the filter voltage VF from the filter circuit 60 with the fourth reference voltage from the reference voltage generator 70.

Therefore, the filter voltage VF is the fourth
When it is higher than the reference voltage, the comparator 81 generates a comparison signal at a high level , and the filter voltage VF is the fourth group.
When the voltage is lower than the quasi voltage, the comparator 81 is at low level.
Generate a comparison signal . The comparator 82 outputs the filter voltage VF from the filter circuit 60 to the reference voltage generator 7
Compare with the second unit voltage from zero. Then, when the filter voltage VF is higher than the second reference voltage, the comparator 72 generates a comparison signal at a high level and the filter voltage
When the voltage VF is lower than the second reference voltage, the comparator 7
2 generates a comparison signal at low level .

The remaining comparators 83, 84 and 85 have a hysteresis characteristic, and the comparator 83 compares the filter voltage VF from the filter circuit 60 with the third reference voltage from the reference voltage generator 70. Then
When the filter voltage VF is lower than the third reference voltage, the comparator 83 generates a comparison signal at high level ,
When the filter voltage VF is higher than the third reference voltage
The comparator 83 generates a comparison signal at low level .

The comparator 84 compares the filter voltage VF from the filter circuit 60 with the first reference voltage from the reference voltage generator 70. Then, the filter voltage VF
Is lower than the first reference voltage, the comparator 84 generates a comparison signal at a high level , and the filter voltage VF is
Comparator 84 is at a low record is higher than the serial first reference voltage
Arising a comparison signal at the bell. The comparator 85 compares the filter voltage VF from the filter circuit 60 with the fifth reference voltage from the reference voltage generator 70. Then, when the filter voltage VF is lower than the fifth reference voltage, the comparator 85 generates a comparison signal at a high level ,
-When the voltage VF is higher than the fifth reference voltage, the comparator
Motor 85 arising the comparison signal at a low level.

The saw-tooth wave current generator 90 has a pair of analog switches 91a and 91b. The analog switch 91a becomes conductive in response to a high level comparison signal from the comparator 85 and becomes low level. It becomes non-conductive in response to the change to. On the other hand, the analog switch 91
b becomes conductive in response to the high level comparison signal from the comparator 84 and becomes non-conductive in response to the change of the comparison signal to the low level. Then, the sawtooth current generator 90
Generates a sawtooth wave current I1 (see FIG. 11A) in accordance with the operations of both analog switches 91a and 91b, the filter circuit 60, the reference voltage generator 70, and the comparison circuit 80.

In such a case, the sawtooth wave current generator 90
The sixth and third reference voltages are received from the reference voltage generator 70 while both analog switches 91a and 91b are in conduction, and the current I1 is increased to I1m in proportion to the rise of the filter voltage VF from the filter circuit 60. Analog switch 91
In response to the non-conduction of b, the current I1 is instantly reduced to -I1m, the current I1 is increased from -I1m to I1m in proportion to the rise of the filter voltage VF, and the current is responded to the non-conduction of the analog switch 91a. I1 is instantly reduced again to -I1m and I1 is increased to I1 = 0 in proportion to the rise of VF.

The sawtooth current generator 100 has an analog switch 101.
1 becomes conductive in response to the high level comparison signal from the comparator 83 and becomes non-conductive in response to the change of the comparison signal to the low level. Then, the sawtooth wave current generator 10
0 is a sawtooth current I2 depending on each operation of the analog switch 101, the reference voltage generator 70 and the filter circuit 60.
(See FIG. 11B) is generated.

In such a case, the sawtooth wave current generator 100
From -I2m in proportion to current I 2 receives a fifth reference voltage at the conduction of a analog switch 101 with receiving a first reference voltage from the reference voltage generator 70 from the filter circuit 60 to increase the filter voltage VF I2m, and the current I in response to the non-conduction of the analog switch 101.
2 instantaneously reduces to -I2m, further the current I2 -I
Increase from 2m to I2m in proportion to the filter voltage VF.

The current-voltage converter 110 (hereinafter referred to as the IV converter 110) receives the current I1 from the sawtooth wave current generator 90 and converts this current I1 into the triangular wave voltage V1 (see FIG. 1).
2 (see (A)). On the other hand, the current-voltage converter 1
20 (hereinafter referred to as an IV converter 120) receives the current I2 from the sawtooth wave current generator 100 and converts the current I2 into a triangular wave voltage V2 (see FIG. 12 (B)). To do. In such a case, the respective voltages V1 and V2 change in a triangular wave shape in accordance with the rise of the filter voltage VF.

The function generator 130 has resistors 131 and 132 connected in series with each other.
Reference numerals 1 and 132 divide the constant voltage Vc1 from the constant voltage generator 20 to generate a divided voltage. However, this divided voltage corresponds to the filter voltage VF = V (90−Xb) corresponding to the deflection angle S = 90 ° −Xb = 46 °. Then, the function generator 1
30 changes the triangular wave voltage V1 from the IV converter 110 in relation to the divided voltage from both resistors 131 and 132, and generates it as a function voltage Vg1 (see the solid line in FIG. 12C).

In this case, Vg1 has a waveform that is linearly bent at VF = V (90-Xb) and line-symmetrical at VF = 0.5 and 1, respectively. However, in the function generator 130, the base-emitter voltages of both transistors 133 and 134 are respectively VBE1 and VBE2, the resistance value of the resistor 135 is R135, and the divided voltage of both resistors 131 and 132 is VA.
Then, the current i1 flowing into the resistor 135 via the transistor 133 is specified by the following equation 1.

[0031]

## EQU1 ## i1 = (V1-VBE1-VA + VBE2) / R135 Therefore, the degree of bending of the functional voltage Vg1 on the waveform is specified by this equation 1. The function generator 140 has both resistors 141 and 142 connected in series with each other, and these resistors 141 and 142 divide the constant voltage Vc1 from the constant voltage generator 20 to generate it as a divided voltage. However, this divided voltage is the filter voltage V corresponding to S = Xb = 44 °.
This corresponds to F = VXb. Then, the function generator 140
The triangular wave voltage V2 from the IV converter 120 is changed in relation to the divided voltage from the resistors 141 and 142, and is generated as a function voltage Vg2 (see the solid line in FIG. 12D).

In this case, Vg2 linearly bends at VF = VXb, and has line-symmetric waveforms at VF = 0.5 and 1. However, in the function generator 140, the base-emitter voltages of the transistors 143 and 144, the resistance value of the resistor 145, and the resistors 141 and 142.
The current flowing through the transistor 143 into the resistor 145 in relation to the divided voltage is specified by equation 1 substantially as in the case of the function generator 130. Therefore, the degree of bending on the waveform of the function voltage Vg2 is similarly specified by Equation 1.

The function generator 150 has both resistors 151 and 152 connected in series with each other.
1, 152 divide the constant voltage Vc1 from the constant voltage generator 20 to generate it as a divided voltage. However, this divided voltage corresponds to the corresponding filter voltage VF = V (90-Xa) at the deflection angle S = 90 ° −Xa = 71.9 °. Then, the function generator 150 changes the function voltage Vg1 from the function generator 130 in relation to the divided voltage from the resistors 151 and 152 to obtain the function voltage Vh1 (see the solid line in FIG. 12E). appear.

In this case, Vh1 has a waveform which is linearly bent at VF = V (90-Xa) and line symmetrical at VF = 0.5 and 1, respectively. However, in the function generator 150, the base-emitter voltages of the transistors 153 and 154 are VBE3 and VBE4, the resistance value of the resistor 155 is R155, and the divided voltage of the resistors 151 and 152 is VB.
Then, the current i2 flowing into the resistor 155 through the transistor 153 is specified by the following equation 2.

[0035]

## EQU00002 ## i2 = ((VB-VBE4) / R155) -Is exp (qVBE4 / KT) Therefore, the bending degree on the waveform different from Vg1 of the function voltage Vh1 is specified by this equation 2.

The function generator 160 has both resistors 161, 162 connected in series with each other.
Reference numerals 1 and 162 divide the constant voltage Vc1 from the constant voltage generator 20 to generate a divided voltage. However, this divided voltage is the filter voltage V corresponding to the deflection angle S = Xa = 18.1 °.
Corresponds to F = VXa. Then, the function generator 160
The function voltage Vg2 from the function generator 140 is changed in relation to the divided voltage from the resistors 161 and 162 and is generated as the function voltage Vh2 (see the solid line in FIG. 12F).

In this case, Vh2 has a waveform which is linearly bent at VF = VXb and line-symmetrical at VF = 0.5 and 1, respectively. However, in the function generator 160,
In relation to the base-emitter voltage of both transistors 163, 164, the resistance value of resistor 165, the divided voltage of both resistors 161, 162, the current flowing into resistor 165 through transistor 163 is in the case of function generator 150. Substantially the same as Therefore, the bending degree on the waveform different from Vg2 of the function voltage Vh2 is specified by the equation 2.

As shown in FIGS. 1 and 7, the output direction switch 170 includes a comparison circuit 170a connected to the current generator 90 and the IV converter 110, and the current generators 100 and I.
The comparison circuit 170b connected to the -V converter 120 and the logic circuit 1 connected to each comparison circuit 80, 170a, 170b
70c.

The comparison circuit 170a has both resistors 171 and 172 connected in series with each other.
1, 172 divide the constant voltage Vc2 from the constant voltage generator 20 to generate it as a divided voltage. However, this divided voltage is Vc2
/ 2. The comparator 173 is the current generator 1
A voltage corresponding to the current I ₁ from 30 is applied to both resistors 171 and 1
Generating a comparison signal at the divided potential pressure by Ri low when a high level from 72, to correspond to the current I1 from the current generator 130
Voltage is higher than the divided voltage from both resistors 171 and 172.
At this time, a comparison signal is generated at low level .

The comparison circuit 170b has resistors 174 and 175 connected in series with each other.
4, 175 divide the constant voltage Vc2 from the constant voltage generator 20 to generate it as a divided voltage. However, this divided voltage is V
Equivalent to c2 / 2. The comparator 176 outputs a voltage corresponding to the current I2 from the current generator 100 to both resistors 175 and 175.
When it is lower than the divided voltage from 176, a comparison signal is generated at a high level and corresponds to the current I2 from the current generator 100.
Voltage is higher than the divided voltage from both resistors 175 and 176.
If not, a comparison signal is generated at low level .

The logic circuit 170c includes both comparators 8
1, 173 is connected to a NOR gate 177a, and both comparators 81 and 82 are connected to a NOR gate 177b.
And a NOR gate 177c connected to the comparator 82 and the NOR gate 177a, and an exclusive OR connected to the comparator 176 and the NOR gate 177c.
Gate 177d, this exclusive OR gate 17
7d and a NOR gate 177e connected to the NOR gate 177b. Thus, the logic circuit 170c has the comparators 81, 82, 173.
NOR gate 17 according to the level of the comparison signal from 176
First and second output direction switching signals are generated from 7c and 177e, respectively.

Incidentally, the low level and the high level are represented by "0" and "1" respectively, and the comparators 81,
The comparison signals from 82, 83, 84, 85, 173 and 176 are respectively Ca, Cb, Cs1, Cs2, Cs3, Csin and Cc.
os, and the first output direction switching signal from the NOR gate 177c and the second output direction switching signal from the NOR gate 177e are represented by Dsin and Dcos, respectively. Table 1 holds.

[0043]

[Table 1]

In the drive circuit 180, the logic circuit 17
When the first output direction switching signal from 0c is low level,
The transistor 181 is rendered conductive by the action of the inverter 181a, and the transistor 182 is rendered conductive by the action of the three inverters 182a, 182b, 182c. Therefore, a current corresponding to (function voltage Vh1 / resistance value of the resistor 183) flows into the resistor 183 through the transistor 181, the cross coil 11, and the transistor 182. On the other hand, when the first output direction switching signal from the logic circuit 170c is at the high level, the transistor 184 is activated by the action of both inverters 184a and 184b, and the transistor 185 is turned on by both inverters 182a and 182a.
Conducted by the action of 85a. Therefore, the current corresponding to (function voltage Vh1 / resistance value of the resistor 183) becomes the transistor 185, the crossing coil 11, and the transistor 184.
Through the resistor 183. This means that the crossing coil 11 generates an electromagnetic force according to the inflow current with a vector amount determined in the inflow direction.

In this case, if both terminals of the crossing coil 11 are represented by reference numerals 11a and 11b as shown in FIG. 8, the terminal voltage V11 between both terminals 11a and 11b is
It is proportional to the inflow current to the filter and changes in the waveform as shown in FIG. 13A in relation to the filter voltage VF. The operational amplifier 186 receives the function voltage V from the function generator 150.
h1 acts so as to be generated as a terminal voltage at the terminal of the resistor 183. Each of the diodes 187 and 188 becomes conductive in response to the first output direction switching signal from the NOR gate 177c, and becomes non-conductive in response to the change of the first output direction switching signal to the low level. This means that each transistor 18
4, 182 can be conducted only under the conduction of the diodes 187, 188, respectively.

On the other hand, in the drive circuit 190, when the second output direction switching signal from the logic circuit 170c is at a low level, the transistor 191 is activated by the action of the inverter 191a, and the transistor 192 has three inverters 192a and 192b. , 192c to conduct electricity. Therefore, a current corresponding to (function voltage Vh2 / resistance value of the resistor 193) flows into the resistor 193 through the transistor 191, the cross coil 12, and the transistor 192. On the other hand, when the second output direction switching signal from the logic circuit 170c is at the low level, the transistor 194 is activated by the action of both the inverters 194a and 194b, and the transistor 195 causes the both inverters 192 to operate.
Conducted by the action of a and 195a. Therefore, the current corresponding to (function voltage Vh2 / resistance value of resistor 193) is
It flows into the resistor 193 through the transistor 195, the cross coil 12, and the transistor 194. This means that the crossing coil 12 generates an electromagnetic force according to the inflow current with a vector amount determined in the inflow direction.

In this case, if both terminals of the crossing coil 12 are represented by reference numerals 12a and 12b as shown in FIG. 8, the terminal voltage V12 between both terminals 12a and 12b is
In proportion to the inflow current into the filter, the waveform changes as shown in FIG. 13B in relation to the filter voltage VF. In this embodiment, the drive device D (vehicle speed sensor 3
0, capacitors 42, 56, 59a and variable resistor 59b
Except for) is formed by an IC.

In the present embodiment constructed as described above,
If put the vehicle in the running state, the frequency of each shaped pulses generated by the vehicle speed sensor 30 in cooperation with the waveform shaper 40 is converted to an analog voltage Vfv by F-V converter 50. Then, the analog voltage Vfv is the vehicle speed V = 0 (K
m / h) and V = 300 (Km / h)
Assuming that fv = 0 (v) changes to Vfv = 2 (V), the filter circuit 60 generates the filter voltage VF according to the analog voltage Vfv as follows.

That is, in the filter circuit 60, when the vehicle speed V <22.5 (Km / h), the comparators 62a, 62b and 62c cooperate with the voltage divider 61 to output the comparison signals at a low level. As a result, each of the analog switches 63a, 63b and 63c is opened.
Therefore, the combined resistance value R of the resistance circuit 64 is equal to each resistance 64a.
This is the sum of the resistances R1 to R4 of .about.64d. Therefore, the filter circuit 60 has a combined resistance value R (= R1 + R2 + R3 + R
The analog voltage Vfv from the FV converter 50 is filtered and smoothed by the cooperation of the resistor circuit 64 having the above 4) and the capacitor 65 and generated as the filter voltage VF.

22.5 (Km / h) <vehicle speed V <4
In the case of 5 (Km / h), the comparator 62a generates a comparison signal at a high level in association with the divided voltage Vref1 from the voltage divider 61, and the remaining both comparators 6
2b and 62c are both divided voltages Vref2 and V from the voltage divider 61.
The comparison signal is generated at a low level in relation to ref3. Therefore, the analog switch 63a is closed in response to the high-level comparison signal from the comparator 62a, while the analog switches 63b and 63c are responsive to the low-level comparison signals from the comparators 62b and 62c, respectively. Open up. Therefore, the combined resistance value R of the resistance circuit 64 is the sum of the resistance values R2, R3 and R4 of the resistors 64b, 64c and 64d. Therefore, the filter circuit 60 filters and smoothes the analog voltage Vfv from the FV converter 50 by the cooperation of the resistor circuit 64 having the combined resistance value R (= R2 + R3 + R4) and the capacitor 65 to obtain the filter voltage VF. appear.

Further, 45 (Km / h) <vehicle speed V <90
In case of (Km / h), both comparators 62a, 62
b generates a high-level comparison signal in association with both divided voltages Vref1 and Vref2 from the voltage divider 61, and a comparator 62c generates a low-level comparison signal in relation to the divided voltage Vref3 from the voltage divider 61. appear. Therefore, both analog switches 63a and 63b are connected to both comparators 62.
The analog switch 63c is opened in response to the high level comparison signal from the a and 62b, while the analog switch 63c is opened in response to the low level comparison signal from the comparator 62. Therefore, the combined resistance value R of the resistance circuit 64 is
It is the sum of the resistance values R3 and R4 of 4c and 64d. Therefore,
The filter circuit 60 filters and smoothes the analog voltage Vfv from the FV converter 50 by the cooperation of the resistor circuit 64 having the combined resistance value R (= R3 + R4) and the capacitor 65, and generates it as the filter voltage VF.

[0052] In addition, 90 (Km / h) <In the case of the vehicle speed V, since the comparators 62A～62 c generates a comparison signal by both the high level by the voltage divider 61 in cooperation with,
All the analog switches 63a to 63c are closed. Therefore, the combined resistance value R of the resistance circuit 64 becomes the resistance value R4 of the resistance 64d. Therefore, the filter circuit 60 filters and smoothes the analog voltage Vfv from the FV converter 50 by the cooperation of the resistor circuit 64 having the combined resistance value R (= R4) and the capacitor 65 to generate the filter voltage VF. To do.

As described above, in the filter circuit 60, since the combined resistance value R changes as shown in FIG. 10 according to the change in the vehicle speed V, the degree of smoothing with respect to the analog voltage Vfv is the same as the combined resistance value R. Relatedly, the lower the vehicle speed V is, the larger the vehicle speed V is. Therefore, when the vehicle speed V is low, the analog voltage Vfv is smoothed to a greater degree and becomes the filter voltage VF. Therefore, the ripple component that causes needle deflection of the filter voltage VF is the ripple of the analog voltage Vfv. Significantly reduced compared to the ingredients.

In this case, since the input frequency to the FV converter 50 is low, there is a delay in the change of the filter voltage VF which causes deterioration of the followability of the pointer 14 due to the large degree of smoothing described above. It never happens. On the other hand, when the vehicle speed V is high, the analog voltage Vfv is smoothed to a smaller degree and becomes the filter voltage VF. There is no delay in the change of the filter voltage VF that causes deterioration. Further, the ripple component of the filter voltage VF does not decrease so much as compared with that of the analog voltage Vfv, but since the input frequency to the FV converter 50 is high, the amplitude of the ripple component is small, so there is no particular problem.

When the filter voltage VF is generated from the filter circuit 60 in this manner, the current generators 90 and 10 are generated.
0 cooperates with the reference voltage generator 70 and the comparison circuit 80 to generate the sawtooth wave currents I1 and I2 (see FIGS. 11A and 11B) according to the change of the filter voltage VF. Then, the IV converters 110 and 120 convert the currents I1 and I2 from the current generators 90 and 100 into the triangular wave voltage V.
1 and V2 (see FIGS. 12 (A) and (B)),
The function generators 130 and 140 generate the triangular wave voltages V1 and V2, respectively.
Function voltages Vg1 and Vg2 (see FIGS. 12C and 12D), respectively, and the function generators 150 and 160 generate function voltages Vh1 and Vh2 according to the function voltages Vg1 and Vg2, respectively.
(See FIGS. 12 (E) and (F)), and the output direction switching device 170 cooperates with the comparison circuit 80 to generate voltages corresponding to the currents I1 and I2 from the current generators 90 and 100, respectively. Accordingly, the first and second output direction switching signals are selectively generated.

Therefore, the drive circuit 180 has the polarity corresponding to the level of the first output direction switching signal from the output direction switching device 170 while the operational amplifier 186 is generating the function voltage Vh1 in the resistor 183. A current is caused to flow into the cross coil 11 . On the other hand, the drive circuit 190 changes the operational amplifier 19
While 6 is generating the functional voltage Vh2 in the resistor 193, a current is caused to flow into the cross coil 12 with a polarity according to the level of the second output direction switching signal from the output direction switching device 170. This means that the terminal voltages V11 and V12 of the crossing coils 11 and 12 depend on the filter voltage VF.
(A) and (B) means that they change respectively.

In other words, the filter voltage VF is 0
In the process of changing from (V) to 2 (V), the currents I1 and I2 are out of phase with each other by 90 ° (corresponding to VF = 0.5 (V)), as shown in FIGS. As shown in, the voltage changes to a sawtooth wave, and the voltages V1 and V2 are 90 ° to each other.
Change into a triangular wave with different phase, and the function voltage Vg1
However, as shown in FIG. 12C, the apex angle of the waveform of the voltage V1 with V (90-Xb) ≦ VF ≦ (0.5 + V (90-Xb)) with VF = 0.5 (V) as the center The voltage V1 is changed so as to be larger, and VF = 1.5 (V) is the center ((1 + V (90
-Xb)) ≤VF≤ (1.5 + V (90-Xb)), the voltage V1 is changed so as to increase the apex angle of the waveform of the voltage V1 .

On the other hand, as shown in FIG. 12D, the function voltage Vg2 is changed so that the apex angle of the waveform of the voltage V2 is increased when 0≤VF≤VXb, and VF = 1 (V). Centered at (0.5 + VXb) ≤VF≤ (1 + VXb) and voltage V2
The voltage V2 is changed so as to increase the apex angle of the waveform, and the voltage V2 is changed so as to increase the apex angle of the waveform of the voltage V2 when (1.5 + VXb) ≤VF≤2 (V). Done
It

Further, as shown in FIG. 12E, the function voltage Vh1 is centered at VF = 0.5 (V) and V (90-Xa) ≤.
When VF ≦ (0.5 + V (90-Xa)), the function voltage Vg1 is changed so that the waveform of the function voltage Vg1 is almost flat, and (1 + V (90- Xa)) ≤
It is formed by changing the function voltage so as to substantially flatten the waveform function voltage Vg1 at VF ≦ (1 .5 + V ( 90-Xa)).

On the other hand, as shown in FIG. 12F, the function voltage Vh2 is 0≤VF≤VXa, (1-VXa) ≤VF≤ (1+
VXa) and (2-VXa) ≤VF≤2 (V), the function voltage Vg2 is changed so that the waveform of the function voltage Vg2 is substantially flat.

Therefore, the terminal voltage V11 of the crossing coil 11 is
Has a pseudo sine waveform as shown in FIG. 13A, while the terminal voltage V12 of the crossing coil 12 has a pseudo cosine waveform as shown in FIG. 13B. In such a case, the terminal voltages V11 and V12 change gently due to the above-described analog circuit configuration. Therefore, the pointer 14 swings in accordance with the change in the vehicle speed V in relation to the electromagnetic forces generated in the crossing coils 11 and 12 according to the terminal voltages V11 and V12 as described above, and as a result, the pointer 14 It is possible to promote the elimination of discomfort with respect to the degree of shake of.

In such a case, the function generators 130 to 16 are associated with the filter voltage VF from the filter circuit 60.
Since the terminal voltages V11 and V12 of the pseudo sine wave and the pseudo cosine wave are generated based on the adoption of 0, the ripple component in the output of the FV converter 50 eliminates the needle shake phenomenon. The terminal voltages V11 and V12 are created on the premise of the filter voltage VF smoothed in accordance with the vehicle speed V as described above so as to ensure good followability of the pointer 14 and the pointer 14. Therefore, when the vehicle speed V is low, the needle deflection phenomenon of the pointer 14 can be surely eliminated, and when the vehicle speed V is high, the followability of the pointer 14 can be ensured satisfactorily, and thus the deflection of the pointer 14 due to the ripple component as described above. There is no sense of discomfort. Further, since the filter circuit 60 may be a single filter circuit, it is possible to reduce the size and cost of this type of drive device without requiring an extra filter.

In implementing the present invention, the vehicle speed V = 22.5 (Km / h) of the terminal voltage V11 (or V12),
In response to the values corresponding to 45 (Km / h) and 90 (Km / h), the analog switches 63a, 63b, 6
The voltage divider 61 and each of the comparators 62a to 62c may be omitted by operating 3c. Further, in carrying out the present invention, the present invention is applied to a drive device for a cross-coil type analog indicating instrument which indicates various analog inputs through an FV converting action, not limited to the vehicle speed V. You may.

Further, in the practice of the present invention, instead of creating the pseudo sine wave and the pseudo cosine wave from the sawtooth current, for example, a filter circuit is used to create the pseudo sine wave and the pseudo cosine wave from a triangular wave or a trapezoidal wave. 6
The output from 0 may be utilized for implementation.

[Brief description of drawings]

FIG. 1 is a block diagram showing one embodiment of the present invention.

FIG. 2 is a schematic configuration diagram of a cross-coil type analog indicating instrument.

3 is a detailed circuit diagram of the constant voltage generator of FIG.

FIG. 4 is a detailed circuit diagram of the waveform shaper and FV converter of FIG.

5 is a detailed circuit diagram of the filter circuit of FIG.

FIG. 6 is a detailed circuit diagram of the reference voltage generator, the comparison circuit, and the both current generators of FIG.

7 is a detailed circuit diagram of both IV converters, function generators, and output direction changers of FIG. 1. FIG.

FIG. 8 is a detailed circuit diagram of both drive circuits of FIG.

9 is an output waveform diagram of the waveform shaper and the FV converter of FIG.

10 is a graph showing the relationship between the combined resistance value R of the resistance circuit in the filter circuit of FIG. 1 and the vehicle speed V and the analog voltage V _fv .

FIG. 11 is an output waveform diagram of each current generator of FIG.

12 is an output waveform diagram of each IV converter and each function generator of FIG. 1. FIG.

FIG. 13 is a terminal voltage waveform diagram of each cross coil of FIG. 1.

[Explanation of symbols]

10 ... Analog indicating instrument, 11, 12 ... Crossing coil, 1
4 ... pointer, 30 ... vehicle speed sensor, 50 ... FV converter, 6
0 ... Filter circuit, 61 ... Voltage divider, 62a-62c ...
Comparator, 63a to 63c ... Analog switch, 6
4 ... Resistance circuit, 65 ... Capacitor, 70 ... Reference voltage generator, 80 ... Comparison circuit, 90, 100 ... Current generator, 11
0,120 ... IV converter, 130-160 ... Function generator, 170 ... Output direction changer, 180, 190 ... Driving circuit.

Claims (1)

[Claims] 1. A pair of crossing coils arranged substantially concentrically and intersecting each other to generate respective electromagnetic forces corresponding to analog inputs according to respective inflow currents, and a combined value of the respective electromagnetic forces. An analog indicating instrument comprising a pointer for indicating the analog input at a deflection angle according to a composite value, and pulse signal generating means for sequentially generating pulse signals at a frequency proportional to the analog input, and each pulse. A frequency-voltage conversion means for converting a signal into an analog voltage proportional to the frequency of each pulse signal, and an analog switch corresponding to the increase of the analog voltage .
With decreasing stepwise resistance value in response to the switching operation
Of the analog switch corresponding to the decrease of the analog voltage
And a variable resistor circuit and a capacitor for increasing stepwise resistance value in response to the switching operation, these variable resistance circuits and the capacitor and by filtering with a filter voltage the analog voltage depending on the resistance value and the capacitance A cross-coil type vehicle characterized by comprising: a filter means for generating the above-mentioned; and a current inflow means for respectively injecting each of the inflow currents into each of the cross-coils in accordance with the filter voltage.
Drive for dual-purpose analog indicating instrument.