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JP4201928B2 - Solenoid valve control circuit - Google Patents
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JP4201928B2 - Solenoid valve control circuit - Google Patents

Solenoid valve control circuit Download PDF

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Publication number
JP4201928B2
JP4201928B2 JP24129699A JP24129699A JP4201928B2 JP 4201928 B2 JP4201928 B2 JP 4201928B2 JP 24129699 A JP24129699 A JP 24129699A JP 24129699 A JP24129699 A JP 24129699A JP 4201928 B2 JP4201928 B2 JP 4201928B2
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voltage
square wave
wave pulse
circuit
current
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JP2001065732A (en
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大輔 廣野
孝輝 吉沢
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Sanden Corp
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Sanden Corp
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Priority to DE2000141958 priority patent/DE10041958B4/en
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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01H—ELECTRIC SWITCHES; RELAYS; SELECTORS; EMERGENCY PROTECTIVE DEVICES
    • H01H47/00—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current
    • H01H47/22—Circuit arrangements not adapted to a particular application of the relay and designed to obtain desired operating characteristics or to provide energising current for supplying energising current for relay coil
    • H01H47/32—Energising current supplied by semiconductor device
    • H01H47/325—Energising current supplied by semiconductor device by switching regulator
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F04—POSITIVE - DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS FOR LIQUIDS OR ELASTIC FLUIDS
    • F04B—POSITIVE-DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS
    • F04B27/00—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders
    • F04B27/08—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders having cylinders coaxial with, or parallel or inclined to, main shaft axis
    • F04B27/14—Control
    • F04B27/16—Control of pumps with stationary cylinders
    • F04B27/18—Control of pumps with stationary cylinders by varying the relative positions of a swash plate and a cylinder block
    • F04B27/1804—Controlled by crankcase pressure
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F16—ENGINEERING ELEMENTS AND UNITS; GENERAL MEASURES FOR PRODUCING AND MAINTAINING EFFECTIVE FUNCTIONING OF MACHINES OR INSTALLATIONS; THERMAL INSULATION IN GENERAL
    • F16K—VALVES; TAPS; COCKS; ACTUATING-FLOATS; DEVICES FOR VENTING OR AERATING
    • F16K31/00—Actuating devices; Operating means; Releasing devices
    • F16K31/02—Actuating devices; Operating means; Releasing devices electric; magnetic
    • F16K31/06—Actuating devices; Operating means; Releasing devices electric; magnetic using a magnet, e.g. diaphragm valves, cutting off by means of a liquid
    • F16K31/0675—Electromagnet aspects, e.g. electric supply therefor
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F04—POSITIVE - DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS FOR LIQUIDS OR ELASTIC FLUIDS
    • F04B—POSITIVE-DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS
    • F04B27/00—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders
    • F04B27/08—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders having cylinders coaxial with, or parallel or inclined to, main shaft axis
    • F04B27/14—Control
    • F04B27/16—Control of pumps with stationary cylinders
    • F04B27/18—Control of pumps with stationary cylinders by varying the relative positions of a swash plate and a cylinder block
    • F04B27/1804—Controlled by crankcase pressure
    • F04B2027/1809—Controlled pressure
    • F04B2027/1813—Crankcase pressure
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F04—POSITIVE - DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS FOR LIQUIDS OR ELASTIC FLUIDS
    • F04B—POSITIVE-DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS
    • F04B27/00—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders
    • F04B27/08—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders having cylinders coaxial with, or parallel or inclined to, main shaft axis
    • F04B27/14—Control
    • F04B27/16—Control of pumps with stationary cylinders
    • F04B27/18—Control of pumps with stationary cylinders by varying the relative positions of a swash plate and a cylinder block
    • F04B27/1804—Controlled by crankcase pressure
    • F04B2027/1822—Valve-controlled fluid connection
    • F04B2027/1827—Valve-controlled fluid connection between crankcase and discharge chamber
    • F—MECHANICAL ENGINEERING; LIGHTING; HEATING; WEAPONS; BLASTING
    • F04—POSITIVE - DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS FOR LIQUIDS OR ELASTIC FLUIDS
    • F04B—POSITIVE-DISPLACEMENT MACHINES FOR LIQUIDS; PUMPS
    • F04B27/00—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders
    • F04B27/08—Multi-cylinder pumps specially adapted for elastic fluids and characterised by number or arrangement of cylinders having cylinders coaxial with, or parallel or inclined to, main shaft axis
    • F04B27/14—Control
    • F04B27/16—Control of pumps with stationary cylinders
    • F04B27/18—Control of pumps with stationary cylinders by varying the relative positions of a swash plate and a cylinder block
    • F04B27/1804—Controlled by crankcase pressure
    • F04B2027/184—Valve controlling parameter
    • F04B2027/1854—External parameters

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  • Engineering & Computer Science (AREA)
  • General Engineering & Computer Science (AREA)
  • Mechanical Engineering (AREA)
  • Physics & Mathematics (AREA)
  • Electromagnetism (AREA)
  • Power Engineering (AREA)
  • Magnetically Actuated Valves (AREA)
  • Flow Control (AREA)

Description

【０００１】
【発明の属する技術分野】
本発明は電磁弁の制御回路に関するものである。
【０００２】
【従来の技術】
本願出願人は、特願平１０−３０７９７９号において、図１に示すように、コイル１ａとコイル１ａに挿通されたプランジャ１ｂとにより構成され、半導体スイッチング素子２を介してデューティー制御される電磁ソレノイド１と、電磁ソレノイド１に並列に配設された半導体スイッチング素子保護ダイオード８とを有し、斜板式可変容量圧縮機の吐出室とクランク室とを連通する連通路を開閉する電磁弁Ａの制御回路であって、直流電源３から電磁弁Ａへ流入する方形波パルス電流を方形波パルス電圧に変換する電流電圧変換回路９と、電流電圧変換回路９の出力である方形波パルス電圧を直流電圧に変換するローパスフィルタ１０と、ローパスフィルタ１０の出力電圧が反転入力側に入力され外部入力可変電圧６が非反転入力側に入力される誤差増幅器１１と、三角波発振器４と、三角波発振器４の出力電圧が反転入力側に入力され誤差増幅器１１の出力電圧が非反転入力側に入力されるＰＷＭ比較器５と、ＰＷＭ比較器５の出力である方形波パルス電圧が入力される半導体スイッチング素子駆動回路７とを有する制御回路を提案した。
【０００３】
図１の制御回路によれば、直流電源３から電磁弁Ａへ流入する方形波パルス電流の時間平均値である平均電流に比例する直流電圧が誤差増幅器１１の反転入力側に入力される。誤差増幅器１１は、反転入力側に入力される直流電圧と非反転入力側に入力される外部入力可変電圧６とを比較し、比較値に応じた直流電圧を出力する。誤差増幅器１１の出力電圧は、電磁弁Ａへ流入する方形波パルス電流の平均電流が一定であれば外部入力可変電圧６の増減に対応して増減し、外部入力可変電圧６が一定であれば電磁弁Ａへ流入する方形波パルス電流の平均電流の増減に対応して減増する。
三角波発振器４の所定周波数ｆの三角波出力電圧がＰＷＭ比較器５の反転入力側に入力され、誤差増幅器１１の出力電圧がＰＷＭ比較器５の非反転入力側に入力される。ＰＷＭ比較器５は、三角波入力電圧と直流入力電圧とを比較し、比較値に応じたＯＮパルス幅の周波数ｆの方形波電圧を出力する。直流入力電圧が大きくなる程、方形波出力電圧のＯＮパルス幅は大きくなる。ＰＷＭ比較器５の方形波出力電圧は半導体スイッチング素子制御回路７を介して半導体スイッチング素子２に出力される。
【０００４】
半導体スイッチング素子２はＰＷＭ比較器５の方形波出力電圧によりＯＮ／ＯＦＦされ、周波数ｆの方形波パルス電流が電磁弁Ａへ流入する。ＰＷＭ比較器５の方形波出力電圧のＯＮパルス幅が広くなる程半導体スイッチング素子２のＯＮ状態の幅が広くなり、電磁弁Ａへ流入する方形波パルス電流のＯＮパルス幅が広くなり、電磁弁Ａへ流入する方形波パルス電流のデューティー比が大きくなり、平均電流が大きくなる。ＰＷＭ比較器５の方形波出力電圧のＯＮパルス幅が狭くなる程半導体スイッチング素子２のＯＮ状態の幅が狭くなり、電磁弁Ａへ流入する方形波パルス電流のＯＮパルス幅が狭くなり、電磁弁Ａへ流入する方形波パルス電流のデューティー比が小さくなり、平均電流が小さくなる。
保護ダイオード８は、半導体スイッチング素子２のＯＦＦ時に過大電圧が半導体スイッチング素子２に負荷されるのを防止し、半導体スイッチング素子２の損傷を防止する。
【０００５】
上記説明から分かるように、図１の制御回路においては、外部入力可変電圧６を制御することにより、電磁弁Ａへ流入する方形波パルス電流のデューティー比を制御して平均電流を制御し、電磁ソレノイド１のプランジャの移動量を制御して電磁弁Ａの開度を制御し、吐出室内からクランク室へ導入される高圧ガスの流量を制御し、クランク室内のガス圧と吸入室内のガス圧との差圧を制御し、斜板の傾斜角を制御し、これらの結果、圧縮機の吐出容量を制御する。図１の制御回路においては、方形波パルス電流のデューティー比と平均電流との相関に基づいて、外部入力可変電圧６を制御する。
【０００６】
直流電源３の電圧が増減すると、電磁弁Ａへ流入する方形波パルス電流のＯＮパルスの電流値が増減する。他方、直流電源３の電圧が増減すると、誤差増幅器１１の出力電圧が減増し、ＰＷＭ比較器５の方形波出力電圧のＯＮパルス幅が減増し、半導体スイッチング素子２のＯＮ状態の幅が減増し、電磁弁Ａへ流入する方形波パルス電流のＯＮパルス幅が減増し、電磁弁Ａへ流入する方形波パルス電流のデューティー比が減増する。従って、外部入力可変電圧６が一定であれば、直流電源３の電圧が増減しても、直流電源３の電圧の増減によって惹起される電磁弁Ａへ流入する方形波パルス電流のＯＮパルスの電流値の増減と、直流電源３の電圧の増減による電磁弁Ａへ流入する方形波パルス電流のデューティー比の減増とが相殺して、電磁弁Ａへ流入する方形波パルス電流の平均電流は一定に保たれる。
従って、図１の制御回路においては、直流電源３の電圧が不安定であっても、外部入力可変電圧６を制御することにより、電磁弁Ａへ流入する方形波パルス電流の平均電流を安定して制御することができ、ひいては電磁弁Ａの作動を安定して制御することができ、圧縮機の吐出容量を安定して制御することができる。
【０００７】
【発明が解決しようとする課題】
直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、図１で矢印で示すように、保護ダイオード８を介して電磁ソレノイド１へ電流が流入する。電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に保護ダイオード８を介して電磁ソレノイド１へ流入する電流の存在により、電磁ソレノイド１へ流入する電流は非方形波パルス電流となる。従って、方形波パルス電流のデューティー比と平均電流との相関に基づいて外部入力可変電圧６を制御する図１の制御回路では、電磁弁Ａへ流入する方形波パルス電流の平均電流を正確に制御することはできるが、電磁ソレノイド１へ流入する非方形波パルス電流の平均電流を正確に制御することはできず、電磁弁Ａの作動を正確に制御することはできず、ひいては圧縮機の吐出容量を正確に制御することはできない。
【０００８】
本発明は上記問題に鑑みてなされたものであり、半導体スイッチング素子を介してデューティー制御される電磁ソレノイドと、電磁ソレノイドに並列に配設された半導体スイッチング素子保護ダイオードとを有する電磁弁の制御回路であって、直流電源から電磁弁へ流入する方形波パルス電流を方形波パルス電圧に変換する電流電圧変換回路と、電流電圧変換回路の出力である方形波パルス電圧を直流電圧に変換するローパスフィルタと、ローパスフィルタの出力電圧が反転入力側に入力され外部入力可変電圧が非反転入力側に入力される誤差増幅器と、三角波発振器と、三角波発振器の出力電圧が反転入力側に入力され誤差増幅器の出力電圧が非反転入力側に入力されるＰＷＭ比較器と、ＰＷＭ比較器の出力である方形波パルス電圧が入力される半導体スイッチング素子駆動回路とを有する制御回路において、外部入力可変電圧を制御して電磁ソレノイドへ流入する非方形波パルス電流の平均電流を正確に制御することができ、ひいては電磁弁の作動を正確に制御することができ、当該電磁弁を例えば可変容量圧縮機の容量制御弁として用いた場合に、圧縮機の吐出容量を正確に制御することができる制御回路を提供することを目的とする。
【０００９】
【課題を解決するための手段】
上記課題を解決するために、本発明においては、半導体スイッチング素子を介してデューティー制御される電磁ソレノイドと、電磁ソレノイドに並列に配設された半導体スイッチング素子保護ダイオードとを有する電磁弁の制御回路であって、直流電源から電磁弁へ流入する方形波パルス電流を方形波パルス電圧に変換する電流電圧変換回路と、電流電圧変換回路の出力である方形波パルス電圧を直流電圧に変換するローパスフィルタと、ローパスフィルタの出力電圧が反転入力側に入力され外部入力可変電圧が非反転入力側に入力される誤差増幅器と、三角波発振器と、三角波発振器の出力電圧が反転入力側に入力され誤差増幅器の出力電圧が非反転入力側に入力されるＰＷＭ比較器と、ＰＷＭ比較器の出力である方形波パルス電圧が入力される半導体スイッチング素子駆動回路とを有する制御回路において、直流電源から電磁弁へ流入する方形波パルス電流のＯＦＦ時に保護ダイオードを介して電磁ソレノイドへ流入する電流を電流電圧変換回路で電圧に変換した場合の電流電圧変換回路の出力電圧に等しい電圧を、電流電圧変換回路の出力である方形波パルス電圧に付加する電圧付加手段を備え、電圧付加手段は、電流電圧変換回路とローパスフィルタとを接続する配線上に配設されたダイオードと、ダイオードの下流側で電流電圧変換回路とローパスフィルタとを接続する配線から分岐して配設されたコンデンサと、コンデンサの下流側で電流電圧変換回路とローパスフィルタとを接続する配線から分岐して配設された抵抗とを有しており、コンデンサと抵抗とはアースされており、電磁ソレノイドの抵抗値を R 1 とし、電磁ソレノイドのコイルのインダクタンスを L 1 とし、電圧付加手段の抵抗の抵抗値を R ２ とし、電圧付加手段のコンデンサの容量値を C ２ とした時に、 R 1 /
L 1 = 1/( R ２ C ２ ) が成立するように、電圧付加手段の抵抗の抵抗値 R ２ と、電圧付加手段のコンデンサの容量値 C ２ とが設定されていることを特徴とする制御回路を提供する。
【００１０】
本発明に係る制御回路においては、直流電源から電磁弁へ流入する方形波パルス電流のＯＦＦ時に保護ダイオードを介して電磁ソレノイドへ流入する電流を電流電圧変換回路で電圧に変換した場合の電流電圧変換回路の出力電圧に等しい電圧を、電流電圧変換回路の出力である方形波パルス電圧に付加し、付加後の非方形波パルス電圧と外部入力可変電圧とに基づいて、ＰＷＭ比較器の方形波出力電圧のＯＮパルス幅を制御するので、外部入力可変電圧を制御することにより目指した方形波パルス電流の平均電流に、電磁ソレノイドへ流入する非方形波パルス電流の平均電流を一致させることができる。従って、本発明に係る制御回路においては、外部入力可変電圧を制御して電磁ソレノイドへ流入する非方形波パルス電流の平均電流を正確に制御することができ、ひいては電磁弁の作動を正確に制御することができる。従って当該電磁弁を例えば可変容量圧縮機の容量制御弁として用いた場合に、圧縮機の吐出容量を正確に制御することができる。
【００１１】
本発明においては、半導体スイッチング素子を介してデューティー制御される電磁ソレノイドと、電磁ソレノイドに並列に配設された半導体スイッチング素子保護ダイオードとを有する電磁弁の制御回路であって、直流電源から電磁弁へ流入する方形波パルス電流を方形波パルス電圧に変換する電流電圧変換回路と、電流電圧変換回路の出力である方形波パルス電圧を直流電圧に変換するローパスフィルタと、ローパスフィルタの出力電圧が反転入力側に入力され外部入力可変電圧が非反転入力側に入力される誤差増幅器と、三角波発振器と、三角波発振器の出力電圧が反転入力側に入力され誤差増幅器の出力電圧が非反転入力側に入力されるＰＷＭ比較器と、ＰＷＭ比較器の出力である方形波パルス電圧が入力される半導体スイッチング素子駆動回路とを有する制御回路において、電磁ソレノイドを流れる非方形波パルス電流の平均電流と直流電源から電磁弁へ流入する方形波パルス電流の平均電流の比で、ローパスフィルタの出力電圧を増幅する電圧増幅手段を備え、電圧増幅手段は、ローパスフィルタと誤差増幅器との間に配設された増幅回路と、半導体スイッチング素子駆動回路と半導体スイッチング素子とを接続する配線から分岐して配設されたデューティー比検出回路と、デューティー比検出回路に接続された増幅比決定回路とを有し、増幅比決定回路に増幅回路が接続されており、ＰＷＭ比較器の方形波出力電圧のデューティー比をデューティー比検出回路が検出し、予め計測された電磁ソレノイドを流れる非方形波パルス電流の時間平均値と直流電源から電磁弁へ流入する方形波パルス電流の時間平均値の比とＰＷＭ比較器の方形波出力電圧のデューティー比との相関と検出したＰＷＭ比較器の方形波出力電圧のデューティー比とを用いて増幅比決定回路が電磁ソレノイドを流れる非方形波パルス電流の時間平均値と直流電源から電磁弁へ流入する方形波パルス電流の時間平均値の比を決定し、決定した比で増幅回路がローパスフィルタの出力電圧を増幅することを特徴とする制御回路を提供する。
【００１２】
本発明に係る制御回路においては、ローパスフィルタの出力電圧を、電磁ソレノイドを流れる非方形波パルス電流の平均電流と直流電源から電磁弁へ流入する方形波パルス電流の平均電流の比で増幅し、増幅後の電圧と外部入力可変電圧とに基づいて、ＰＷＭ比較器の方形波出力電圧のＯＮパルス幅を制御するので、外部入力可変電圧を制御することにより目指した方形波パルス電流の平均電流に、電磁ソレノイドへ流入する非方形波パルス電流の平均電流を一致させることができる。従って、本発明に係る制御回路においては、外部入力可変電圧を制御して電磁ソレノイドへ流入する非方形波パルス電流の平均電流を正確に制御することができ、ひいては電磁弁の作動を正確に制御することができる。従って、当該電磁弁を例えば可変容量圧縮機の容量制御弁として用いた場合、圧縮機の吐出容量を正確に制御することができる。
【００１３】
【発明の実施の形態】
本発明の第１実施例に係る電磁弁の制御回路を図２、３に基づいて説明する。
図２から分かるように、本実施例に係る制御回路においては、電流電圧変換回路９とローパスフィルター１０との間に、電圧付加回路１２が配設されている。電圧付加回路１２は、電流電圧変換回路９とローパスフィルター１０とを接続する配線上に配設されたダイオード１２ａと、ダイオード１２ａの下流側で電流電圧変換回路９とローパスフィルター１０とを接続する配線から分岐して配設されたコンデンサ１２ｂと、コンデンサ１２ｂの下流側で電流電圧変換回路９とローパスフィルター１０とを接続する配線から分岐して配設された抵抗１２ｃとを有している。コンデンサ１２ｂと抵抗１２ｃとはアースされている。上記を除き本実施例に係る制御回路の構成は図１の制御回路の構成と同一である。
【００１４】
本実施例に係る制御回路においては、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、電圧付加回路１２のコンデンサ１２ｂから抵抗１２ｃを介して電荷が放出され電圧E(t)′が発生する。電圧E(t)′は、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、保護ダイオード８を介して電磁ソレノイド１へ流入する電流を電流電圧変換回路９で電圧に変換した場合の電流電圧変換回路９の出力電圧に等しい電圧である。
【００１５】
電圧E(t)′が、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、保護ダイオード８を介して電磁ソレノイド１へ流入する電流を電流電圧変換回路９で電圧に変換した場合の電流電圧変換回路９の出力電圧に等しい電圧となるための条件を以下に考察する。
図３（ａ）に示すように、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、保護ダイオード８を介して電磁ソレノイド１へ電流I(t)が流れる。この時、電磁ソレノイド１に加わる電圧E(t)と保護ダイオード８を介して電磁ソレノイド１へ流れる電流I(t)との関係は、
I(t) = (R1/L1)∫[E(t)/R1 - I(t)]dt・・・・・▲１▼
で表される。ここで、R1は電磁ソレノイド１の抵抗値であり、L1は電磁ソレノイド１のコイル１ａのインダクタンス値である。
図３（ｂ）に示すように、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、コンデンサ１２ｂから抵抗１２ｃへ電流I(t)′が流れる。この時、コンデンサ１２ｂの電位E(t)′と抵抗１２ｃの下流側の電位E(t)″との関係は、
E(t)′ = (1/(R2C2)) ∫[ E(t)″- E(t)′]dt ・・・・・▲２▼
で表される。ここで、R2は抵抗１２ｃの抵抗値であり、C2はコンデンサ１２ｂの容量値である。
【００１６】
▲１▼、▲２▼より、
R1/L1 = 1/(R2C2) ・・・・・▲３▼
E(t)/R1 = AE(t)″・・・・・▲４▼
が成立すれば、
I(t) = AE(t)′・・・・・・▲５▼
となることが分かる。ここで、A は任意の定数である。
ここで、E(t)≒０であり、抵抗１２ｃはアースされておりE(t)″＝０なので、▲４▼は成立する。従って、▲３▼が成立するように、電圧付加回路１２のコンデンサ１２ｂの容量値C2と、抵抗１２ｃの抵抗値R2を設定すれば、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、保護ダイオード８を介して電磁ソレノイド１へ流れる電流I(t)に比例する電圧E(t)′を、電圧付加回路１２に発生させることができる。
【００１７】
他方、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＮ時には、電磁ソレノイド１ヘ流れる電流i(t)と電流電圧変換回路９の出力電圧ε(t) との間の関係は、
i(t) = aε(t) ・・・・・・▲６▼
となる。
直流電源３から電磁弁Ａへ流入する方形波パルス電流がＯＦＦになった瞬間には、i(t) = I(t)であり、ε(t) = E(t)′なので、 a = Aである。 aは電流電圧変換回路９固有の変換定数なので、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、保護ダイオード８を介して電磁ソレノイド１へ流れる電流I(t)が電流電圧変換回路９固有の変換定数 aと等しい変換定数A で電圧E(t)′に変換されることになる。
以上より、▲３▼が成立するように、電圧付加回路１２のコンデンサ１２ｂの容量値C2と、抵抗１２ｃの抵抗値R2を設定すれば、電圧付加回路１２は、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に、保護ダイオード８を介して電磁ソレノイド１へ流入する電流を電流電圧変換回路９で電圧に変換した場合の電流電圧変換回路９の出力電圧に等しい電圧を発生させることが分かる。
【００１８】
本実施例に係る制御装置によれば、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に保護ダイオード８を介して電磁ソレノイド１へ流入する電流を電流電圧変換回路９で電圧に変換した場合の電流電圧変換回路９の出力電圧に等しい電圧を、電流電圧変換回路９の出力である方形波パルス電圧に付加し、付加後の非方形波パルス電圧と外部入力可変電圧６とに基づいて、ＰＷＭ比較器５の方形波出力電圧のＯＮパルス幅を制御するので、外部入力可変電圧６を制御することにより目指した方形波パルス電流の平均電流に、電磁ソレノイド１へ流入する非方形波パルス電流の平均電流を一致させることができる。
より詳細に説明すると、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に保護ダイオード８を介して電磁ソレノイド１へ流入する電流を電流電圧変換回路９で電圧に変換した場合の電流電圧変換回路９の出力電圧に等しい電圧が、電流電圧変換回路９の出力である方形波パルス電圧に付加されることにより、ローパスフィルタ１０の出力電圧は前記付加電圧分だけ増加する。この結果、ＰＷＭ比較器５の方形波出力電圧のデューティー比は、外部入力可変電圧６が予定した値よりも前記付加電圧分だけ減少し、直流電源３から電磁弁Ａへ流入する方形波パルス電流のデューティー比も、外部入力可変電圧６が予定した値よりも前記付加電圧分だけ減少する。直流電源３から電磁弁Ａへ流入する方形波パルス電流のデューティー比が、外部入力可変電圧６が予定した値よりも減少することによって惹起された、電磁ソレノイド１を流れるパルス電流の平均電流の減少が、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に保護ダイオード８を介して電磁ソレノイド１へ流入する電流によって惹起された、電磁ソレノイド１を流れるパルス電流の平均電流の増加と相殺する。この結果、電磁ソレノイド１を流れるパルス電流の平均電流は、外部入力可変電圧６が予定した値となる。
従って、実施例に係る制御回路においては、外部入力可変電圧６を制御して電磁ソレノイド１へ流入する非方形波パルス電流の平均電流を正確に制御することができ、ひいては電磁弁Ａの作動を正確に制御することができる。従って、電磁弁Ａを例えば可変容量圧縮機の容量制御弁として用いた場合に、圧縮機の吐出容量を正確に制御することができる。
【００１９】
本発明の第２実施例に係る電磁弁の制御回路を図４、５に基づいて説明する。
図４から分かるように、本実施例に係る制御回路においては、ローパスフィルタ１０と誤差増幅器１１との間に、増幅回路１３が配設されている。半導体スイッチング素子駆動回路７と半導体スイッチング素子２とを接続する配線から分岐してデューティー比検出回路１４が配設され、デューティー比検出回路１４に増幅比決定回路１５が接続されている。増幅比決定回路１５に増幅回路１３が接続されている。上記を除き、本実施例に係る制御回路の構成は図１の制御回路の構成と同一である。
直流電源３から電磁弁Ａへ流入する方形波パルス電流の平均電流I1と、電磁ソレノイド１を流れる非方形波パルス電流の平均電流I2との間には、図５に示すように、
I2/I1 = ｆ( ＰＷＭ比較器５の方形波出力電圧のデューティー比) ・・・▲７▼
なる関係がある。
関数ｆは、電磁弁Ａの特性に依存する関数であり、電磁弁Ａの特性が確定していれば、ＰＷＭ比較器５の方形波出力電圧のデューティー比を種々に代えてI2/I1 を計測することにより求めることができる。本願発明者は、電磁弁Ａの特性が確定していれば、関数ｆはＰＷＭ比較器５の方形波出力電圧のデューティー比のみの関数であり、直流電源３の電圧の変化により影響を受けないことを実験により確認している。
【００２０】
本実施例に係る制御回路においては、デューティー比検出回路１４がＰＷＭ比較器５の方形波出力電圧のデューティー比を検出し、計測により予め設定した関数ｆと、デューティー比検出回路１４が検出したＰＷＭ比較器５の方形波出力電圧のデューティーとに基づいて、増幅比決定回路１５がI2/I1 を決定する。増幅回路１３は、ローパスフィルター１０の出力電圧をI2/I1 倍に増幅する。
本実施例に係る制御回路においては、ローパスフィルタ１０の出力電圧を、電磁ソレノイド１を流れる非方形波パルス電流の平均電流I2と、直流電源３から電磁弁Ａへ流入する方形波パルス電流の平均電流I1の比I2/I1 で増幅し、増幅後の電圧と外部入力可変電圧６とに基づいて、ＰＷＭ比較器５の方形波出力電圧のＯＮパルス幅を制御するので、外部入力可変電圧６を制御することにより目指した方形波パルス電流の平均電流に、電磁ソレノイド１へ流入する非方形波パルス電流の平均電流を一致させることができる。
より詳細に説明すると、ローパスフィルタ１０の出力電圧がI2/I1 の比で増幅されるので、ＰＷＭ比較器５の方形波出力電圧のデューティー比は、外部入力可変電圧６が予定した値よりも前記増幅分だけ減少し、直流電源３から電磁弁Ａへ流入する方形波パルス電流のデューティー比も、外部入力可変電圧６が予定した値よりも前記増幅だけ減少する。直流電源３から電磁弁Ａへ流入する方形波パルス電流のデューティー比が、外部入力可変電圧６が予定した値よりも減少することによって惹起された、電磁ソレノイド１を流れるパルス電流の平均電流の減少が、直流電源３から電磁弁Ａへ流入する方形波パルス電流のＯＦＦ時に保護ダイオード８を介して電磁ソレノイド１へ流入する電流によって惹起された、電磁ソレノイド１を流れるパルス電流の平均電流の増加と相殺する。この結果、電磁ソレノイド１を流れるパルス電流の平均電流は、外部入力可変電圧６が予定した値となる。
従って、実施例に係る制御回路においては、外部入力可変電圧６を制御して電磁ソレノイド１へ流入する非方形波パルス電流の平均電流を正確に制御することができ、ひいては電磁弁Ａの作動を正確に制御することができる。従って、電磁弁Ａを例えば可変容量圧縮機の容量制御弁として用いた場合に、圧縮機の吐出容量を正確に制御することができる。
【００２１】
【発明の効果】
以上説明したごとく、本発明に係る制御回路においては、直流電源から電磁弁へ流入する方形波パルス電流のＯＦＦ時に保護ダイオードを介して電磁ソレノイドへ流入する電流を電流電圧変換回路で電圧に変換した場合の電流電圧変換回路の出力電圧に等しい電圧を、電流電圧変換回路の出力である方形波パルス電圧に付加し、付加後の非方形波パルス電圧と外部入力可変電圧とに基づいて、ＰＷＭ比較器の方形波出力電圧のＯＮパルス幅を制御するので、外部入力可変電圧を制御することにより目指した方形波パルス電流の平均電流に、電磁ソレノイドへ流入する非方形波パルス電流の平均電流を一致させることができる。従って、本発明に係る制御回路においては、外部入力可変電圧を制御して電磁ソレノイドへ流入する非方形波パルス電流の平均電流を正確に制御することができ、ひいては電磁弁の作動を正確に制御することができる。従って当該電磁弁を例えば可変容量圧縮機の容量制御弁として用いた場合に、圧縮機の吐出容量を正確に制御することができる。
【００２２】
本発明に係る制御回路においては、ローパスフィルタの出力電圧を、電磁ソレノイドを流れる非方形波パルス電流の平均電流と直流電源から電磁弁へ流入する方形波パルス電流の平均電流の比で増幅し、増幅後の電圧と外部入力可変電圧とに基づいて、ＰＷＭ比較器の方形波出力電圧のＯＮパルス幅を制御するので、外部入力可変電圧を制御することにより目指した方形波パルス電流の平均電流に、電磁ソレノイドへ流入する非方形波パルス電流の平均電流を一致させることができる。従って、本発明に係る制御回路においては、外部入力可変電圧を制御して電磁ソレノイドへ流入する非方形波パルス電流の平均電流を正確に制御することができ、ひいては電磁弁の作動を正確に制御することができる。従って当該電磁弁を例えば可変容量圧縮機の容量制御弁として用いた場合に、圧縮機の吐出容量を正確に制御することができる。
【図面の簡単な説明】
【図１】従来の電磁弁の制御回路の回路図である。
【図２】本発明の第１実施例に係る電磁弁の制御回路の回路図である。
【図３】本発明の第１実施例に係る電磁弁の制御回路において、電磁弁へ流入する方形波パルス電流のＯＦＦ時に電磁弁の電磁ソレノイドに流れる電流と、電磁弁へ流入する方形波パルス電流のＯＦＦ時に制御回路の電圧付加回路に発生する電圧との関係を説明する図である。（ａ）は電磁弁の電磁ソレノイドに流れる電流を説明する図であり、（ｂ）は制御回路の電圧付加回路に発生する電圧を説明する図である。
【図４】本発明の第２実施例に係る電磁弁の制御回路の回路図である。
【図５】直流電源から電磁弁へ流入する方形波パルス電流の平均電流I1と、電磁ソレノイドを流れる非方形波パルス電流の平均電流I2との間の関係を示す図である。
【符号の説明】
１ 電磁ソレノイド
１ａ コイル
１ｂ プランジャー
２ 半導体スイッチング素子
３ 直流電源
４ 三角波発信回路
５ ＰＷＭ比較器
６ 外部入力可変電圧
７ 半導体スイッチング素子駆動回路
８ 半導体スイッチング素子保護ダイオード
９ 電流電圧変換回路
１０ ローパスフィルタ
１１ 誤差増幅器
１２ 電圧付加回路
１２ａ ダイオード
１２ｂ コンデンサ
１２ｃ 抵抗
１３ 増幅回路
１４ デューティー比検出回路
１５ 増幅比決定回路[0001]
BACKGROUND OF THE INVENTION
The present invention relates to a control circuit for a solenoid valve.
[0002]
[Prior art]
As shown in FIG. 1, the applicant of the present application, as shown in FIG. 1, in Japanese Patent Application No. 10-307879, is composed of a coil 1 a and a plunger 1 b inserted into the coil 1 a, and is an electromagnetic solenoid that is duty-controlled via a semiconductor switching element 2. 1 and a semiconductor switching element protection diode 8 arranged in parallel with the electromagnetic solenoid 1, and control of an electromagnetic valve A that opens and closes a communication path that connects the discharge chamber and the crank chamber of the swash plate type variable capacity compressor. A current-voltage conversion circuit 9 that converts a square-wave pulse current flowing from the DC power supply 3 into the solenoid valve A into a square-wave pulse voltage, and a square-wave pulse voltage that is an output of the current-voltage conversion circuit 9 as a DC voltage. The low-pass filter 10 for converting to the low-pass filter 10 and the output voltage of the low-pass filter 10 are input to the inverting input side and the external input variable voltage 6 is input to the non-inverting input side. Error amplifier 11, triangular wave oscillator 4, PWM comparator 5 in which the output voltage of triangular wave oscillator 4 is input to the inverting input side, and the output voltage of error amplifier 11 is input to the non-inverting input side. A control circuit having a semiconductor switching element driving circuit 7 to which a square-wave pulse voltage as an output is input has been proposed.
[0003]
According to the control circuit of FIG. 1, a DC voltage proportional to an average current that is a time average value of a square wave pulse current flowing from the DC power supply 3 to the solenoid valve A is input to the inverting input side of the error amplifier 11. The error amplifier 11 compares the DC voltage input to the inverting input side with the external input variable voltage 6 input to the non-inverting input side, and outputs a DC voltage corresponding to the comparison value. The output voltage of the error amplifier 11 increases or decreases corresponding to the increase or decrease of the external input variable voltage 6 if the average current of the square wave pulse current flowing into the solenoid valve A is constant, and if the external input variable voltage 6 is constant. It increases and decreases corresponding to the increase and decrease of the average current of the square wave pulse current flowing into the solenoid valve A.
A triangular wave output voltage of a predetermined frequency f of the triangular wave oscillator 4 is input to the inverting input side of the PWM comparator 5, and an output voltage of the error amplifier 11 is input to the non-inverting input side of the PWM comparator 5. The PWM comparator 5 compares the triangular wave input voltage and the DC input voltage, and outputs a square wave voltage having a frequency f with an ON pulse width corresponding to the comparison value. As the DC input voltage increases, the ON pulse width of the square wave output voltage increases. The square wave output voltage of the PWM comparator 5 is output to the semiconductor switching element 2 via the semiconductor switching element control circuit 7.
[0004]
The semiconductor switching element 2 is turned on / off by the square wave output voltage of the PWM comparator 5, and a square wave pulse current having a frequency f flows into the solenoid valve A. As the ON pulse width of the square wave output voltage of the PWM comparator 5 becomes wider, the ON state width of the semiconductor switching element 2 becomes wider, and the ON pulse width of the square wave pulse current flowing into the electromagnetic valve A becomes wider. The duty ratio of the square-wave pulse current flowing into A increases, and the average current increases. As the ON pulse width of the square wave output voltage of the PWM comparator 5 becomes narrower, the ON state width of the semiconductor switching element 2 becomes narrower, and the ON pulse width of the square wave pulse current flowing into the solenoid valve A becomes narrower. The duty ratio of the square wave pulse current flowing into A is reduced, and the average current is reduced.
The protection diode 8 prevents an excessive voltage from being applied to the semiconductor switching element 2 when the semiconductor switching element 2 is OFF, and prevents damage to the semiconductor switching element 2.
[0005]
As can be seen from the above description, in the control circuit of FIG. 1, by controlling the external input variable voltage 6, the duty ratio of the square wave pulse current flowing into the solenoid valve A is controlled to control the average current, The amount of movement of the plunger of the solenoid 1 is controlled to control the opening of the solenoid valve A, the flow rate of the high-pressure gas introduced from the discharge chamber to the crank chamber is controlled, and the gas pressure in the crank chamber and the gas pressure in the suction chamber Are controlled, and the inclination angle of the swash plate is controlled. As a result, the discharge capacity of the compressor is controlled. In the control circuit of FIG. 1, the external input variable voltage 6 is controlled based on the correlation between the duty ratio of the square wave pulse current and the average current.
[0006]
When the voltage of the DC power supply 3 increases or decreases, the current value of the ON pulse of the square wave pulse current flowing into the solenoid valve A increases or decreases. On the other hand, when the voltage of the DC power supply 3 increases or decreases, the output voltage of the error amplifier 11 decreases, the ON pulse width of the square wave output voltage of the PWM comparator 5 decreases, and the width of the ON state of the semiconductor switching element 2 decreases. The ON pulse width of the square wave pulse current flowing into the solenoid valve A decreases, and the duty ratio of the square wave pulse current flowing into the solenoid valve A decreases. Therefore, if the external input variable voltage 6 is constant, even if the voltage of the DC power supply 3 increases or decreases, the ON pulse current of the square wave pulse current flowing into the solenoid valve A caused by the increase or decrease of the voltage of the DC power supply 3 The increase / decrease in value and the increase / decrease in the duty ratio of the square wave pulse current flowing into the solenoid valve A due to increase / decrease in the voltage of the DC power supply 3 cancel each other, and the average current of the square wave pulse current flowing into the solenoid valve A is constant. To be kept.
Therefore, in the control circuit of FIG. 1, even if the voltage of the DC power supply 3 is unstable, the average current of the square wave pulse current flowing into the solenoid valve A is stabilized by controlling the external input variable voltage 6. Therefore, the operation of the solenoid valve A can be controlled stably, and the discharge capacity of the compressor can be controlled stably.
[0007]
[Problems to be solved by the invention]
When the square wave pulse current flowing from the DC power supply 3 to the solenoid valve A is OFF, current flows into the electromagnetic solenoid 1 via the protective diode 8 as shown by an arrow in FIG. Due to the current flowing into the electromagnetic solenoid 1 via the protective diode 8 when the square wave pulse current flowing into the electromagnetic valve A is OFF, the current flowing into the electromagnetic solenoid 1 becomes a non-square wave pulse current. Therefore, in the control circuit of FIG. 1 that controls the external input variable voltage 6 based on the correlation between the duty ratio of the square wave pulse current and the average current, the average current of the square wave pulse current flowing into the solenoid valve A is accurately controlled. However, the average current of the non-square wave pulse current flowing into the electromagnetic solenoid 1 cannot be accurately controlled, and the operation of the solenoid valve A cannot be accurately controlled, and thus the discharge of the compressor The capacity cannot be controlled accurately.
[0008]
The present invention has been made in view of the above-described problems, and includes a solenoid valve control circuit having an electromagnetic solenoid that is duty-controlled via a semiconductor switching element, and a semiconductor switching element protection diode disposed in parallel with the electromagnetic solenoid. A current-voltage conversion circuit that converts a square-wave pulse current flowing from a DC power source into a solenoid valve into a square-wave pulse voltage, and a low-pass filter that converts a square-wave pulse voltage output from the current-voltage conversion circuit into a DC voltage And the error amplifier in which the output voltage of the low-pass filter is input to the inverting input side and the external input variable voltage is input to the non-inverting input side, the triangular wave oscillator, and the output voltage of the triangular wave oscillator is input to the inverting input side. PWM comparator whose output voltage is input to the non-inverting input side and square wave pulse voltage which is the output of the PWM comparator is input Control circuit having a semiconductor switching element driving circuit capable of controlling the external input variable voltage to accurately control the average current of the non-square wave pulse current flowing into the electromagnetic solenoid, and thus the operation of the electromagnetic valve accurately. It is an object of the present invention to provide a control circuit that can accurately control the discharge capacity of a compressor when the electromagnetic valve is used as, for example, a capacity control valve of a variable capacity compressor.
[0009]
[Means for Solving the Problems]
In order to solve the above problems, in the present invention, a solenoid valve control circuit having an electromagnetic solenoid that is duty-controlled via a semiconductor switching element, and a semiconductor switching element protection diode that is arranged in parallel to the electromagnetic solenoid. A current-voltage conversion circuit that converts a square-wave pulse current flowing from a DC power source into a solenoid valve into a square-wave pulse voltage, and a low-pass filter that converts a square-wave pulse voltage, which is the output of the current-voltage conversion circuit, into a DC voltage The error amplifier in which the output voltage of the low-pass filter is input to the inverting input side and the external input variable voltage is input to the non-inverting input side, the triangular wave oscillator, and the output voltage of the triangular wave oscillator is input to the inverting input side. The PWM comparator that inputs the voltage to the non-inverting input side and the square wave pulse voltage that is the output of the PWM comparator In a control circuit having a semiconductor switching element drive circuit that converts a current flowing into the electromagnetic solenoid through a protective diode into a voltage by a current-voltage conversion circuit when the square wave pulse current flowing from the DC power supply to the solenoid valve is OFF Voltage adding means for adding a voltage equal to the output voltage of the current-voltage converter circuit to the square-wave pulse voltage that is the output of the current-voltage converter circuitThe voltage adding means is arranged by branching from a diode arranged on a wiring connecting the current-voltage conversion circuit and the low-pass filter, and a wiring connecting the current-voltage conversion circuit and the low-pass filter on the downstream side of the diode. And a resistor branched from the wiring connecting the current-voltage conversion circuit and the low-pass filter on the downstream side of the capacitor. The capacitor and the resistor are grounded, and the electromagnetic solenoid Resistance value of R 1 And the inductance of the electromagnetic solenoid coil L 1 And the resistance value of the resistance of the voltage adding means R 2 And the capacitance value of the capacitor of the voltage addition means C 2 When R 1 /
L 1 = 1 / (R 2 C 2 ) The resistance value of the resistance of the voltage adding means so that R 2 And the capacitance value of the capacitor of the voltage adding means C 2 And are setA control circuit is provided.
[0010]
In the control circuit according to the present invention, the current-voltage conversion when the current flowing into the electromagnetic solenoid via the protective diode is converted into the voltage by the current-voltage conversion circuit when the square wave pulse current flowing from the DC power supply to the solenoid valve is OFF. A voltage equal to the output voltage of the circuit is added to the square wave pulse voltage that is the output of the current-voltage conversion circuit, and the square wave output of the PWM comparator is based on the non-square wave pulse voltage after addition and the external input variable voltage Since the ON pulse width of the voltage is controlled, it is possible to match the average current of the non-square wave pulse current flowing into the electromagnetic solenoid with the average current of the square wave pulse current aimed by controlling the external input variable voltage. Therefore, in the control circuit according to the present invention, it is possible to accurately control the average current of the non-square wave pulse current flowing into the electromagnetic solenoid by controlling the external input variable voltage, and thus accurately controlling the operation of the solenoid valve. can do. Accordingly, when the electromagnetic valve is used as a capacity control valve of a variable capacity compressor, for example, the discharge capacity of the compressor can be accurately controlled.
[0011]
According to the present invention, there is provided a control circuit for an electromagnetic valve having an electromagnetic solenoid that is duty-controlled via a semiconductor switching element, and a semiconductor switching element protection diode disposed in parallel to the electromagnetic solenoid. Current-voltage conversion circuit that converts square-wave pulse current flowing into the square-wave pulse voltage, low-pass filter that converts square-wave pulse voltage that is the output of the current-voltage conversion circuit to DC voltage, and the output voltage of the low-pass filter is inverted The error amplifier that is input to the input side and the external input variable voltage is input to the non-inverting input side, the triangular wave oscillator, the output voltage of the triangular wave oscillator is input to the inverting input side, and the output voltage of the error amplifier is input to the non-inverting input side And a semiconductor switching element to which a square wave pulse voltage that is an output of the PWM comparator is input In a control circuit having a drive circuit, a voltage that amplifies the output voltage of the low-pass filter by the ratio of the average current of the non-square wave pulse current flowing through the electromagnetic solenoid and the average current of the square wave pulse current flowing from the DC power supply to the solenoid valve With amplification meansThe voltage amplification means includes an amplification circuit disposed between the low-pass filter and the error amplifier, a duty ratio detection circuit disposed branched from a wiring connecting the semiconductor switching element driving circuit and the semiconductor switching element, and The amplification ratio determination circuit connected to the duty ratio detection circuit is connected to the amplification ratio determination circuit, and the duty ratio detection circuit detects the duty ratio of the square wave output voltage of the PWM comparator. The ratio of the time average value of the non-square wave pulse current flowing through the electromagnetic solenoid measured in advance and the time average value of the square wave pulse current flowing from the DC power supply to the solenoid valve and the duty ratio of the square wave output voltage of the PWM comparator And the detected duty ratio of the square wave output voltage of the PWM comparator, the amplifying ratio determining circuit flows through the electromagnetic solenoid. Determining the ratio of the time-averaged value of the square wave pulse current flowing time average value of the scan current from the DC power supply to the electromagnetic valve, the amplifier circuit amplifying the output voltage of the low-pass filter at the determined ratioA control circuit is provided.
[0012]
In the control circuit according to the present invention, the output voltage of the low-pass filter is amplified by the ratio of the average current of the non-square wave pulse current flowing through the electromagnetic solenoid and the average current of the square wave pulse current flowing from the DC power supply to the solenoid valve, Since the ON pulse width of the square wave output voltage of the PWM comparator is controlled based on the amplified voltage and the external input variable voltage, the average current of the square wave pulse current aimed by controlling the external input variable voltage can be obtained. The average current of the non-square wave pulse current flowing into the electromagnetic solenoid can be matched. Therefore, in the control circuit according to the present invention, it is possible to accurately control the average current of the non-square wave pulse current flowing into the electromagnetic solenoid by controlling the external input variable voltage, and thus accurately controlling the operation of the solenoid valve. can do. Therefore, when the solenoid valve is used as a capacity control valve of a variable capacity compressor, for example, the discharge capacity of the compressor can be accurately controlled.
[0013]
DETAILED DESCRIPTION OF THE INVENTION
A solenoid valve control circuit according to a first embodiment of the present invention will be described with reference to FIGS.
As can be seen from FIG. 2, in the control circuit according to this embodiment, a voltage addition circuit 12 is disposed between the current-voltage conversion circuit 9 and the low-pass filter 10. The voltage addition circuit 12 includes a diode 12a disposed on a wiring connecting the current-voltage conversion circuit 9 and the low-pass filter 10, and a wiring connecting the current-voltage conversion circuit 9 and the low-pass filter 10 on the downstream side of the diode 12a. Capacitor 12b branched from the capacitor 12b and a resistor 12c branched from the wiring connecting the current-voltage conversion circuit 9 and the low-pass filter 10 on the downstream side of the capacitor 12b. The capacitor 12b and the resistor 12c are grounded. Except for the above, the configuration of the control circuit according to the present embodiment is the same as the configuration of the control circuit of FIG.
[0014]
In the control circuit according to the present embodiment, when the square-wave pulse current flowing from the DC power supply 3 to the solenoid valve A is OFF, electric charges are discharged from the capacitor 12b of the voltage addition circuit 12 via the resistor 12c, and the voltage E (t) 'Occurs. The voltage E (t) ′ is obtained by converting the current flowing into the electromagnetic solenoid 1 via the protective diode 8 into a voltage by the current-voltage conversion circuit 9 when the square wave pulse current flowing from the DC power supply 3 into the solenoid valve A is OFF. The voltage is equal to the output voltage of the current-voltage conversion circuit 9 in this case.
[0015]
When the square wave pulse current flowing from the DC power source 3 to the solenoid valve A is OFF, the current flowing into the solenoid 1 via the protective diode 8 is converted into a voltage by the current-voltage conversion circuit 9. The conditions for achieving a voltage equal to the output voltage of the current-voltage conversion circuit 9 will be considered below.
As shown in FIG. 3A, current I (t) flows to the electromagnetic solenoid 1 via the protective diode 8 when the square wave pulse current flowing from the DC power supply 3 to the electromagnetic valve A is OFF. At this time, the relationship between the voltage E (t) applied to the electromagnetic solenoid 1 and the current I (t) flowing to the electromagnetic solenoid 1 via the protective diode 8 is as follows:
I (t) = (R1/ L1) ∫ [E (t) / R1 -I (t)] dt …… ▲ 1 ▼
It is represented by Where R1Is the resistance value of electromagnetic solenoid 1, L1Is the inductance value of the coil 1a of the electromagnetic solenoid 1.
As shown in FIG. 3B, when the square wave pulse current flowing from the DC power source 3 to the solenoid valve A is OFF, a current I (t) ′ flows from the capacitor 12b to the resistor 12c. At this time, the relationship between the potential E (t) ′ of the capacitor 12b and the potential E (t) ″ downstream of the resistor 12c is
E (t) ′ = (1 / (R2C2)) ∫ [E (t) ″-E (t) ′] dt …… ▲ ▼▼
It is represented by Where R2Is the resistance value of the resistor 12c, and C2Is the capacitance value of the capacitor 12b.
[0016]
From ▲ 1 ▼ and ▲ 2 ▼,
R1/ L1 = 1 / (R2C2(3)
E (t) / R1 = AE (t) ″ …… ▲ 4 ▼
If
I (t) = AE (t) '... 5
It turns out that it becomes. Here, A is an arbitrary constant.
Here, since E (t) ≈0 and the resistor 12c is grounded and E (t) ″ = 0, the condition (4) is established. Therefore, the voltage adding circuit 12 is established so that the condition (3) is established. Capacitance value C of capacitor 12b2And the resistance value R of the resistor 12c2Is set to a voltage E (t) ′ proportional to the current I (t) flowing to the electromagnetic solenoid 1 via the protective diode 8 when the square wave pulse current flowing from the DC power supply 3 to the electromagnetic valve A is OFF. It can be generated in the voltage adding circuit 12.
[0017]
On the other hand, when the square wave pulse current flowing from the DC power source 3 to the solenoid valve A is ON, the relationship between the current i (t) flowing to the solenoid 1 and the output voltage ε (t) of the current-voltage conversion circuit 9 is
i (t) = aε (t) ・ ・ ・ ・ ・ ・ ▲ 6 ▼
It becomes.
At the moment when the square wave pulse current flowing into the solenoid valve A from the DC power supply 3 is turned off, i (t) = I (t) and ε (t) = E (t) ', so a = A It is. Since a is a conversion constant inherent to the current-voltage conversion circuit 9, the current I (t) flowing to the electromagnetic solenoid 1 via the protection diode 8 is the current voltage when the square wave pulse current flowing from the DC power supply 3 to the solenoid valve A is OFF. The voltage is converted to voltage E (t) ′ with a conversion constant A equal to the conversion constant a unique to the conversion circuit 9.
From the above, the capacitance value C of the capacitor 12b of the voltage adding circuit 12 is established so that (3) is established.2And the resistance value R of the resistor 12c2When the square wave pulse current flowing from the DC power source 3 to the solenoid valve A is OFF, the voltage adding circuit 12 converts the current flowing into the electromagnetic solenoid 1 through the protection diode 8 into a voltage by the current-voltage conversion circuit 9. It can be seen that a voltage equal to the output voltage of the current-voltage conversion circuit 9 is generated.
[0018]
According to the control device of the present embodiment, the current flowing into the electromagnetic solenoid 1 via the protection diode 8 when the square wave pulse current flowing into the solenoid valve A from the DC power supply 3 is OFF is converted into a voltage by the current-voltage conversion circuit 9. A voltage equal to the output voltage of the current-voltage conversion circuit 9 when converted is added to the square-wave pulse voltage that is the output of the current-voltage conversion circuit 9, and the added non-square-wave pulse voltage and the external input variable voltage 6 are added. Based on this, the ON pulse width of the square wave output voltage of the PWM comparator 5 is controlled, so that the non-square shape that flows into the electromagnetic solenoid 1 into the average current of the square wave pulse current aimed by controlling the external input variable voltage 6 is controlled. The average current of the wave pulse current can be matched.
More specifically, when the square wave pulse current flowing from the DC power source 3 to the solenoid valve A is OFF, the current when the current flowing into the electromagnetic solenoid 1 through the protective diode 8 is converted into a voltage by the current-voltage conversion circuit 9 When a voltage equal to the output voltage of the voltage conversion circuit 9 is added to the square wave pulse voltage that is the output of the current-voltage conversion circuit 9, the output voltage of the low-pass filter 10 increases by the additional voltage. As a result, the duty ratio of the square wave output voltage of the PWM comparator 5 is reduced by the additional voltage from the predetermined value of the external input variable voltage 6, and the square wave pulse current flowing from the DC power supply 3 to the solenoid valve A is reduced. , The external input variable voltage 6 is also reduced by the additional voltage from the expected value. Decrease in the average current of the pulse current flowing through the electromagnetic solenoid 1 caused by the duty ratio of the square wave pulse current flowing into the solenoid valve A from the DC power source 3 being reduced from the predetermined value of the external input variable voltage 6 However, an increase in the average current of the pulse current flowing through the electromagnetic solenoid 1 caused by the current flowing into the electromagnetic solenoid 1 through the protective diode 8 when the square wave pulse current flowing into the electromagnetic valve A from the DC power source 3 is OFF. cancel. As a result, the average current of the pulse current flowing through the electromagnetic solenoid 1 becomes a value that the external input variable voltage 6 is scheduled.
Therefore, in the control circuit according to the embodiment, it is possible to accurately control the average current of the non-square wave pulse current flowing into the electromagnetic solenoid 1 by controlling the external input variable voltage 6, and consequently the operation of the electromagnetic valve A. It can be controlled accurately. Therefore, when the electromagnetic valve A is used as a capacity control valve of a variable capacity compressor, for example, the discharge capacity of the compressor can be accurately controlled.
[0019]
A solenoid valve control circuit according to a second embodiment of the present invention will be described with reference to FIGS.
As can be seen from FIG. 4, in the control circuit according to the present embodiment, an amplifier circuit 13 is disposed between the low-pass filter 10 and the error amplifier 11. A duty ratio detection circuit 14 is arranged branched from the wiring connecting the semiconductor switching element drive circuit 7 and the semiconductor switching element 2, and an amplification ratio determination circuit 15 is connected to the duty ratio detection circuit 14. An amplification circuit 13 is connected to the amplification ratio determination circuit 15. Except for the above, the configuration of the control circuit according to the present embodiment is the same as the configuration of the control circuit of FIG.
Average current I of square wave pulse current flowing from DC power supply 3 to solenoid valve A1And the average current I of the non-square wave pulse current flowing through the electromagnetic solenoid 12As shown in FIG.
I2/ I1= f (duty ratio of the square wave output voltage of the PWM comparator 5) (7)
There is a relationship.
The function f is a function that depends on the characteristics of the solenoid valve A. If the characteristics of the solenoid valve A are fixed, the duty ratio of the square wave output voltage of the PWM comparator 5 is changed to I2/ I1Can be obtained by measuring If the characteristic of the solenoid valve A is determined, the inventor of the present application is a function of only the duty ratio of the square wave output voltage of the PWM comparator 5 and is not affected by the change in the voltage of the DC power supply 3. This is confirmed by experiments.
[0020]
In the control circuit according to the present embodiment, the duty ratio detection circuit 14 detects the duty ratio of the square wave output voltage of the PWM comparator 5, and the function f preset by measurement and the PWM detected by the duty ratio detection circuit 14 are detected. Based on the duty of the square wave output voltage of the comparator 5, the amplification ratio determining circuit 152/ I1To decide. The amplifier circuit 13 converts the output voltage of the low-pass filter 10 to I2/ I1Amplify twice.
In the control circuit according to the present embodiment, the output voltage of the low-pass filter 10 is used as the average current I of the non-square wave pulse current flowing through the electromagnetic solenoid 1.2And the average current I of the square wave pulse current flowing into the solenoid valve A from the DC power source 31Ratio I2/ I1Since the ON pulse width of the square wave output voltage of the PWM comparator 5 is controlled based on the amplified voltage and the external input variable voltage 6, the square shape aimed by controlling the external input variable voltage 6 is controlled. The average current of the non-square wave pulse current flowing into the electromagnetic solenoid 1 can be matched with the average current of the wave pulse current.
More specifically, the output voltage of the low-pass filter 10 is I2/ I1Therefore, the duty ratio of the square wave output voltage of the PWM comparator 5 is reduced by an amount corresponding to the amplification of the external input variable voltage 6 and flows into the solenoid valve A from the DC power supply 3. The duty ratio of the square-wave pulse current is also reduced by the amplification from the value that the external input variable voltage 6 has planned. Decrease in the average current of the pulse current flowing through the electromagnetic solenoid 1 caused by the duty ratio of the square wave pulse current flowing into the solenoid valve A from the DC power source 3 being reduced from the predetermined value of the external input variable voltage 6 However, an increase in the average current of the pulse current flowing through the electromagnetic solenoid 1 caused by the current flowing into the electromagnetic solenoid 1 through the protective diode 8 when the square wave pulse current flowing into the electromagnetic valve A from the DC power source 3 is OFF. cancel. As a result, the average current of the pulse current flowing through the electromagnetic solenoid 1 becomes a value that the external input variable voltage 6 is scheduled.
Therefore, in the control circuit according to the embodiment, it is possible to accurately control the average current of the non-square wave pulse current flowing into the electromagnetic solenoid 1 by controlling the external input variable voltage 6, and consequently the operation of the electromagnetic valve A. It can be controlled accurately. Therefore, when the electromagnetic valve A is used as a capacity control valve of a variable capacity compressor, for example, the discharge capacity of the compressor can be accurately controlled.
[0021]
【The invention's effect】
As described above, in the control circuit according to the present invention, the current flowing into the electromagnetic solenoid via the protection diode when the square wave pulse current flowing into the solenoid valve from the DC power source is turned off is converted into a voltage by the current-voltage conversion circuit. The voltage equal to the output voltage of the current-voltage converter circuit is added to the square-wave pulse voltage that is the output of the current-voltage converter circuit, and the PWM comparison is made based on the non-square-wave pulse voltage after addition and the external input variable voltage Because the ON pulse width of the square wave output voltage of the detector is controlled, the average current of the non-square wave pulse current flowing into the electromagnetic solenoid matches the average current of the square wave pulse current aimed by controlling the external input variable voltage. Can be made. Therefore, in the control circuit according to the present invention, it is possible to accurately control the average current of the non-square wave pulse current flowing into the electromagnetic solenoid by controlling the external input variable voltage, and thus accurately controlling the operation of the solenoid valve. can do. Accordingly, when the electromagnetic valve is used as a capacity control valve of a variable capacity compressor, for example, the discharge capacity of the compressor can be accurately controlled.
[0022]
In the control circuit according to the present invention, the output voltage of the low-pass filter is amplified by the ratio of the average current of the non-square wave pulse current flowing through the electromagnetic solenoid and the average current of the square wave pulse current flowing from the DC power supply to the solenoid valve, Since the ON pulse width of the square wave output voltage of the PWM comparator is controlled based on the amplified voltage and the external input variable voltage, the average current of the square wave pulse current aimed by controlling the external input variable voltage can be obtained. The average current of the non-square wave pulse current flowing into the electromagnetic solenoid can be matched. Therefore, in the control circuit according to the present invention, it is possible to accurately control the average current of the non-square wave pulse current flowing into the electromagnetic solenoid by controlling the external input variable voltage, and thus accurately controlling the operation of the solenoid valve. can do. Accordingly, when the electromagnetic valve is used as a capacity control valve of a variable capacity compressor, for example, the discharge capacity of the compressor can be accurately controlled.
[Brief description of the drawings]
FIG. 1 is a circuit diagram of a conventional solenoid valve control circuit.
FIG. 2 is a circuit diagram of a control circuit for a solenoid valve according to a first embodiment of the present invention.
FIG. 3 is a diagram illustrating a solenoid valve control circuit according to a first embodiment of the present invention. FIG. 3 shows a current flowing in an electromagnetic solenoid of a solenoid valve when a square wave pulse current flowing into the solenoid valve is OFF, and a square wave pulse flowing into the solenoid valve. It is a figure explaining the relationship with the voltage which generate | occur | produces in the voltage addition circuit of a control circuit at the time of electric current OFF. (A) is a figure explaining the electric current which flows into the electromagnetic solenoid of a solenoid valve, (b) is a figure explaining the voltage which generate | occur | produces in the voltage addition circuit of a control circuit.
FIG. 4 is a circuit diagram of a control circuit for a solenoid valve according to a second embodiment of the present invention.
FIG. 5: Average current I of square wave pulse current flowing from a DC power supply to a solenoid valve1And the average current I of the non-square wave pulse current flowing through the electromagnetic solenoid2It is a figure which shows the relationship between.
[Explanation of symbols]
1 Electromagnetic solenoid
1a coil
1b Plunger
2 Semiconductor switching element
3 DC power supply
4 Triangular wave transmission circuit
5 PWM comparator
6 External input variable voltage
7 Semiconductor switching element drive circuit
8 Semiconductor switching element protection diode
9 Current-voltage conversion circuit
10 Low-pass filter
11 Error amplifier
12 Voltage addition circuit
12a diode
12b capacitor
12c resistance
13 Amplifier circuit
14 Duty ratio detection circuit
15 Amplification ratio determination circuit

Claims (2)

半導体スイッチング素子を介してデューティー制御される電磁ソレノイドと、電磁ソレノイドに並列に配設された半導体スイッチング素子保護ダイオードとを有する電磁弁の制御回路であって、直流電源から電磁弁へ流入する方形波パルス電流を方形波パルス電圧に変換する電流電圧変換回路と、電流電圧変換回路の出力である方形波パルス電圧を直流電圧に変換するローパスフィルタと、ローパスフィルタの出力電圧が反転入力側に入力され外部入力可変電圧が非反転入力側に入力される誤差増幅器と、三角波発振器と、三角波発振器の出力電圧が反転入力側に入力され誤差増幅器の出力電圧が非反転入力側に入力されるＰＷＭ比較器と、ＰＷＭ比較器の出力である方形波パルス電圧が入力される半導体スイッチング素子駆動回路とを有する制御回路において、直流電源から電磁弁へ流入する方形波パルス電流のＯＦＦ時に保護ダイオードを介して電磁ソレノイドへ流入する電流を電流電圧変換回路で電圧に変換した場合の電流電圧変換回路の出力電圧に等しい電圧を、電流電圧変換回路の出力である方形波パルス電圧に付加する電圧付加手段を備え、電圧付加手段は、電流電圧変換回路とローパスフィルタとを接続する配線上に配設されたダイオードと、ダイオードの下流側で電流電圧変換回路とローパスフィルタとを接続する配線から分岐して配設されたコンデンサと、コンデンサの下流側で電流電圧変換回路とローパスフィルタとを接続する配線から分岐して配設された抵抗とを有しており、コンデンサと抵抗とはアースされており、電磁ソレノイドの抵抗値を R 1 とし、電磁ソレノイドのコイルのインダクタンスを L 1 とし、電圧付加手段の抵抗の抵抗値を R ２ とし、電圧付加手段のコンデンサの容量値を C ２ とした時に、 R 1 /
L 1 = 1/( R ２ C ２ ) が成立するように、電圧付加手段の抵抗の抵抗値 R ２ と、電圧付加手段のコンデンサの容量値 C ２ とが設定されていることを特徴とする制御回路。A control circuit for an electromagnetic valve having an electromagnetic solenoid duty-controlled through a semiconductor switching element and a semiconductor switching element protection diode arranged in parallel with the electromagnetic solenoid, wherein the square wave flows from a DC power source to the electromagnetic valve The current-voltage conversion circuit that converts the pulse current into a square-wave pulse voltage, the low-pass filter that converts the square-wave pulse voltage that is the output of the current-voltage conversion circuit into a DC voltage, and the output voltage of the low-pass filter are input to the inverting input side An error amplifier in which an external input variable voltage is input to the non-inverting input side, a triangular wave oscillator, and a PWM comparator in which the output voltage of the triangular wave oscillator is input to the inverting input side and the output voltage of the error amplifier is input to the non-inverting input side And a semiconductor switching element driving circuit to which a square wave pulse voltage that is an output of the PWM comparator is inputted. In the control circuit, when the square wave pulse current flowing from the DC power supply to the solenoid valve is OFF, the current flowing into the electromagnetic solenoid via the protection diode is converted into a voltage by the current-voltage conversion circuit. Voltage adding means for adding an equal voltage to the square-wave pulse voltage that is the output of the current-voltage conversion circuit , the voltage addition means comprising a diode disposed on the wiring connecting the current-voltage conversion circuit and the low-pass filter; The capacitor is branched from the wiring connecting the current-voltage conversion circuit and the low-pass filter on the downstream side of the diode, and is branched from the wiring connecting the current-voltage conversion circuit and the low-pass filter on the downstream side of the capacitor. has a disposed resistor, the capacitor and the resistor are grounded, the resistance value of the electromagnetic solenoid and R 1, electrostatic The inductance of the coil of the solenoid and L 1, the resistance value of the resistance of the voltage adding means and R 2, the capacitance of the capacitor of the voltage adding means when a C 2, R 1 /
L 1 = 1 / As (R 2 C 2) is satisfied, the resistance value R 2 of the resistor of the voltage adding means, characterized by Rukoto and the capacitance value C 2 of the capacitor voltage adding means is configured Control circuit. 半導体スイッチング素子を介してデューティー制御される電磁ソレノイドと、電磁ソレノイドに並列に配設された半導体スイッチング素子保護ダイオードとを有する電磁弁の制御回路であって、直流電源から電磁弁へ流入する方形波パルス電流を方形波パルス電圧に変換する電流電圧変換回路と、電流電圧変換回路の出力である方形波パルス電圧を直流電圧に変換するローパスフィルタと、ローパスフィルタの出力電圧が反転入力側に入力され外部入力可変電圧が非反転入力側に入力される誤差増幅器と、三角波発振器と、三角波発振器の出力電圧が反転入力側に入力され誤差増幅器の出力電圧が非反転入力側に入力されるＰＷＭ比較器と、ＰＷＭ比較器の出力である方形波パルス電圧が入力される半導体スイッチング素子駆動回路とを有する制御回路において、電磁ソレノイドを流れる非方形波パルス電流の時間平均値と直流電源から電磁弁へ流入する方形波パルス電流の時間平均値の比で、ローパスフィルタの出力電圧を増幅する電圧増幅手段を備え、電圧増幅手段は、ローパスフィルタと誤差増幅器との間に配設された増幅回路と、半導体スイッチング素子駆動回路と半導体スイッチング素子とを接続する配線から分岐して配設されたデューティー比検出回路と、デューティー比検出回路に接続された増幅比決定回路とを有し、増幅比決定回路に増幅回路が接続されており、ＰＷＭ比較器の方形波出力電圧のデューティー比をデューティー比検出回路が検出し、予め計測された電磁ソレノイドを流れる非方形波パルス電流の時間平均値と直流電源から電磁弁へ流入する方形波パルス電流の時間平均値の比とＰＷＭ比較器の方形波出力電圧のデューティー比との相関と検出したＰＷＭ比較器の方形波出力電圧のデューティー比とを用いて増幅比決定回路が電磁ソレノイドを流れる非方形波パルス電流の時間平均値と直流電源から電磁弁へ流入する方形波パルス電流の時間平均値の比を決定し、決定した比で増幅回路がローパスフィルタの出力電圧を増幅することを特徴とする制御回路。A control circuit for an electromagnetic valve having an electromagnetic solenoid duty-controlled through a semiconductor switching element and a semiconductor switching element protection diode arranged in parallel with the electromagnetic solenoid, wherein the square wave flows from a DC power source to the electromagnetic valve The current-voltage conversion circuit that converts the pulse current into a square-wave pulse voltage, the low-pass filter that converts the square-wave pulse voltage that is the output of the current-voltage conversion circuit into a DC voltage, and the output voltage of the low-pass filter are input to the inverting input side An error amplifier in which an external input variable voltage is input to the non-inverting input side, a triangular wave oscillator, and a PWM comparator in which the output voltage of the triangular wave oscillator is input to the inverting input side and the output voltage of the error amplifier is input to the non-inverting input side And a semiconductor switching element driving circuit to which a square wave pulse voltage that is an output of the PWM comparator is inputted. In the control circuit, voltage amplifying means for amplifying the output voltage of the low-pass filter by the ratio of the time average value of the non-square wave pulse current flowing through the electromagnetic solenoid and the time average value of the square wave pulse current flowing from the DC power supply to the solenoid valve The voltage amplification means includes an amplification circuit disposed between the low-pass filter and the error amplifier, and a duty ratio detection circuit disposed by branching from a wiring connecting the semiconductor switching element driving circuit and the semiconductor switching element. And an amplification ratio determination circuit connected to the duty ratio detection circuit, the amplification circuit is connected to the amplification ratio determination circuit, and the duty ratio detection circuit detects the duty ratio of the square wave output voltage of the PWM comparator. The time average value of the non-square wave pulse current flowing through the electromagnetic solenoid measured in advance and the square wave flowing from the DC power source to the solenoid valve The amplification ratio determining circuit flows through the electromagnetic solenoid using the correlation between the ratio of the time average value of the pulse current and the duty ratio of the square wave output voltage of the PWM comparator and the detected duty ratio of the square wave output voltage of the PWM comparator. the ratio of the time-averaged value of the square wave pulse current flowing time average value of the non-square wave pulse current from the DC power supply to the electromagnetic valve determined, the amplifier circuit at the determined ratio that you amplifies the output voltage of the low-pass filter Characteristic control circuit.
JP24129699A 1999-08-27 1999-08-27 Solenoid valve control circuit Expired - Fee Related JP4201928B2 (en)

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JP24129699A JP4201928B2 (en) 1999-08-27 1999-08-27 Solenoid valve control circuit
DE2000141958 DE10041958B4 (en) 1999-08-27 2000-08-25 Control circuit for an electromagnetic valve

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