JPS5832482B2 - Transformer winding for phase control device - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION The present invention relates to a transformer winding for a phase control device, and particularly to a method of winding a phase control winding and a switching winding in a secondary winding thereof.

Prior to explaining the present invention, first, a control method and an induced disturbance will be explained for electric vehicles in which phase control transformers are often used.

There are various control methods used in electric vehicles, but here we will explain a method in which the secondary winding of the transformer is divided into five equal parts.

FIG. 1 is a diagram showing the principle of such a 5-piece unequal division method.

In this figure, Tr is a transformer consisting of an iron core 1, a negative winding 2, a secondary winding consisting of a phase control winding 3, a switching winding 4 and non-control windings 5, 6.7. It is configured.

These phase control winding 3, switching winding 4 and non-control winding 5
, 6.7 are the turns ratios, that is, the terminal voltages E2□, E
2□l E231 E24.

The voltage ratio of E25 is 1:1:2:2:2, and each rectifier unit consists of thyristor 8 and diode 9)
Connected to MRf1 to MRf5.

Further, MSL is a smoothing reactor, MM is a main motor armature, and MF is a field winding.

As shown in FIG. 2, the operation starts with phase control angles α1 to α, =180°
, it is in a blocking state, and the DC voltage ed=O.

When trying to increase the total voltage, in notch 1, by controlling the phase control angle α1 from 180°→0°, e=o→
ed1 (edl is a DC voltage corresponding to E21, and ed2 to ed below are also DC voltages corresponding to E2□ to E25) (step 1).

Next, set α1 = 180° and at the same time fire α2 (α2
=O°) Then E2, =E2□, so ed is ed
2, which remains unchanged (step 2).

In notch 2, by controlling α1-1800→0°, ed=ed2→ed2+ed1 (step 3
).

Furthermore, at the same time α1 is set to α2−180° (blocking state), α3 is turned on (conducting state).

At this time, since E23=E21+E2□, ed becomes ed3, which remains unchanged (step 4).

In Notch 3, by controlling α1-180°→0°, ed=eds→ed3+ed1 (step 5)
.

By repeating these steps, finally ed=
It is controlled up to ed1+ed2+ed3+ed4+ed5.

The characteristics required of the transformer in this control are as follows: When α1 is set to 180' (blocking state) and α2 is simultaneously turned on (conducting state) in step 2, that is, the control winding 3 of the transformer is When the switching winding 4 is switched, the reactance x2 seen from the control winding 3 and the actance X22 seen from the switching winding 4 are equal, so that X21=X
If it is 2□, smooth transition can be made without voltage fluctuation.

However, when X2□\X2□, the following problem occurs.

That is, all electric cars currently use DC series motors, and the speed-current characteristics of electric cars can be expressed from this characteristic.

This is shown in FIG. 3 for step 2 described above.

As can be seen from this figure, when using the control winding 3 of the transformer (reactance X21), if the characteristic is shown by curve A, when X22<X2□, the characteristic is shown by curve B, When X2゜〉X21, the characteristic is shown by curve C.

If the control winding 3 of the transformer is switched to the switching winding 4 when the DC current is running at Id-Id', then when the characteristic is shown by curve B, ■d'→I a /
/ causes an increase in current.

On the other hand, in the case of the characteristic shown by curve C, the current decreases from ■d' to ■d'''.

When the characteristic is shown by curve C, the immediate rectification unit) MRfl
This can be prevented by providing a control function that increases the voltage by controlling the phase control angle α1 of curve B.
In the case of the characteristics shown in , it cannot be prevented by control or other means.

Therefore, in the case of this control method, the transformer reactance should be X2l-X2□, or it must be X21
When \X2□, the characteristic shown by curve C is X2□〉X2,
Must be.

Next, induced failure will be explained.

In the case of electric railways, inductive disturbances are telephone communication disturbances due to noise in the audio frequency band induced in communication lines by currents flowing in overhead conductors and negative conductors.

Regarding communication interference, a combination of harmonic currents is called an equivalent interference current, which is expressed by the symbol JP and evaluated by Jp.

This Jp is calculated by the following formula.

The transformer-subcurrent current (teleline current) is as shown in Figure 4,
The waveform distortion is large and it contains many harmonic components, so that Jp tends to become a dog.

As seen from equation (1), Jp is determined by In, but In is approximated by equation (2).

Here, n: Coefficient, JILO: Rising part due to natural commutation uo: Overlapping angle due to natural commutation, (ILα: Phase control current Uα: Commutation type angle of phase control current Characteristics and equivalent disturbance of phase control winding When paying attention to the relationship between the current Jp, it can be seen from equation (2) that Jp can be reduced by increasing the overlap angle Uα in the second term in [ ].

The overlap angle Uα is the actance X21 seen from the control winding 3.
Therefore, if this reactance X21 becomes a dog, the overlap angle Uα also becomes a dog.

As explained above, for the control winding 3 and switching winding 4 of the transformer, from the control point of view, X2□=X22,
From the point of view of guidance obstacles, it is desirable to make X2□ a dog as much as possible.

By the way, as shown in FIG. 5, the conventional winding structure includes, from below, a secondary switching winding 4, a secondary phase control winding 3, a -order winding 2, secondary non-control windings 5 to 7, - arranged in the order of the next winding 2;

That is, since the control winding 3 and the switching winding 4 are required to have X21=X2□ or X2□<X2□ from the control surface, they are arranged adjacent to each other so that X21<X2□, and the sixth Each is wound separately as shown in the figure.

In FIG. 6, 8 indicates a lead wire.

Reactance X21 in such a conventional winding structure
is calculated using equation (3) (see Figure 7).

: Rogowski coefficient A2: Thickness of winding 3 = Thickness of winding 4) δ is the dimension between primary winding 2 and winding 3: A constant depending on the shape of secondary winding 2 Also, switching winding 4 The reactance X2□ is calculated using equation (4) (see Figure 7).

Here, the constants other than those in equation (3) are N2□: Number of turns of winding 4 (N2□ - N21) A2: Dimension between primary winding 2 and winding 4 From these equations (3) and (4) δ1〈A
2, so X2□〈N2゜.

The present invention has been made in view of these points, and its purpose is to reduce the fluctuation range of the reactance value as much as possible when switching from the phase control winding to the switching winding, and to stabilize the control. It is an object of the present invention to provide a transformer winding for a phase control device, which can reduce inductive disturbances by increasing the actance of the phase control winding as much as possible.

To achieve this objective, the invention is characterized in that the phase control winding and the switching winding are wound together in juxtaposition.

An embodiment of the present invention will be described below with reference to FIGS. 8 and 9.

In these figures, the same reference numerals as in FIGS. 5 and 6 indicate the same or equivalent parts.

As shown in FIG. 9, the phase control winding 3 and the switching winding 4 are wound together in parallel in the radial direction of the windings, that is, in the direction perpendicular to the main magnetic flux direction, and the other windings The structure is the same as the conventional example.

Therefore, the entire winding structure is as shown in FIG.

In this case, the reactance X2 of the control winding 3 (and the reactance X2□ of the switching winding 4) is calculated using equation (5) (see FIG. 10).

Here, the constants other than those in equation (3) are: A3: Thickness of windings 3 and 4. As seen from equations 3) to (5), since there is a relationship of A2 < A3 and δ1 × A2, X21〈N2(-X
The relationship is 26〈X2□.

Therefore, it can be seen that the winding structure as in the embodiment has the following advantages over the conventional structure.

(1) From the viewpoint of control, N2,'=X2≦, and smooth control is possible.

(2) The control winding flux actance can be set to N2;>X21, and the equivalent disturbance current Jp can be reduced.

(3) As can be seen from FIGS. 6 and 9, since the space for the lead wire 8 passing between the windings is not required, the gap between the windings becomes A2<dl, and the transformer is made smaller and lighter.

Note that the arrangement of each winding is not limited to the arrangement as in the above embodiment, for example, the non-control windings 5 to 7 may be arranged outside the primary winding 2, or the control winding 3 and the switching winding 4 may be arranged together. It is also possible to arrange a coil wound around the primary winding 2 between the primary windings 2, and in these cases, the same effects as in the embodiment described above can be obtained.

In addition, a control winding 3, a switching winding 4, and non-control windings 5 to 7
The winding ratio is not limited to 1:1:2:2:2, but also 1:1:
As long as the turn ratio of the control winding 3 and the switching winding 4 is 1:1, such as 1:1:1 or 1:1:2:4:4, the others can be arbitrarily selected.

Furthermore, in the embodiment, the control winding 3 and the switching winding 4
are arranged in parallel in the radial direction of the winding and wound together, but the first
As shown in FIGS. 1 and 12, the control winding 3 and the switching winding 4 can also be wound together in juxtaposition in the axial direction of the windings, ie in the same direction as the main magnetic flux direction.

In these cases, the separation distances between the control winding 3 and the switching winding 4 from the primary winding 2 are approximately equal, and it is easier to switch from the control winding 3 to the switching winding 4 than when winding each winding separately as in the past. These winding methods are effective in cases where a certain degree of coverage can be achieved by the control method, since the range of variation in the actance value upon transition can be reduced.

As explained above, according to the present invention, since the phase control winding and the switching winding are arranged side by side and wound together, the phase control winding and the switching winding have almost the same actance, and the phase control winding It is possible to reduce the fluctuation range of the actance value when switching from the winding to the switching winding, making it possible to perform stable control.

Further, since the reactance of the phase control winding becomes larger than when the phase control winding and the switching winding are wound separately, induction disturbances can also be reduced.

[Brief explanation of drawings]

Figure 1 is a diagram of the principle of the 5 unequal division control method for the secondary windings of an electric car transformer, Figure 2 is an explanatory diagram showing how the DC voltage changes due to the phase control of each rectifier unit, and Figure 3 is an electrical Vehicle speed-current characteristic diagram, Figure 4 is the primary current waveform diagram during phase control,
Fig. 5 is a winding configuration diagram showing the arrangement of each winding of a conventional phase control transformer, Fig. 6 is a sectional view showing the winding state of the conventional phase control winding and switching winding, and Fig. 7 is FIG. 8 is a reference explanatory diagram for calculating the winding flux actance of a conventional phase control transformer. FIG. 8 is a winding configuration diagram showing the arrangement of each winding of a phase control transformer according to an embodiment of the present invention. FIG. 10 is a sectional view showing an example of the winding state of the phase control winding and switching winding in the present invention, FIG. 10 is a reference explanatory diagram of the phase control transformer winding according to an embodiment of the present invention, and FIG. Figure and 1st
FIG. 2 is a sectional view showing the other side of the phase control winding and the switching winding according to the present invention. Explanation of symbols, 2... - next winding, 3...
Secondary phase control winding, 4...Secondary switching winding, 5~
7...Secondary uncontrolled winding.

Claims (1)

[Scope of Claims] A primary winding and a secondary winding consisting of a phase control winding, a switching winding, and a non-controlling winding, wherein the turns ratio of the phase control winding and the switching winding is 1. 1. A transformer winding for a phase control device, wherein the phase control winding and the switching winding are arranged side by side and wound together. 2. The transformer winding for a phase control device according to claim 1, wherein the phase control winding and the switching winding are arranged side by side in the radial direction of the winding and wound together.