JPH0347763B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention relates to a mixer device that can be used in transmitters and receivers for televisions, radios, stereo tuners, personal radios, and other communication devices in general.

Conventional configurations and their problems In recent years, the number of broadcast waves from televisions and radios and communication waves from communication devices has increased, and the performance of mixer devices that selectively output desired intermediate frequency signals requires high tuning accuracy, stability, and Reliability is needed. On the other hand, reducing the manufacturing costs of the receivers, transmitters, and communication devices that install the mixer equipment is also a major issue, and it is especially important to develop fundamental new technologies for the components of the mixer equipment in the high frequency section, which is difficult to rationalize. is necessary.

A conventional mixer device will be described below with reference to the drawings. FIG. 1 is a circuit configuration diagram of a conventional mixer device, in which 1 is a tuning inductor and 2 is a fixed capacitor, each of which constitutes a tuning circuit 3. An intermediate frequency output terminal 7 of a mixer 6 having a first input terminal 4 and a second input terminal 5 was connected to the tuning circuit 3.

Furthermore, FIG. 2 is a diagram of the conventional component configuration that constitutes the tuned circuit 3 in FIG. .
However, in the above configuration, the inductor parts and capacitor parts are large in size compared to other high-frequency parts, and their height is particularly high, which hinders the miniaturization and thinning of equipment in which the mixer device is installed. ing.

The inductance of an inductor component tends to shift due to mechanical vibration, and since the ferrite core has a large temperature dependence, the inductance is unstable, and the tuning frequency of an intermediate frequency tuner fluctuates greatly. Therefore, even if a mixer device is constructed, its intermediate frequency selection characteristics vary, and as a result, the intermediate frequency output signal level and unnecessary signal suppression characteristics vary greatly depending on the surrounding conditions.

The inductor component and the capacitor component exist as separate components and are connected by a long circuit conductor, resulting in a large amount of lead inductance and straight capacitor, making the operation of the intermediate frequency tuning circuit unstable. As a result, sufficient intermediate frequency selection characteristics cannot be secured,
Furthermore, problems such as unnecessary resonance phenomena occurring at uncertain frequency points occur, making it impossible to realize an intermediate frequency tuner as designed. This causes the occurrence of abnormal oscillation, the generation of spurious signals, an increase in distortion caused by an increase in harmonic components in the intermediate frequency signal, and furthermore, a deterioration of intermodulation interference rejection characteristics and spurious interference rejection characteristics. do.

Since the intermediate frequency tuning circuit is a collective circuit of independent minimum functional units, there is a limit to the reduction in the number of parts in the intermediate frequency tuner and the rationalization of manufacturing the mixer device using it.

It had problems such as.

OBJECT OF THE INVENTION An object of the present invention is to construct a mixer device equipped with a tuner formed by integrating an inductor part and a capacitor part, and further to make the form of the mixer device ultra-thin and compact. The mixing operation is stable against fluctuations in ambient conditions such as mechanical vibrations and temperature changes, and the intermediate frequency accuracy is high. Stable mixing operation is possible even in the high frequency range, excluding the negative effects of the connecting leads in the tuner. An object of the present invention is to provide a mixer device that enables rationalization of manufacturing by reducing the number of parts.

Structure of the Invention The oscillation device of the present invention is an oscillator in which the terminals connected to the ground of the electrodes that are arranged opposite to each other via a dielectric or arranged in parallel on the surface of the dielectric are arranged in opposite directions to each other in a tuner. The open terminal of one electrode of the tuner is connected to the intermediate frequency output terminal of the mixer, so that one electrode acts as a distributed inductor in the opposing or parallel electrodes of the tuner, and this An electrode that acts as a distributed inductor and the other electrode are placed opposite or in parallel to form a distributed constant circuit with an open tip, thereby realizing distributed capacitance due to the generated negative reactance, and connecting it in parallel with the above distributed inductor. The mixer function is obtained by connecting this tuning circuit to the mixer as a load or a precircuit for the mixer.

DESCRIPTION OF EMBODIMENTS Hereinafter, embodiments of the present invention will be described with reference to the drawings.

FIG. 3 shows a circuit configuration diagram of a mixer device in an embodiment of the present invention. Reference numeral 12 denotes a mixer, which mixes the input signals to be mixed that are input to the input terminals 13 and 14, respectively, and outputs an intermediate frequency output signal to the output terminal 15.
Output terminal 15 is connected to tuner 16 . In the tuner 16, reference numeral 17 is a transmission line electrode having an inductance due to the sum of a distributed inductor and a lumped inductor generated by bending the transmission line. On the other hand, 18 is a transmission line electrode that faces or is parallel to the transmission line electrode 17 via a dielectric (not shown) or on its surface. Then, the respective transmission line electrodes 17 and 18
The ground terminals are set to be on opposite sides of each other. Further, the input terminal 15 of the tuner 16 (common with the output terminal 15 of the mixer 12) is set to an open terminal of the transmission line electrode 17.

FIG. 4 shows a circuit diagram of a mixer device according to another embodiment of the present invention. A mixer 19 mixes the mixed input signals input to the input terminals 20 and 21, respectively, and outputs an intermediate frequency output signal to the output terminal 22. Output terminal 22 is connected to tuner 23 . In addition, input terminals 20 and 21 are connected to the tuner 2, respectively.
4 and 25, respectively. Tuner 2
3, 24, 25, 26, 27,
Each of the transmission line electrodes 28 is a transmission line electrode having an inductance due to the sum of the distributed inductor and the concentrated inductor generated by bending the transmission line electrode. On the other hand, 29, 30, 31
Each is a transmission line electrode that is paired with or parallel to each of the transmission line electrodes 26, 27, and 28 via a dielectric (not shown) or on its surface.
Then, the respective transmission line electrodes 26, 29, 27
The ground terminals of 30, 28, and 31 are set in opposite directions.
The input terminal 22 of the tuner 23 (commonly shared with the output terminal 22 of the mixer 19) is set to an open terminal of the transmission line electrode 26. Also,
Input terminals 20 and 21 in mixer 19 (common with output terminals 20 and 21 in tuners 24 and 25) are connected to transmission line electrodes 27 and 2, respectively.
8 each is set to open terminal. Here, voltage variable capacitance diodes 32 and 33 are connected to the tuners 24 and 25, respectively. As a result, a variable tuner is connected to each of the input terminals 20 and 21 of the mixer 19. That is, when an amplifier is connected and installed, for example, to the input terminal 34 provided on the transmission line electrode 30 of the tuner 24, a variable selection amplifier function is installed in front of the input terminal 34 provided on the transmission line electrode 30 of the tuner 25. Transmission line electrode 31
For example, when a feedback amplifier is connected to the input terminal 35 provided in the input terminal 35, a variable oscillation function is provided in advance. The variable control in each of the variable selection amplification function and the variable oscillation function depends on the control voltages input to the control terminals 36 and 37 of the voltage variable capacitance diodes 32 and 33. In this way, the input signals inputted to the input terminals 20 and 21 are mixed in the mixer 19, and the intermediate frequency signal obtained by the mixing action is supplied to the selective load circuit by the tuner 23 and transmitted. An intermediate frequency signal is output to an output terminal 38 provided on the path electrode 29.

In the embodiments shown in FIGS. 3 and 4 above, each of the terminals set to ground in each tuner 16, 23, 24, 25 is
Each tuner 16, 2 without connection to earth
3, 24, and 25 as a common terminal to connect to other circuits including the respective mixers, the desired purpose can be achieved. Further, a tuner 16,
The input terminals 15, 22 and the output terminals 20, 21 in 23, 24, 25 are not limited to being set at the tips of the respective transmission line electrodes 17, 26, 27, 28, but can be any arbitrary terminal having the required impedance. It can be set in the following position. Furthermore, the installation positions of the voltage variable capacitance diodes 32 and 33 are not limited to being connected to predetermined positions on the transmission line electrodes 27 and 28;
The desired purpose can be achieved by connecting it at any position in the .

In the embodiments shown in FIGS. 3 and 4 above, if it is necessary to adjust the tuning frequency in each tuner 16, 23, 24, 25,
Either cut out a required portion of the transmission line electrodes 18, 29, 30, 31, or remove the transmission line electrodes 17, 18, 26, 29, 27, 30, 28, 3.
By arbitrarily setting the ground terminal in 1 at a required location, the distributed capacitance and inductance can be changed, and the purpose can be achieved.

FIGS. 5 to 13 represent embodiments of the structure of the transmission line electrodes and dielectric material, representing the tuner 16 explained in FIG. 3. In Fig. 5, a is a surface view, b is a side view, and c
shows the back view. (The same applies to FIGS. 6 to 12 below) In FIG. 5, 100 is a dielectric substrate, and 101 and 102 are electrodes forming a distributed constant circuit to realize a distributed inductor and a distributed capacitor. The ground terminals of the electrodes 101 and 102 are set so that the opposing electrodes are arranged in opposite directions, as shown in FIG. (Hereafter, the 6th
13) The sides shown in FIG. 5a correspond to the sides shown in FIG. 6c, respectively. (The same applies to FIGS. 6 to 12 below) In FIG.
Electrodes 104 and 105 having bent portions are placed opposite each other.

In FIG. 7, electrodes 107 and 108 having a plurality of bent portions are placed facing each other with a dielectric substrate 106 in between.

In FIG. 8, meander-shaped electrodes 110 and 111 are placed facing each other with a dielectric substrate 109 in between.

In FIG. 9, spiral-shaped electrodes 113 and 114 are placed facing each other with a dielectric substrate 112 in between.

In FIG. 10, electrodes 116 and 117 are installed on the surface of a dielectric substrate 115, facing each other laterally.

In FIG. 1, electrodes 119 and 120 are provided inside a dielectric substrate 118, facing each other.

In FIG. 12, an electrode 122 is installed inside a dielectric substrate 121, an electrode 123 is installed on the surface of the dielectric substrate 121, and the electrodes 122 and 123 are opposed to each other.

FIG. 13 shows a configuration diagram of a tuner in another embodiment of the present invention. Cylindrical dielectric 12
4, an electrode 125 is installed on the inner periphery, and an electrode 126 is installed on the outer periphery facing the electrode 125. And each electrode 12
The ground terminals 5 and 126 are set to be on opposite sides of each other. Here, the dielectric 124
In addition to the cylindrical shape, a rectangular cylinder shape or a solenoid shape can also be used.

In the embodiments shown in FIGS. 5 to 13, the opposing electrodes have the same shape and completely face each other across the entire surface. However, even if one arbitrary electrode has a different equivalent length compared to the other electrode, It can also be realized by partially opposing the partner electrodes. Further, the shapes of the electrodes used in the embodiments shown in FIGS. 10 to 13 can also be realized using those shown in the embodiments shown in FIGS. 6 to 9.

Furthermore, in the embodiments shown in FIGS. 6 to 9, the bent portions are formed in an arcuate pattern having an arbitrary bending angle; It goes without saying that the electrode may be formed with a pattern of:

In each of the above embodiments, the ground terminal of each electrode does not have to be specially set as a ground terminal, but can generally be connected to other circuit parts (not shown) as a common terminal to achieve the desired purpose. I can do it. Furthermore, these ground terminals or common terminals are not limited to the ends of the respective electrodes, but can be arbitrarily set at respective portions that are in a mutually opposing positional relationship.

In each of the above embodiments, the one shown in FIG. 5 can be constructed with a simple electrode pattern, and a highly accurate electrode pattern can be easily formed. Thereby, it is possible to construct a tuner that precisely matches the design target tuning frequency. What is shown in FIGS. 6 to 9 allows relatively large inductors and capacitors to be formed even if the area occupied by the tuner is small. Therefore, a compact tuner with a relatively low tuning frequency can be realized, and the space factor of the tuner can be improved. In the case shown in FIG. 10, both electrodes can be formed on only one side of the dielectric, so the manufacturing process can be simplified. Furthermore, both electrodes can be formed by the same electrode forming process. Thereby, the positioning accuracy between the electrodes can be achieved with extremely high accuracy, and a tuner can be configured that matches the design target tuning frequency with extremely high accuracy. What is shown in FIGS. 11 and 12 can be introduced into the manufacturing process of multilayer circuit boards. As a result, the electrodes are placed inside the dielectric and are not exposed to the outside, so they are not directly affected by changes in external conditions. Therefore, since the tuning frequency of the tuner is not affected, it is possible to realize a tuner with extremely stable performance. 1st
Even if the tuner shown in FIG. 3 is made smaller than those shown in FIGS. 5 to 12, it is possible to form a sufficiently large inductor and capacitor. Therefore, an ultra-small tuner having a sufficiently low tuning frequency can be realized. Furthermore, when manufacturing the device shown in FIG. 13, the electrodes are formed on a continuous cylindrical dielectric material in succession, and then cut to the required length, thereby making it easy to manufacture in large quantities. It is possible to manufacture.

Note that metal conductors, printed metal foil conductors, thick film printed conductors, thin film conductors, etc. can be used as the transmission path electrodes in each of the above embodiments, and transmission path electrodes can also be formed by combining different types of conductors. may be formed. On the other hand, as the dielectric material, aluminium-ceramic, chitabari, plastic, Teflon, glass, mica, resin printed circuit board, etc. can be used.

The operation of the tuner of this embodiment configured as described above will be explained below.

FIG. 14 is an equivalent circuit for explaining the operation of the tuner of the present invention. In FIG. 14a, a signal source 72 that generates a voltage is connected to a transmission path formed by transmission path electrodes 70 and 71 that have an electrical length and are set on opposite sides of the ground terminal. It is assumed that it is connected to the transmission path electrode 70 to supply a signal. As a result, a traveling wave voltage _A is excited at the open terminal at the tip of the transmission line electrode 70. on the other hand,
Since the transmission line electrode 71 is disposed close to and opposite to the transmission line electrode 70, a voltage is induced by mutual induction. Let _B be the traveling wave voltage induced in the open terminal at the tip of the transmission line electrode 71.

Since the respective ground terminals of the transmission line electrodes 70 and 71 are set in opposite directions, the induced traveling wave voltage _B has an opposite phase to the excited traveling wave voltage _A. Since the tips of the transmission lines are open, the respective traveling wave voltages _A and _B are applied to the transmission line electrodes 70 and 7.
A voltage standing wave is formed in the transmission path consisting of 1. Here, if the voltage distribution coefficient indicating the distribution mode of the voltage standing wave in the transmission line electrode 70 is expressed as K, then the voltage distribution coefficient in the transmission line electrode 71 can be expressed as (1-K).

Therefore, next, we will discuss the potential difference V generated at any opposing portions of the transmission line electrodes 70 and 71.
can be expressed as V=Kl _A - (1-K)l _B (1). Here, if the respective transmission line electrodes 70 and 71 have the same electrical length l, then l _B = -l _A ...(2), so the potential difference V in the first equation is V = Kl _A + (1 -K) l _A = l _A ...(3). That is, a potential difference V can be generated in all parts where the transmission line electrodes 70 and 71 face each other.

Here, it is assumed that the transmission line electrodes 70 and 71 have an electrode width W (the thickness of the electrodes is thin), and are opposed to each other at a distance d via a dielectric material having a dielectric constant ε _S. . In this case, the capacitance formed per unit length of the transmission line
C _O is C _O =Q/V=Q/l _A ……(4) Q=ε _O ε _S W・V/d=ε _O ε _S W・l _A /d ……(5) Therefore, C _O = ε _O ε _S W/d ...(6).

Therefore, the transmission path shown in FIG. 14a is as shown in FIG. 14b.
It can be found using the 6th formula per unit length as shown in
This becomes a transmission path including a C _O distributed capacitor 73.

Furthermore, as shown in FIG. 14c, this transmission line has an overall distributed inductance 77 and 7 due to a distributed inductor component of the transmission line and a lumped inductor component generated due to the bent shape of the transmission line, respectively.
8 and a distributed capacitor 73.

Next, the relationship between the formation of the distributed capacitor 73 and the electrical length l of the transmission path will be explained. The characteristic impedance Z _O per unit length in a balanced mode transmission line as shown in FIG. 15a can be expressed by an equivalent circuit shown in FIG. 15b. Its characteristic impedance Z _O is generally becomes. If the transmission path is lossless, then becomes. This assumption can be applied to many of the embodiments of the tuner of the present invention, and to simplify the explanation, the characteristic impedance Z _O
Use. The capacitance C _O in the eighth equation is the same as the capacitance C _O per unit length of the transmission line found in the sixth equation. That is, the characteristic impedance per unit length Z _O in the transmission line is a function of the capacitance C _O , which is also a function of the permittivity ε _S of the dielectric material involved in the capacitor C _O ,
It is also a function of the width W of the transmission line electrodes and the installation interval d of each transmission line electrode.

As described above, the characteristic impedance per unit length in the transmission line is Z _O , the electrical length is l, and the equivalent reactance X generated at the terminal of the transmission line with the end open is X = -Z _O cotθ can be expressed as (9). Here, θ=2πl/λ...(10), and especially in the case of θ=O~π/2 θ=π~3/4π...(11), the equivalent reactance X is X≦O...(12) becomes. That is, the equivalent reactance at the terminal of the transmission line can be the capacitance reactance. Therefore, depending on the electrical length l of the transmission path, θ becomes the
When formula 11 is satisfied, for example, a capacitor can be formed by setting the electrical length l to λ/4 or less. And the capacitance C that can be formed is As expressed by , any capacitance C can be realized by changing θ, that is, by setting the electrical length l of the transmission path.

The operation mode of the transmission line explained above in Equations 9 to 13 is shown in the diagram in the 16th equation.
It is a diagram. FIG. 16 shows how the equivalent reactance X generated at the terminal changes in accordance with the change in the electrical length l of the transmission line with its tip in an open state. As is clear from Figure 16,
The electrical length l of the transmission line is λ/4 or less or λ/2 ~
In cases such as at 4λ/3, it is possible to form a negative terminal reactance, ie equivalently to form a capacitor.
Further, by arbitrarily setting the electrical length l of the transmission path under conditions that generate negative terminal reactance, it is possible to realize the capacitance C to an arbitrary value.

The capacitor C thus formed can be equivalently replaced as a lumped capacitor 79 shown in FIG. 14d. Furthermore, the inductor formed by the sum of the distributed inductor component existing in the transmission line and the concentrated inductor component generated by bending the transmission line is:
It can be equivalently replaced as a lumped constant inductor 80. If the ground terminal is shown in common in FIG. 14d, it will eventually become equivalent to a parallel resonant circuit consisting of a lumped constant capacitor 79 and a lumped constant inductor 80, as shown in FIG. 14e. can be realized.

Incidentally, in each of the above embodiments, each electrode is commonly connected to the ground, but it is also possible to connect the electrodes to the ground through a common terminal.

Mixers used in the mixer device described above include transistors, field effect transistors, and ICs.
It is possible to use a device using a semiconductor device such as , a device using a vacuum tube, or the like.

Effects of the Invention As is clear from the above description, the present invention configures a tuner with electrodes that are placed opposite to each other via a thin dielectric layer or arranged in parallel on the surface of the dielectric, and the tuner is connected to a mixer. Since it is configured to be connected to the input terminal and/or the output terminal, it is possible to configure a resonant circuit in a tuner used for a mixer device without installing a connection lead between the inductor and the capacitor, and also to tune it. can perform a function. Thereby, lead inductance and stray capacitance in the tuner can be completely eliminated. Therefore, unexpected resonance other than resonance at the target tuning frequency does not occur over a wide frequency band. As a result, stable frequency selection characteristics can be ensured, the level of the fundamental wave in the signal to be mixed can be made sufficiently high, and the level of its harmonic components can be sufficiently reduced. Therefore, distortion in the mixed signal can be significantly stabilized and reduced. Furthermore, by ensuring stable frequency selection characteristics, it becomes possible to sufficiently reduce the problems of intermodulation interference and spurious interference that occur when a large number of signals are mixed simultaneously.

Since a mixing device with a tuner that can be made into a module can be realized, there is no occurrence of constant fluctuations in the inductance and capacitor in the tuner due to mechanical vibration, and the mixing tuning characteristics are therefore extremely stable. be. In addition, by using a material with a low temperature dependence of dielectric constant as the dielectric material constituting the tuner, fluctuations in capacitance due to changes in ambient temperature can be made extremely small, thereby making it possible to extremely improve tuning characteristics. It can be made stable.
Therefore, the conversion gain characteristics and unnecessary interference signal rejection characteristics of the mixer device do not depend on changes in ambient conditions, and these characteristics are ensured stably not only during the initial stage of configuring the mixer device but also over a very long period of time. can do.

With a simple configuration, it is possible to realize a mixer device having an integrated tuner and having a very simple form. Furthermore, it becomes possible to realize an ultra-thin and compact mixer device. Therefore, the amount of unnecessary radiation of intermediate frequency signals and other signals radiated from the tuner can be extremely reduced. Thereby, not only can the mixing operation of the constituent mixer device itself be stabilized, but also there is no interference with other mixing systems.

If the circuit board constituting the mixer is shared as the dielectric used in the tuner in the mixer device, the mounting form in the mixer device can be rationalized. Moreover, it is thereby possible to further significantly reduce the number of parts constituting the tuner, thereby making it possible to realize a mixer device suitable for mass production, and to significantly reduce manufacturing costs.

This excellent effect can be obtained.

[Brief explanation of drawings]

Fig. 1 is a configuration circuit diagram of a conventional mixer device, Fig. 2 is a perspective view of a component configuration of a tuner used in a conventional mixer, and Figs. 3 and 4 are a diagram of a mixer device according to an embodiment of the present invention. 5 to 13 are configuration diagrams of a tuner used in a mixer device according to an embodiment of the present invention. In FIGS. 5 to 12, a is a surface view, b is a side view, and c is a side view. In FIG. 13, a is a side view, b is a top view, and FIGS. 14 to 16 are diagrams illustrating the operating principle of the tuner used in the mixer device in the embodiment of the present invention. 14, 19...Mixer, 16, 23, 24, 2
5... Tuner, 32, 33... Voltage variable capacitance diode, 17, 18, 26, 29, 2
7, 30, 28, 31, 101, 102, 10
4,105,107,108,110,111,
113, 114, 116, 117, 119, 12
0,122,123,125,126,70,7
1, 75, 76...Transmission line electrode, 100, 10
3,106,109,112,115,118,
121, 124...Dielectric material.

Claims (1)

[Scope of Claims] 1. A tuner group in which the common terminals connected to respective electrodes that are arranged opposite to each other via a dielectric material or arranged in parallel on the surface of a dielectric material are set in a different facing positional relationship so that they do not face each other. It is characterized by being connected to the input terminal and output terminal of the mixer directly or through a coupling element so that the tuning frequency of one tuner is equal to the difference in tuning frequency of the other two tuners. mixer equipment. 2 In multiple input signals input to the mixer,
The mixer device according to claim 1, wherein the frequency of all or some of the input signals is variable. 3 Claims 1 and 2, in which a tuner having a configuration similar to the tuner described in claim 1 is connected to the input signal terminal of the mixer directly or through another circuit element. The mixer device according to any one of Item 2. 4. The variable reactance element according to claim 2 or 3, wherein in each tuner, a variable reactance element is connected to an open terminal of one electrode of at least one tuner. Mixer equipment. 5 Claim 4 using a voltage variable capacitance diode as a variable reactance element
Mixer device as described in section. 6 Claim 1 using a tuner having at least one bending part exhibiting a predetermined bending angle or bending rate and a predetermined bending direction as an electrode
The mixer device according to any one of Items 5 to 6. 7. The mixer device according to any one of claims 1 to 5, using a tuner having a spiral shape as an electrode. 8. Any one of claims 1 to 7, which uses a tuner in which the length of one electrode is set shorter than the length of the other electrode, and the tuner is installed facing each other or in parallel at a predetermined portion. The mixer device described in . 9. The mixer device according to any one of claims 1 to 8, which uses a tuner in which each electrode or a part or all of one side of the electrode is installed inside the dielectric. 10. The mixer device according to any one of claims 1 to 9, which uses a tuner in which each electrode is installed at the inner circumference or outer circumference of a cylindrical or prismatic dielectric body. 11. The mixer device according to any one of claims 1 to 10, which uses a tuner that cuts out a required portion of one or both electrodes and controls the tuning frequency range to a predetermined tuning frequency range. 12. The mixer device according to claim 11, wherein a part of the electrode is cut out. 13. Claims according to any one of claims 1 to 12, which uses a tuner that sets and controls a tuning frequency range by setting a predetermined portion of one or both electrodes as a terminal connected to the ground. mixer equipment. 14. The mixer device according to any one of claims 1 to 13, wherein the common terminal is connected to ground.