JPH0360201B2 - - Google Patents

Description

DETAILED DESCRIPTION OF THE INVENTION Field of Industrial Application The present invention relates to a tuner that can be used in radio, television transmitters and receivers, and other communication devices in general.

Conventional configuration and its problems In recent years, the number of radio and television broadcast waves and communication waves of communication devices has increased, and the performance of the tuner that selects the frequency of the radio waves that you want to receive has a high level of stability. and reliability is required. On the other hand, reducing the manufacturing costs of receivers, transmitters, and communication devices that install tuners is also a major issue, and it is especially necessary to develop radical new technologies for tuning circuit components in the high frequency section, which are difficult to rationalize. has been done.

A conventional tuner will be described below with reference to the drawings. Figure 1 shows a basic tuning circuit, with 1
is an inductor, and 2 is a capacitor. and,
A tuner constituted by a parallel resonant circuit 3 consisting of an inductor 1 and a capacitor 2 has conventionally been realized with a configuration of components as shown in FIG. 2 or 3. That is, as shown in FIG. 2, separate components, an inductor component 4 and a capacitor component 5, are connected by circuit conductors 6 and 7 to form a tuner. Another method, as shown in FIG. 3, is to install a planar inductor 9 on the surface of a plate-shaped dielectric 8, and further install a capacitor 12 consisting of opposing electrodes 10 and 11, each with a separate inductor. 9 and capacitor 12 were connected by circuit conductors 13 and 14 to form a tuner.

However, in the above configuration, as shown in Figure 2, the inductor component 4 is large in size compared to other components, and in particular, the height dimension is very large, which makes it difficult to make the device smaller and thinner. was hindering the realization of Furthermore, the setting position of the ferrite core inserted into the coil of the inductor component fluctuates due to mechanical vibrations, resulting in extremely large fluctuations in the tuning frequency. Furthermore, the inductance is unstable due to the large temperature dependence of the magnetic permeability μ in the ferrite core, and this also causes the tuning frequency to fluctuate greatly. At the same time, the tuning Q was also affected and fluctuated greatly. Furthermore, in order to stably maintain the tuning frequency at the set target value, it is necessary to install each component with high precision in a predetermined setting position, and it is difficult to ensure the installation precision, especially when mass-producing a high frequency tuner. As a result, the tuning frequency deviates greatly from the set target value, and it is impossible to converge it to a constant value, which poses a problem in mass production.

The device shown in FIG. 3 occupies a large area due to the inductor and capacitor, which hinders the miniaturization of the device. Furthermore, each component requires at least three functional electrodes: an inductor electrode and a counter electrode that forms a capacitor, which requires the use of a large amount of electrode material that has high conductivity and is therefore expensive. This increases the manufacturing cost of the tuner and makes it impossible to save materials.

A common problem with those shown in Figures 2 and 3 is that the inductor and capacitor are each formed as separate components and are connected via long circuit conductor paths to each installed component. It was configured to be As a result, many unnecessary lead inductances and stray capacitors are generated, which makes the operation of the tuner unstable and makes it difficult to realize the initial design goals. Therefore, a lot of time was wasted on design work including modifications. Moreover, since each tuner is a collective circuit of separate parts that are independent minimum functional units, it has been impossible to reduce the number of parts and rationalize manufacturing using existing technical concepts.

This has resulted in problems such as a limit to the cost reduction of the tuner.

OBJECTS OF THE INVENTION The present invention consists in integrating an inductor part and a capacitor part, thereby making the form of the tuner ultra-thin and compact, and furthermore,
A tuner that is mechanically stable, has low temperature dependence of tuning frequency and tuning Q, is stable at high frequencies by eliminating the negative effects of connection leads, and also reduces the number of parts and streamlines the manufacturing process. The purpose is to provide

Structure of the Invention In order to achieve the above object, the present invention has a structure in which the ground terminals or common terminals of the electrodes placed opposite to each other with a dielectric substrate in between are set to be on the opposite side. It acts as an inductor, and the other electrode of this electrode faces to form a distributed constant circuit with an open-ended transmission path, and a capacitor is realized by the negative reactance generated by this distributed constant circuit. They act in parallel.

DESCRIPTION OF EMBODIMENTS Tuners in embodiments of the present invention will be described below with reference to the drawings.

FIG. 4 shows the configuration of a tuner to illustrate the principle of the present invention. 4A shows a front view of the tuner, FIG. 4B shows a side view thereof, and FIG. 4C shows a back view thereof. In FIGS. 4a to 4c, 15 is a plate-shaped dielectric made of ceramic or the like, and 16 is an electrode forming an inductor on the surface of the dielectric 15. In FIGS. 17 is a dielectric 15
The electrode 17 and the electrode 16 form a distributed constant circuit and a capacitor. 18 is the electrode 16
19 is an open terminal of the electrode 16. On the other hand, in the electrode 17, the electrode 16
20 on the opposite side to the terminal 18 is a ground terminal, and 21 is an open terminal.

5a-5c show other tuner configurations to illustrate the principles of the invention. In the figure, the installation configuration of the electrodes 23 and 24 on the plate-shaped dielectric 22 is the same as the example explained in FIGS. 4a to 4c, but the positions of the common terminals are reversed.
3 is an open terminal, and 26 is a ground terminal of the electrode 23. On the other hand, 27 is a ground terminal of the electrode 24, and 28 is an open terminal of the electrode 24.

FIGS. 6a-6c show still other tuner configurations to illustrate the principles of the present invention. As shown in the figure, an electrode 30 and an electrode 31 are arranged side by side on the same surface of a plate-shaped dielectric 29, and the electrodes 30 and 31 are arranged side by side to face each other. 32 is a ground terminal of the electrode 30, and 33 is an open terminal. On the other hand, in the electrode 31, 34 is an open terminal, and 35 is a ground terminal of the electrode 31. Here, the terminal mode for each electrode 30, 31 can be arbitrarily set by arranging the ground terminal and the open terminal to be on the opposite sides, respectively, as explained in FIGS. 4 a to c and 5 a to c. .

7a to 7c show the configuration of a tuner to illustrate the principle of the present invention. The installation configuration and terminal mode of the electrodes 37 and 38 relative to the plate-shaped dielectric 36 are the same as those described in FIGS. 4a to 4c, but the areas of the electrodes 37 and 38 are not the same;
Further, each electrode 37, 38 is arranged so as to partially face each other.

Figures 8a-c to 10a-c are the first embodiments of the present invention.
- This shows the configuration of a tuner in a third embodiment. The installation configuration and terminal mode of the electrodes 40 and 41 on the plate-shaped dielectric 39 in FIG. 8, the installation configuration and terminal mode of the electrodes 43 and 44 on the plate-shaped dielectric 42 in FIG. 9,
The installation configuration and terminal mode of the electrodes 46 and 47 relative to the dielectric 45 in FIG. 10 are the same as those described in FIGS. Use one that has a bent part that indicates the direction of bending.

11a to 11c show the configuration of a tuner in a fourth embodiment of the present invention. The arrangement and terminal mode of the electrodes 49 and 50 relative to the plate-shaped dielectric 48 are the same as in the example explained in FIG. 4, but each electrode has a spiral shape.

FIGS. 12a to 12c show the configuration of a tuner for illustrating the principle of the present invention. Plate-shaped dielectric 5
The installation configuration and terminal mode of the electrodes 52 and 53 relative to the electrode 1 are the same as the example explained in FIG. This is the installed configuration.

13a to 13c show the configuration of a tuner for illustrating the principle of the present invention. Plate-shaped dielectric 5
The installation configuration and terminal mode of the electrodes 55 and 56 for the dielectric 54 are the same as the example described in FIG.

FIGS. 14a and 14b show the configuration of a tuner in a fifth embodiment of the present invention. An electrode 58 is installed on the inner periphery of the cylindrical dielectric 57, and an electrode 59 is placed opposite the electrode 58 on the outer periphery. The ground terminals of the electrodes 58 and 59 are set in opposite directions. Here, in addition to the cylindrical dielectric body 57, a rectangular cylinder shape or a solenoid shape can also be used.

In addition, in the embodiments shown in FIGS. 8 to 11, the bent portions are formed in an arcuate pattern having an arbitrary bending angle. It goes without saying that the electrode may be formed with a pattern of:

In addition, in the example shown in FIG. 13, both electrodes 5
5 and 56 are not installed inside the dielectric 54, but one arbitrary electrode 55 is installed inside the dielectric 54,
The other electrode 56 may be placed on the surface of the dielectric 54.

In each of the above embodiments, the ground terminal of each electrode does not have to be specially set as a ground terminal, but can be generally set as a common terminal and connected to other circuit parts (not shown) to achieve the required purpose. can be achieved. Further, these ground terminals or common terminals are not limited to the ends of each electrode, but can be arbitrarily set at respective portions that are positioned in different directions.

In each of the above, those shown in FIGS. 4 and 5 can be constructed with a simple electrode pattern, and can easily form a highly accurate electrode pattern. Thereby, it is possible to realize a tuner that matches the design target tuning frequency with extremely high accuracy. In the case shown in FIG. 6, since both electrodes 30 and 31 can be formed on only one side of the dielectric 29, the manufacturing process can be simplified, and furthermore, both electrodes 30 and 31 can be formed in the same electrode formation process. Can be formed. This makes it possible to achieve extremely high setting accuracy between the electrodes, and to construct a tuner that matches the design target tuning frequency with extremely high accuracy. In the case shown in FIGS. 7 and 12, a desired purpose tuner can be realized even if the patterns of both electrodes do not match completely. Thereby, it is possible to realize a tuner in which the tuning frequency can be arbitrarily set depending on the length and width of the portion where both electrodes face each other. In the configuration shown in FIGS. 8 to 11, it is possible to form a relatively large distributed inductor and distributed capacitor even if the area occupied by the tuner is small. Therefore, a compact tuner with a relatively low tuning frequency can be realized, and the space factor of the tuner can be improved. 13th
What is shown in the figure can be introduced into the manufacturing process of multilayer circuit boards. As a result, the electrodes 55 and 56 are installed inside the dielectric 54 and are not exposed to the outside, so that they are not directly affected by changes in external conditions. Therefore, since the tuning frequency of the tuner is not affected, it is possible to realize a tuner with extremely stable performance. Even if the tuner shown in FIG. 14 is made smaller than those shown in FIGS. 4 to 13, it is possible to form a sufficiently large inductor and capacitor. Therefore, an ultra-small tuner having a sufficiently low tuning frequency can be realized. In addition, when manufacturing the device shown in FIG. 14, electrodes 58 and 59 are successively formed on a continuous cylindrical dielectric 57, and the electrodes 58 and 59 are cut to the required length. It can be manufactured quickly and easily.

In addition, as the transmission line electrode in each of the above embodiments, a metal conductor, a printed metal foil conductor, a thick film printed conductor, a thin film conductor, etc. can be used.
Further, the transmission path electrode may be formed by combining different types of the above-mentioned conductors. On the other hand, dielectric materials include alumina ceramic, chitavari, plastic,
Teflon (registered trademark), glass, mica, resin-based printed circuit boards, etc. can be used.

The operation of the tuner of this embodiment configured as described above will be explained below.

FIGS. 15a to 15e are equivalent circuits for explaining the operation of the tuner of the present invention. In FIG. 15a, the transmission line electrodes 70, 7 each have an electrical length l and have their ground terminals set in opposite directions.
Assume that a signal source 72 that generates a voltage e is connected to the transmission line electrode 70 to supply a signal to the transmission line formed by the transmission line 1. As a result, a traveling wave voltage e _A is excited at the open terminal at the tip of the transmission line electrode 70 . On the other hand, since the transmission line electrode 71 is disposed close to the above-mentioned transmission line electrode 70 and facing each other or in parallel, a voltage is induced by mutual induction. Let e _B be the traveling wave voltage induced in the open terminal at the tip of the transmission line electrode 71.

Here, since the respective ground terminals of the transmission line electrodes 70 and 71 are set in opposite directions, the induced traveling wave voltage e _B has an opposite phase to the excited traveling wave voltage e _A. Since the tips of the transmission paths of the traveling wave voltages e _A and e _B are open, voltage standing waves are formed in the transmission path formed by the transmission path electrodes 70 and 71. Here, if the voltage distribution coefficient indicating the distribution mode of voltage standing waves in the transmission line electrode 70 is expressed as K, then the voltage distribution coefficient in the transmission line electrode 71 can be expressed as (1-K).

Therefore, next, we will discuss the potential difference V generated at any opposing portions of the transmission line electrodes 70 and 71.
can be expressed as V=Ke _A −(1−K)e _B (1). Here, assuming that the respective transmission line electrodes 70 and 71 have the same electrical length l, e _B = -e _A ...(2), so that the potential difference V in the first equation is V = Ke _A + (1 -K) e _A = e _A ...(3). That is, a potential difference V can be generated in all parts where the transmission line electrodes 70 and 71 face each other.

Here, it is assumed that the transmission line electrodes 70 and 71 have an electrode width W (the thickness of the electrodes is thin), and are opposed to each other at a distance d via a dielectric material having a dielectric constant ε _S. . In this case, the capacitance C _O formed per unit length of the transmission path is C _O =Q/V=Q/e _A ...(4) Q=ε _O ε _S W・V/d=ε _O ε _S W・e _A /d……(5
), and therefore C _O = ε _O ε _S W/d ...(6).

Therefore, the transmission line shown in FIG. 15a becomes a transmission line including a distributed capacitor 73 of C _O determined by the formula 6 per unit length as shown in FIG. 15b. Furthermore, as shown in FIG. 15c, this transmission line has a distributed inductor component 77 and 7 due to a distributed inductor component of the transmission line and a concentrated inductor component generated by the bent shape of the transmission line.
8 and a distributed capacitor 73.

Next, the relationship between the formation of the distributed capacitor 73 and the electrical length l of the transmission path will be explained. The characteristic impedance Z _O per unit length in a balanced mode transmission line as shown in FIG. 16a can be expressed by an equivalent circuit shown in FIG. 16b. Its characteristic impedance Z _O is generally becomes. If the transmission path is lossless, then becomes. This assumption can be applied to many of the embodiments of the tuner of the present invention, and to simplify the explanation, the characteristic impedance Z _O
Use. The capacitance C _O in the eighth equation is the same as the capacitance C _O per unit in the transmission line found in the sixth equation. In other words, the characteristic impedance per unit length in the transmission line
Z _O is a function of the capacitance C _O , which is also a function of the permittivity ε _S of the dielectric material involved in the capacitor C _O , the width W of the transmission line electrodes and the spacing d between the respective transmission line electrodes.

As described above, the characteristic impedance per unit length in the transmission line is Z _O , the electrical length is l, and the equivalent reactance X generated at the terminal of the transmission line with the end open is X = -Z _O cotθ can be expressed as (9). Here, θ=2πl/λ...(10), and especially in the case of θ=O~π/2 θ=π~3/4π...(11), the equivalent reactance X is X≦O...(12) becomes. In other words, the equivalent reactance at the terminal of the transmission line can be the capacitive reactance. Therefore, depending on the electrical length l of the transmission path, θ becomes the
When formula 11 is satisfied, for example, a capacitor can be formed by setting the electrical length l to λ/4 or less. And the capacitance C of the capacitor that can be formed is As expressed by , any capacitance C can be realized by changing θ, that is, by setting the electrical length l of the transmission path.

FIG. 17 is a diagram illustrating the operation mode of the transmission line explained in Equations 9 to 13 above. FIG. 17 shows how the equivalent reactance X generated at the terminal changes in accordance with the change in the electrical length l of the transmission line with its tip in an open state. As is clear from Fig. 17, the electrical length l of the transmission line is λ/4 or less or λ/2 ~
In cases such as at 4λ/3, it is possible to form a negative terminal reactance, ie equivalently to form a capacitor.
Further, by arbitrarily setting the electrical length l of the transmission path under conditions that generate negative terminal reactance, it is possible to realize the capacitance C to an arbitrary value.

The capacitor C thus formed can be equivalently replaced as a lumped constant capacitor 79 shown in FIG. 15d. The inductor formed by combining the distributed inductor component existing in the transmission path and the lumped inductor component generated by bending the transmission path can be equivalently replaced as the lumped constant inductor 80. If the ground terminal is made common in FIG. 15 d, the final cost will be the same as that of a parallel resonant circuit consisting of a lumped constant capacitor 79 and a lumped constant inductor 80, as shown in FIG. 15 e. A tuner can be realized. Although the configuration and operation described above realize the tuner of the present invention, the configuration of the tuner of the present invention and its operating principle are completely different from those of conventional tuners. Therefore, in order to prove that the tuner according to the present invention is completely different from conventional tuners or those having other configurations even if they use the same transmission line as the tuner of the present invention. The structure and operation of a conventional tuner or a tuner with other transmission line configurations will now be described and compared. This clarifies the difference from the tuner according to the present invention and also clarifies the novelty of the tuner according to the present invention.

FIG. 18 shows the operation when the transmission line electrode is made of the same material as that used in the tuner of the present invention, but the difference is that the ground terminals are set in the same direction. be. In FIG. 18a, it is assumed that a transmission line with an open end consisting of transmission line electrodes 81 and 82 is driven by a signal source 83 that generates a voltage e. As a result, a standing wave voltage e _A is excited at the open terminal at the tip of the transmission line electrode 81, and a standing wave voltage e _B is excited at the open terminal at the tip of the transmission line electrode 82, which is placed opposite or in parallel. shall be induced. Here, since the ground terminals of the respective transmission line electrodes 81 and 82 are set in the same direction, the respective standing wave voltages
e _A and e _B are in phase with each other. Therefore, the respective voltage distribution coefficients at transmission line electrodes 81 and 82 have the same K. As a result, the potential difference V at any part where the transmission line electrodes face becomes Ke _A - Ke _B (14). Here, if the electrical lengths of the transmission line electrodes 81 and 82 are the same, e _A = e _B ... (15), so the potential difference V in Equation 14 is V = Ke _A - Ke _B =O...(16) In other words, no potential difference occurs in any part of the transmission path. FIG. 18b shows a configuration in which the signal source 83 in FIG. 18a is replaced at the end of the transmission line, and the cost is equivalent to installing an unbalanced signal source 84 that generates voltage e'. In this equivalent circuit, there are only parallel transmission lines with no potential difference between them. In other words, it is clear that this is equivalent to the case where only one transmission line electrode 85 exists, as shown in FIG. 18c. Then, by equivalently replacing the signal source 83 and the ground terminal with the original circuit as shown in FIG. 18a, the circuit shown in FIG. 18d is obtained. In other words, only an equivalent lumped constant inductor 86 is formed, which is composed of a distributed inductor component of the transmission line and a lumped inductor component generated by the curved shape of the transmission line. As is clear from the above, since a capacitor cannot be formed in parallel with an inductor, the intended parallel resonant circuit tuner cannot be realized.

Figure 19 shows a general microstrip line formed with the same transmission line electrode as in the tuner of the present invention as one side of the transmission line electrode, but the electrode facing the transmission line electrode has a sufficiently wide ground. This shows the operation when the curved points are different. In FIG. 19a, a transmission line electrode 87 faces a sufficiently wide ground electrode 88, is driven by a signal source 89 that generates voltage e, and a standing wave voltage e _A is excited at the open terminal at the end of the transmission line. Let K be the voltage distribution coefficient. On the other hand, the voltage distribution coefficient K is virtually applied to the ground electrode 88.
Assuming that a standing wave voltage e _B is generated, the potential difference V at any part where the transmission line electrode 87 and the ground electrode 88 face each other is expressed as V=Ke _A −Ke _B (17). However, the standing wave voltage e _B at the ground electrode 88 is uniformly at the ground potential (zero potential), and e _B =O (18). Therefore, there is no voltage distribution coefficient in the ground electrode 88 either. As a result, the potential difference V becomes V=Ke _A (19). This makes it possible to form a distributed capacitor between the transmission line electrode 87 and the ground electrode 88. However, since the transmission line electrode 87 is located close to and facing the ground electrode 88, the two ends of the transmission line electrode 87 are almost equivalent to being in a shot state due to mutual induction. Therefore, the Q performance of the inductor component in the transmission line electrode 87 is significantly degraded. In other words, this microstrip line is the 19th
A lumped constant inductor 91 and a lumped constant capacitor 92 including an equivalent loss resistance 90 as shown in FIG.
A parallel resonant circuit is formed by each. Here, since the equivalent loss resistance 90 actually has a considerably large resistance value, the loss in the resonant circuit becomes very large. Therefore, it is obvious that only a tuner with very low Q performance can be realized, and is not suitable for practical use.

FIG. 20 shows the circuit configuration of a λ/4 resonator, which is the most commonly used circuit in the past. This shows that the tuner is completely different from the tuner of Second
In Figure 0, balanced mode transmission line electrodes 93 and 9
4, whose electrical length l is λ/4 at the resonant frequency
and the tip is shot. It is assumed that each transmission line electrode is driven in a balanced mode by a balanced signal source 95 that generates voltage e. The ground terminal is set at the neutral point of the balanced signal source 95, and does not specifically ground any terminal in the transmission line electrode. In this case, the equivalent terminal reactance X generated at the terminal of the transmission line is as follows, where Z _O is the characteristic impedance of the transmission line: X=Z _O tanθ (20). Here, the characteristic impedance Z _O is the same as that shown in the 8th equation, and θ is the same as that shown in the 10th equation. In this resonator, the electrical length l of the transmission path is l = λ/4 (21), so θ = π/2 (22). Therefore, _the terminal reactance X in Equation 20 is as follows: However, when comparing the configuration of this λ/4 resonator with the configuration of the tuner of the present invention, first of all, regarding the terminal conditions of the transmission line, the tuner of the present invention is in an open state, whereas the conventional λ/4 resonator has an open state. It is clear that the /4 resonator is in a short state and therefore has a completely different configuration in terms of terminal conditions. Furthermore, regarding the setting of the electrical length l of the transmission line, in the tuner of the present invention, it is set to λ/4 or less of the tuning frequency, and in practice it is set to a very short value of about λ/16. However, the conventional λ/4
In the resonator, the resonant frequency is strictly set to λ/4, and it is therefore clear that the configuration is fundamentally different in setting the electrical length l of the transmission path. Also, the electrical length l of the transmission path in the configuration
Due to the difference in λ/
In the case of four resonators, it is necessary to provide a very long transmission path, which has the disadvantage of increasing the size. Conventional λ/
4.In order to downsize the resonator, there are some cases in which the length of the transmission path is shortened by interposing a dielectric material with a very high permittivity, but the dielectric material with a high permittivity used for this purpose generally has a dielectric loss tanδ. It is very large, and therefore has the disadvantage that the Q performance as a resonator is significantly reduced. Furthermore, the temperature dependence of the dielectric constant of a dielectric material having a high dielectric constant is generally large, and therefore there is also the disadvantage that it is difficult to ensure the stability of the resonant frequency.

Next, in order to clarify the superiority of the performance of the tuner of the present invention, experimental results will be shown and explained in comparison with the performance of a conventional tuner. FIG. 21 is a graph showing the experimental results of measuring the temperature dependence of the tuning frequency. The 22nd graph is a graph showing the experimental results of measuring the temperature dependence characteristics of resonance Q. In FIGS. 21 and 22, characteristic A is the temperature dependence of the tuner according to the present invention, and is an experimental result when an alumina ceramic material or a resin-based printed circuit board is used as the dielectric material. On the other hand, characteristic B is as shown in FIG.
This is the temperature-dependent characteristic of the tuner most commonly used in the past. From these experimental results, it is clear that in the tuner of the present invention, even if it is constructed using a general dielectric material, its tuning frequency is extremely stable, and furthermore, the resonance Q is high and it is stable. On the other hand, in conventional tuners, the tuning frequency and Resonance Q
It was difficult to ensure stability. Thereby, other temperature compensation components or other self-stabilizing compensation circuits were added to compensate for the instability.

Effects of the Invention As described above, the present invention effectively reduces the potential difference between the respective transmission path electrodes by setting the ground terminals or common terminals of the electrodes that are placed opposite to each other through a dielectric material to be on opposite sides. is generated, thereby forming a distributed capacitor, and acting in parallel with a comprehensive inductor consisting of a distributed constant inductor and a lumped constant inductor in the transmission line, equivalently forming a parallel resonant circuit to form a tuner. I'm trying to make it happen.

An inductor and a capacitor can be integrated into an extremely simple structure and a simple manufacturing method using only two electrodes and one dielectric that function as transmission paths. Thereby, it is possible to realize a tuner that can be handled as a single component.

The shape of the tuner can be made ultra-thin, which has never been seen before, and it can also be made smaller and lighter at the same time, resulting in a dramatic improvement in space factor. By that,
The present invention can contribute to thinner, smaller, and lighter equipment in which the tuner of the present invention is mounted.

Since the tuner can be realized with a modular configuration in which there are no mechanically movable parts, fluctuations in the tuning frequency and resonance Q due to fluctuations in ambient conditions can be made extremely small. In particular, it is possible to realize a tuner that is extremely stable against mechanical vibrations.

Even if a common dielectric material (alumina ceramic or resin printed circuit board) is used, it is possible to realize a tuner in which the temperature dependence of the tuning frequency and resonance Q is extremely stable. Therefore, it is no longer necessary to manage the temperature characteristics of individual components, which was the most difficult task when designing a conventional tuner, and the design management of the temperature characteristics of the tuner can be made extremely easy. Furthermore, the temperature-dependent characteristics are stable, and the above-mentioned effect, including stability against mechanical vibration, dramatically improves not only the stability of the tuner but also the reliability of the equipment in which it is installed. be able to.

A resonator and a microstrip line (a transmission line constructed by forming a transmission line electrode on one side of a dielectric and a wide ground electrode on the other side, as shown in Figure 19), which have been widely used in the past, In comparison, the loss due to the proximity of the ground electrode can be reduced, so a sufficiently high resonance Q can be achieved.
It is possible to realize a tuner having the following.

Since the inductor and capacitor can be configured as an integrated unit, there is no need for unnecessary connecting leads to be interposed in the tuner, and unstable elements such as lead inductance caused by connecting leads and stray capacitors are completely eliminated. I can do it. Thereby, the tuning operation of the tuner can be realized extremely stably up to the ultra-high frequency range. In addition, since there is no unstable element of reactance component with respect to the design target value of the tuning frequency, the target tuning frequency can be easily secured.
Tuner design can be simplified. Thereby, it is possible to easily standardize the design method of the tuner, and it is possible to improve efficiency in the work of designing the tuner.

Since the tuner can be constructed by combining the minimum functional elements consisting only of transmission line electrodes and dielectric materials, the tuner can be manufactured with a small amount of materials. This makes it possible to save resources and to significantly reduce the manufacturing cost of the tuner.

In the conventional tuner, it was necessary to install two parts each, an inductor and a capacitor, but on the other hand, the tuner of the present invention can be constructed from a single modular part. The number of parts of the tuner can therefore be reduced significantly. Thereby, it is possible to reduce the assembly cost of the tuner, and also to reduce the manufacturing time required for assembly. Furthermore, since the types and quantities of parts in stock can be reduced, manufacturing management can be streamlined. Therefore, the total cost of the tuner can be significantly reduced.

The design of the tuner can be handled with simple artwork such as determining the shape pattern of the transmission line electrodes. Therefore, a high level of skill is not required to design the tuner, and design changes can be easily accommodated. Furthermore, in response to automation in the design of the tuner, a design method using computer graphics can be easily introduced. In other words, the features of the artwork design in the tuner of the present invention match well, and the tuner is simple and easy to convert into data, with the only design parameters being the dimensions of the transmission line electrode pattern, the thickness of the dielectric material, and the dielectric constant. The composition is as follows. As a result, it is possible to shorten the time required for design, improve the design accuracy of the tuning frequency, and realize a tuner with improved design freedom.

[Brief explanation of drawings]

Figure 1 is a basic circuit diagram of a tuner, Figures 2 and 3 are perspective views showing the configuration of a conventional tuner, Figures 4 a-c to 7 a-c, and Figure 12 a. ~
c, Figures 13a-c are front, side, and back views of the tuner illustrating the principle of the present invention, and Figures 8a-c-
11a to 11c are front, side, and back views of the tuner according to the embodiment of the present invention, and FIGS. 14a and 14b are
15 a to e, FIGS. 16 a, b, and 1
Fig. 7 is an explanatory diagram showing the operating principle of the present invention, Figs. 18 a to d, Figs. 19 a and b, and Fig. 20 are explanatory diagrams showing the operating principle of a conventional tuner, Figs. 21 and 22. is a characteristic diagram of the tuning frequency and resonance Q with respect to temperature changes of the present invention and a conventional tuner. 15,2
2, 29, 36, 39, 42, 45, 48, 5
1, 54, 57...dielectric, 16, 17, 23,
24, 30, 31, 37, 38, 40, 41, 4
3, 44, 46, 47, 49, 50, 52, 5
3, 55, 56, 58, 59, 70, 71, 7
5, 76, 81, 82, 85, 87, 93, 94
...Transmission line electrode.

Claims (1)

[Claims] 1. First and second electrodes, each having a predetermined electrical equivalent length and having at least one bent portion, are disposed opposite to each other with a dielectric interposed therebetween, and The ground terminals or common terminals of the respective electrodes are set at predetermined positions in a differentially opposing positional relationship that does not include portions facing each other, and a first terminal is further provided at a predetermined position on the first or second electrode, and A tuner that equivalently forms a resonant circuit in a two-terminal circuit network having a first terminal and the ground terminal or the common terminal as a second terminal. 2. The tuner according to claim 1, wherein electrodes are provided on the front and back sides of the dielectric. 3 Claim 1 in which the electrodes have different equivalent lengths
Tuner as described in section. 4. The tuner according to claim 1, wherein the dielectric body has a cylindrical shape or a prismatic tube shape. 5. The tuner according to claim 1, wherein the dielectric has a plate shape. 6 First and second electrodes, each having a predetermined electrical equivalent length, are installed opposite to each other with a dielectric interposed therebetween, and do not include a portion where the ground terminal or common terminal of each of the first and second electrodes faces each other. A first terminal is provided at a predetermined position of the first or second electrode, and the first terminal and the ground terminal or the common terminal are connected to a second terminal. A tuner in which a resonant circuit is equivalently formed in a two-terminal circuit network, wherein the electrode has a spiral shape.